CN113992190A - Double-layer filter bank design method for DVB-RCS2 - Google Patents

Double-layer filter bank design method for DVB-RCS2 Download PDF

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CN113992190A
CN113992190A CN202111585423.0A CN202111585423A CN113992190A CN 113992190 A CN113992190 A CN 113992190A CN 202111585423 A CN202111585423 A CN 202111585423A CN 113992190 A CN113992190 A CN 113992190A
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filter
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CN113992190B (en
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王捷
缪开济
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Nanjing Xianfeng Shuotong Wireless Technology Co ltd
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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H17/00—Networks using digital techniques
    • H03H17/02—Frequency selective networks
    • H03H17/0294—Variable filters; Programmable filters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H17/00—Networks using digital techniques
    • H03H17/02—Frequency selective networks
    • H03H17/0219—Compensation of undesirable effects, e.g. quantisation noise, overflow
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H17/00—Networks using digital techniques
    • H03H17/02—Frequency selective networks
    • H03H17/0248—Filters characterised by a particular frequency response or filtering method
    • H03H17/0264—Filter sets with mutual related characteristics
    • H03H17/0273—Polyphase filters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H17/00—Networks using digital techniques
    • H03H2017/0072—Theoretical filter design
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H17/00—Networks using digital techniques
    • H03H2017/0072—Theoretical filter design
    • H03H2017/0081—Theoretical filter design of FIR filters

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Abstract

The invention provides a design method of a double-layer filter bank for DVB-RCS2, which utilizes the composition characteristics of MF-TDMA superframes/frames, adopts a double-layer FB technology, adopts PR TMUX based on CMFB to realize RNFB with variable time-frequency resolution between full-frequency-band MF-TDMA frames in the first layer, adopts a multiphase structure to realize RNFB so as to reduce complexity and improve operation speed, and adopts a multiphase interpolation technology to realize uniform FB of multi-carrier in the MF-TDMA frames in the second layer. The invention designs the FB which can almost perfectly support the dynamic allocation of DVB-RCS2 RL MF-TDMA frequency-time slot resources, and compared with the filtering of all sub-carriers of full-band MF-TDMA which is realized by adopting the classical RNFB, the FB has high flexibility, low complexity and simplicity.

Description

Double-layer filter bank design method for DVB-RCS2
Technical Field
The invention belongs to the technical field of satellite communication, and particularly relates to a design method of a double-layer filter bank for DVB-RCS 2.
Background
A Satellite Digital television broadcast Return Channel (DVB-RCS) broadband Satellite communication system providing various interactive services generally consists of geostationary orbiting satellites operating in the C, X, Ku and Ka bands and a large number of Return Channel Satellite Terminals (RCSTs) distributed over a wide geographical area and employing small aperture antennas, the RCSTs communicating with HUB gateways via satellites. DVB-RCS2 is a new satellite interaction network system based on DVB-RCS, which adopts DVB-S2 forward broadcast and multi-frequency-time division multiple access (MF-TDMA) multi-point return mode, all terminals use MF-TDMA shared satellite return channel, each terminal distributes limited frequency time slot transmission Bursts (Bursts) in limited time period, and HUB gateway station receiver needs to receive all RCST transmission Bursts of various transmission formats MF-TDMA in all frequency bandwidths.
MF-TDMA is designed to dedicate a specific transport format class to each frame, so that all time slots in each frame use equal symbol rates, i.e. occupy equal frequency bandwidth. Dynamic MF-TDMA allows multiple RCSTs (i.e., RCSTs) to transmit consecutive bursts using different transport format classes in different frames, i.e., RCSTs may occupy different frequencies and bandwidths in different frames, which means that the frequencies and bandwidths used by the RCSTs may vary over time, and thus, fast carrier frequency (bandwidth) switching needs to be achieved.
In summary, when the DVB-RCS2 system adopts dynamic MF-TDMA, the HUB gateway station receiver needs to support dynamic allocation of MF-TDMA frequency-timeslot resources by using a reconfigurable non-uniform filter bank (RNFB). RNFB can in principle be implemented directly by band-pass interpolation/decimation with variable conversion factor and center frequency, which requires the use of variable up-sampler/down-sampler and band-pass filter with variable center frequency and bandwidth to construct the variable parameter interpolator/decimator, however, this direct method needs a large number of filters with different orders and characteristics to cover such a wide range of interpolation/decimation factor, and the implementation complexity and cost are very high, which is difficult to be used. The RNFB with lower complexity realizes various design methods such as a recombination method, a modulation method, a coefficient extraction method and the like, but the methods are not designed by utilizing the composition characteristics of MF-TDMA superframes/frames, and the realization complexity still has a larger space for reducing. Therefore, it is necessary to design a new design method of dual-layer filter bank for implementing DVB-RCS2 dynamic MF-TDMA.
Disclosure of Invention
Aiming at the defects in the prior art, the invention provides a design method of a double-layer filter bank for DVB-RCS2, wherein the first layer adopts PR TMUX based on CMFB to realize RNFB with variable time-frequency resolution between full-band MF-TDMA frames, the RNFB is realized by multiple phases, the second layer adopts a multi-phase interpolation technology to realize multi-carrier uniform FB (filter bank) in the MF-TDMA frames, the complexity can be effectively reduced, and the operation speed can be improved.
The present invention achieves the above-described object by the following technical means.
A design method of a double-layer filter bank for DVB-RCS2 is disclosed, wherein a first layer adopts PR TMUX based on CMFB to realize RNFB with variable time-frequency resolution between full-frequency band MF-TDMA frames, the RNFB is realized by a multiphase structure, and a second layer adopts multiphase interpolation technology to realize multi-carrier uniform FB within the MF-TDMA frames;
the first layer design method comprises the following steps:
step 1: designing a prototype filter: the prototype filter is realized by an FIR filter structure based on FRM technology, and a plurality of wide transition band filters are used to form the prototype filter which is a narrow transition band as a whole;
step 2: determining a prototype filter according to the passband cut-off frequency, the stopband starting frequency, the passband fluctuation peak value and the stopband fluctuation peak value of the plurality of wide transition band filters used in the step 1
Figure DEST_PATH_IMAGE001
Length of (2)
Figure 100002_DEST_PATH_IMAGE002
；
And step 3: design a
Figure DEST_PATH_IMAGE003
A channel uniform-resolution FB with a prototype filter of
Figure 239927DEST_PATH_IMAGE001
The prototype filter has a length of
Figure 933077DEST_PATH_IMAGE002
The stop band cut-off frequency is
Figure 100002_DEST_PATH_IMAGE004
(ii) a Wherein,
Figure DEST_PATH_IMAGE005
representing a decimation factor, the number of channels of the analysis filter is also
Figure 401098DEST_PATH_IMAGE005
，
Figure 100002_DEST_PATH_IMAGE006
Which is indicative of a roll-off factor,
Figure DEST_PATH_IMAGE007
；
and 4, step 4: design a
Figure 100002_DEST_PATH_IMAGE008
The CMFB with uniform channel recombination has a prototype filter of
Figure DEST_PATH_IMAGE009
The prototype filter has a length of
Figure 100002_DEST_PATH_IMAGE010
The starting frequency of the stop band is
Figure DEST_PATH_IMAGE011
(ii) a Wherein,
Figure 100002_DEST_PATH_IMAGE012
representing the number of uniform recombination filter channels;
and 5: obtaining a PR TMUX based on the CMFB as
Figure DEST_PATH_IMAGE013
And is and
Figure 100002_DEST_PATH_IMAGE014
Figure DEST_PATH_IMAGE015
，
Figure 100002_DEST_PATH_IMAGE016
wherein,
Figure DEST_PATH_IMAGE017
representing an imaginary number;
Figure 100002_DEST_PATH_IMAGE018
、
Figure DEST_PATH_IMAGE019
all represent intermediate variables;
Figure 100002_DEST_PATH_IMAGE020
；
step 6: let us say the second in RNFB
Figure DEST_PATH_IMAGE021
Of a branch
Figure 100002_DEST_PATH_IMAGE022
Is sub-band at
Figure 407755DEST_PATH_IMAGE003
Starting from index numbers in a channel uniform parsing FB
Figure DEST_PATH_IMAGE023
，
Figure 100002_DEST_PATH_IMAGE024
Is even number, then
Figure 226806DEST_PATH_IMAGE021
Is branched at
Figure 723646DEST_PATH_IMAGE003
Channel uniform resolution in FB
Figure 374071DEST_PATH_IMAGE012
A sub-band can adopt
Figure 298164DEST_PATH_IMAGE008
Directly combining the channels PR TMUX synthesis filters;
Figure 666829DEST_PATH_IMAGE024
odd, the corresponding channel is multiplied by the sequence before combining the sub-bands
Figure DEST_PATH_IMAGE025
Wherein
Figure 100002_DEST_PATH_IMAGE026
indicating an input data sequence;
and 7: in that
Figure 639464DEST_PATH_IMAGE003
The channel uniformly analyzes other branches of the FB to compensate the time delay caused by inserting the TMUX;
the second layer design method comprises the following steps: the second layer implements intra-frame MF-TDMA uniform FB using typical polyphase interpolation techniques, where
Figure DEST_PATH_IMAGE027
Is as follows
Figure 878815DEST_PATH_IMAGE021
The interpolation factor and the number of sub-carriers within a frame frequency band,
Figure 100002_DEST_PATH_IMAGE028
is a prototype filter
Figure DEST_PATH_IMAGE029
Is/are as follows
Figure 100002_DEST_PATH_IMAGE030
Phase component of multiple phases, and
Figure DEST_PATH_IMAGE031
second layer prototype filter
Figure 318018DEST_PATH_IMAGE029
Has a length of
Figure 100002_DEST_PATH_IMAGE032
。
Further, the step 1 specifically comprises:
setting a known sampling rate factor of
Figure DEST_PATH_IMAGE033
Figure 100002_DEST_PATH_IMAGE034
，
Figure DEST_PATH_IMAGE035
Is the number of bands of a full band MF-TDMA frame, and
Figure 100002_DEST_PATH_IMAGE036
symmetric impulse response linear phase LPF mode
Filter
Figure DEST_PATH_IMAGE037
Is of odd length
Figure 100002_DEST_PATH_IMAGE038
Complementary filter thereof
Figure DEST_PATH_IMAGE039
Can be expressed as:
Figure 100002_DEST_PATH_IMAGE040
by using
Figure DEST_PATH_IMAGE041
Each delay unit in the LPF modal filter and its complementary filter is replaced by one delay to form
Figure 100002_DEST_PATH_IMAGE042
And
Figure DEST_PATH_IMAGE043
two filters for filtering the two masksDevice for cleaning the skin
Figure 100002_DEST_PATH_IMAGE044
And
Figure DEST_PATH_IMAGE045
are respectively cascaded
Figure 731901DEST_PATH_IMAGE042
And
Figure 570544DEST_PATH_IMAGE043
the transfer function of the entire filter after cascading (i.e., the prototype filter) is:
Figure 100002_DEST_PATH_IMAGE046
and is
Figure DEST_PATH_IMAGE047
，
Figure 100002_DEST_PATH_IMAGE048
，
Figure DEST_PATH_IMAGE049
，
Figure 100002_DEST_PATH_IMAGE050
，
Figure DEST_PATH_IMAGE051
，
Figure 100002_DEST_PATH_IMAGE052
，
Figure DEST_PATH_IMAGE053
；
Wherein,
Figure 100002_DEST_PATH_IMAGE054
means less than
Figure DEST_PATH_IMAGE055
Of the up-sampling ratio of the LPF modal filter is
Figure 618397DEST_PATH_IMAGE041
，
Figure 100002_DEST_PATH_IMAGE056
And
Figure DEST_PATH_IMAGE057
respectively representing the passband cut-off frequency and the stopband start frequency of the prototype filter,
Figure 100002_DEST_PATH_IMAGE058
and
Figure DEST_PATH_IMAGE059
respectively representing the passband cut-off frequency and the stopband start frequency of the LPF modal filter,
Figure 100002_DEST_PATH_IMAGE060
and
Figure DEST_PATH_IMAGE061
respectively representing two mask filters
Figure 431763DEST_PATH_IMAGE044
And
Figure 509440DEST_PATH_IMAGE045
the passband cut-off frequency of (a),
Figure 100002_DEST_PATH_IMAGE062
and
Figure DEST_PATH_IMAGE063
respectively representing two mask filters
Figure 83598DEST_PATH_IMAGE044
And
Figure 563121DEST_PATH_IMAGE045
the stop band start frequency of (1).
Further, the mask filter
Figure 999919DEST_PATH_IMAGE044
And
Figure 564892DEST_PATH_IMAGE045
are equal in group delay, and
Figure 100002_DEST_PATH_IMAGE064
is an even number.
Further, the specific process of step 2 is as follows:
setting up
Figure DEST_PATH_IMAGE065
And
Figure 100002_DEST_PATH_IMAGE066
respectively, the passband fluctuation peak value and the stopband fluctuation peak value of the prototype filter, and the order of the FIR prototype filter is:
Figure DEST_PATH_IMAGE067
and (2) substituting the passband cut-off frequency and the stopband starting frequency of each sub-filter in the step (1) into an order calculation formula of the FIR prototype filter, wherein each sub-filter has the same passband and stopband fluctuation peak value as the prototype filter, and the order of each sub-filter can be calculated to determine the length of the prototype filter.
Further, the prototype filter is implemented using polyphase decomposition, resulting in a polyphase decomposition filter, since the polyphase decomposition filter coefficients are decimated
Figure 100002_DEST_PATH_IMAGE068
If the stopband attenuation SA is to be maintained
Figure 89545DEST_PATH_IMAGE066
Then FIR prototype filterIn the order calculation formula of (2), the second term on the right side is the extraction of the compensation coefficient
Figure 157996DEST_PATH_IMAGE068
The post polyphase decomposition filter stopband attenuation degrades the number of orders required to be added by the prototype filter.
Further, in the step 3,
Figure 765694DEST_PATH_IMAGE003
the prototype filter I-type polyphase decomposition of channel uniform-resolution FB is:
Figure DEST_PATH_IMAGE069
Figure 100002_DEST_PATH_IMAGE070
；
wherein,
Figure DEST_PATH_IMAGE071
representing the minimum parameter value obtained by PR constraint optimization;
Figure 100002_DEST_PATH_IMAGE072
represents a weight constant between 0 and 1;
Figure DEST_PATH_IMAGE073
and
Figure 100002_DEST_PATH_IMAGE074
are respectively as
Figure 896593DEST_PATH_IMAGE003
The channel uniformly resolves the passband cut-off frequency and the stopband cut-off frequency of the FB;
uniformly resolved FB is PR constrained:
Figure DEST_PATH_IMAGE075
wherein,
Figure 100002_DEST_PATH_IMAGE076
，
Figure DEST_PATH_IMAGE077
which represents a non-zero constant that is,
Figure 100002_DEST_PATH_IMAGE078
is a positive integer.
Further, in the step 4,
Figure 21675DEST_PATH_IMAGE008
prototype filter of channel uniform recombination CMFB
Figure 475790DEST_PATH_IMAGE009
Optimization by PR constraints, weighting of pass band and stop band and
Figure 519969DEST_PATH_IMAGE003
the channel CMFB is the same as the channel CMFB,
Figure 59535DEST_PATH_IMAGE008
the prototype filter of the channel uniform recombination CMFB meets the matching condition:
Figure DEST_PATH_IMAGE079
。
further, the FIR filter complexity is measured by the number of multiplications per unit time (MPU) and additions per unit time (APU) required;
the complexity of the first layer RNFB polyphase implementation is
Figure 100002_DEST_PATH_IMAGE080
And
Figure DEST_PATH_IMAGE081
；
the complexity of the implementation of the second-layer MF-TDMA intra-frame polyphase interpolating multicarrier uniform filter bank is
Figure 100002_DEST_PATH_IMAGE082
And
Figure DEST_PATH_IMAGE083
；
total implementation complexity of
Figure 100002_DEST_PATH_IMAGE084
And
Figure DEST_PATH_IMAGE085
；
wherein,
Figure 388973DEST_PATH_IMAGE035
indicating the number of bands of a full band MF-TDMA frame,
Figure 100002_DEST_PATH_IMAGE086
(ii) a MPUs denotes a plurality of multiplications per unit time and APUs denotes a plurality of additions per unit time.
The invention has the following beneficial effects:
the double-layer filter bank designed by the invention is specially applied to a HUB gateway station receiver of a DVB-RCS2 system for satellite communication, utilizes the characteristic of MF-TDMA superframe/frame composition, designs the filter bank which can nearly perfectly support DVB-RCS2 MF-TDMA frequency-time slot resource dynamic allocation, and has high flexibility, low complexity and simplicity compared with the filtering of all subcarriers of full-band MF-TDMA by adopting classical RNFB.
Drawings
FIG. 1 is a block diagram of the RNFB structure according to the present invention;
FIG. 2 is a block diagram of a FIR filter based on FRM technique;
FIG. 3 is a schematic diagram of the frequency response of an FIR filter based on FRM technology;
FIG. 4 is a diagram of a multiphase component implementation of RNFB;
fig. 5 is a diagram of a polyphase interpolated uniform FB implementation.
Detailed Description
The invention will be further described with reference to the following figures and specific examples, but the scope of the invention is not limited thereto.
As shown in fig. 1 to 5, the method for designing a dual-layer filter bank for DVB-RCS2 according to the present invention specifically includes the following steps:
as shown in fig. 1, the first layer adopts a Perfect Recombination (PR) multiplexer converter (TMUX) based on a Cosine Modulation Filter Bank (CMFB) to implement the RNFB with variable time-frequency resolution between full-band MF-TDMA frames, as shown in fig. 4, the RNFB is implemented by a polyphase structure, which reduces complexity and increases operation speed, and the specific design method mainly includes the following steps:
first, a known sampling rate factor is set to
Figure 100002_DEST_PATH_IMAGE088
Figure 100002_DEST_PATH_IMAGE090
，
Figure 100002_DEST_PATH_IMAGE092
Is the number of bands of a full band MF-TDMA frame, and
Figure 100002_DEST_PATH_IMAGE094
wherein
Figure 100002_DEST_PATH_IMAGE096
represents the decimation factor and the number of channels of the analysis filter is
Figure 41802DEST_PATH_IMAGE096
，
Figure 100002_DEST_PATH_IMAGE098
Representing the number of uniform recombination filter channels;
step 1: designing a prototype filter:
the prototype filter is realized by adopting a FIR filter structure based on a frequency response shielding (FRM) technology, and a plurality of wide transition band filters are used for forming the prototype filter which is integrally a narrow transition band;
setting symmetric impulse response linearityPhase LPF modal filter (namely low-pass modal filter)
Figure 100002_DEST_PATH_IMAGE100
Is of odd length
Figure 100002_DEST_PATH_IMAGE102
Complementary filter thereof
Figure 100002_DEST_PATH_IMAGE104
Can be expressed as:
Figure 100002_DEST_PATH_IMAGE106
by using
Figure 100002_DEST_PATH_IMAGE108
Each delay unit in the LPF modal filter and its complementary filter is replaced by one delay to form
Figure 100002_DEST_PATH_IMAGE110
And
Figure 100002_DEST_PATH_IMAGE112
two filters having a ratio of transition band widths
Figure 945299DEST_PATH_IMAGE100
Is narrow
Figure 706581DEST_PATH_IMAGE108
Doubling; in the FRM technique, two mask filters are used as shown in FIG. 2
Figure 100002_DEST_PATH_IMAGE114
And
Figure 100002_DEST_PATH_IMAGE116
are respectively cascaded
Figure 235783DEST_PATH_IMAGE110
And
Figure 398911DEST_PATH_IMAGE112
the transfer function of the entire filter after cascading (i.e., the prototype filter) is:
Figure 100002_DEST_PATH_IMAGE118
wherein the filter
Figure 988155DEST_PATH_IMAGE114
And
Figure 502313DEST_PATH_IMAGE116
must be equal, and
Figure 100002_DEST_PATH_IMAGE120
must be an even number;
Figure 100002_DEST_PATH_IMAGE122
，
Figure 100002_DEST_PATH_IMAGE124
，
Figure 100002_DEST_PATH_IMAGE126
，
Figure 100002_DEST_PATH_IMAGE128
，
Figure 100002_DEST_PATH_IMAGE130
，
Figure 100002_DEST_PATH_IMAGE132
，
Figure 100002_DEST_PATH_IMAGE134
；
wherein,
Figure 100002_DEST_PATH_IMAGE136
means less than
Figure 100002_DEST_PATH_IMAGE138
Of the up-sampling ratio of the LPF modal filter is
Figure 681595DEST_PATH_IMAGE108
，
Figure 100002_DEST_PATH_IMAGE140
And
Figure 100002_DEST_PATH_IMAGE142
respectively representing the passband cut-off frequency and the stopband start frequency of the prototype filter,
Figure 100002_DEST_PATH_IMAGE144
and
Figure 100002_DEST_PATH_IMAGE146
respectively representing the passband cut-off frequency and the stopband start frequency of the LPF modal filter,
Figure 100002_DEST_PATH_IMAGE148
and
Figure 100002_DEST_PATH_IMAGE150
respectively representing two mask filters
Figure 777858DEST_PATH_IMAGE114
And
Figure 334741DEST_PATH_IMAGE116
the passband cut-off frequency of (a),
Figure 100002_DEST_PATH_IMAGE152
and
Figure 100002_DEST_PATH_IMAGE154
respectively representing two mask filters
Figure 8299DEST_PATH_IMAGE114
And
Figure 941620DEST_PATH_IMAGE116
the stop band start frequency of (a);
there are 5 frequency response curves in fig. 3, and the first curve represents the LPF mode filter when viewed from top to bottom
Figure 813761DEST_PATH_IMAGE100
The passband cut-off frequency and the stopband start frequency of the modal filter are respectively
Figure 541546DEST_PATH_IMAGE144
And
Figure 30296DEST_PATH_IMAGE146
(ii) a The second curve represents the complementary filter of the LPF mode filter
Figure 236150DEST_PATH_IMAGE104
A frequency response; by using
Figure 228376DEST_PATH_IMAGE108
A delay replacement
Figure 392641DEST_PATH_IMAGE100
And
Figure 837529DEST_PATH_IMAGE104
each delay unit of (1) to obtain
Figure 847074DEST_PATH_IMAGE110
And
Figure 224965DEST_PATH_IMAGE112
two filters with a frequency response of a third curve; the fourth curve represents two mask filters
Figure 28973DEST_PATH_IMAGE114
And
Figure 226736DEST_PATH_IMAGE116
frequency response of
Figure 774392DEST_PATH_IMAGE114
And
Figure 6791DEST_PATH_IMAGE116
are respectively cascaded
Figure 981700DEST_PATH_IMAGE110
And
Figure 666759DEST_PATH_IMAGE112
(ii) a The fifth curve represents the prototype filter obtained after the cascade
Figure 100002_DEST_PATH_IMAGE156
The frequency response of (c). It can be seen that the present invention utilizes four sub-filters (i.e.
Figure 486948DEST_PATH_IMAGE110
、
Figure 573852DEST_PATH_IMAGE112
、
Figure 985242DEST_PATH_IMAGE114
、
Figure 892018DEST_PATH_IMAGE116
) A narrow transition band FIR prototype filter is obtained, and since the sub-filters have wide transition bands, the overall complexity is much lower than that of a narrow transition band FIR filter designed directly or by a conventional method.
Step 2: determining prototype filters
Figure 47056DEST_PATH_IMAGE156
Length of (2)
Figure 100002_DEST_PATH_IMAGE158
：
Setting up
Figure 100002_DEST_PATH_IMAGE160
And
Figure 100002_DEST_PATH_IMAGE162
respectively the passband cut-off frequency and the stopband start frequency of the prototype filter (normalized within 0-1, 1 corresponding to half of the sampling frequency),
Figure 100002_DEST_PATH_IMAGE164
and
Figure 100002_DEST_PATH_IMAGE166
respectively, the passband fluctuation peak value and the stopband fluctuation peak value of the prototype filter, and the order of the FIR prototype filter is:
Figure 100002_DEST_PATH_IMAGE168
（1）
the prototype filter is implemented using polyphase decomposition, resulting in a polyphase decomposition filter, since the coefficients of the polyphase decomposition filter are decimated
Figure 100002_DEST_PATH_IMAGE170
If the stopband attenuation SA is to be maintained
Figure 795657DEST_PATH_IMAGE166
Then the second term on the right side of equation (1) is the compensation coefficient extraction
Figure 112369DEST_PATH_IMAGE170
The attenuation of the stop band of the post polyphase decomposition filter deteriorates the required increased order of the prototype filter;
and (2) bringing the passband cut-off frequency and the stopband starting frequency of each sub-filter in the step (1) into a formula (1), and setting that each sub-filter has the same passband and stopband fluctuation peak value as the prototype filter, so as to obtain the order of each sub-filter, thereby determining the length of the prototype filter.
And step 3: design a
Figure 100002_DEST_PATH_IMAGE172
A channel uniform analysis filter bank having prototype filters of
Figure 240862DEST_PATH_IMAGE156
Filter length of
Figure DEST_PATH_IMAGE174
The stop band cut-off frequency is
Figure DEST_PATH_IMAGE176
(ii) a Setting the polyphase decomposition of type I of its prototype filter to
Figure DEST_PATH_IMAGE178
And is and
Figure DEST_PATH_IMAGE180
wherein,
Figure DEST_PATH_IMAGE182
which is indicative of a roll-off factor,
Figure DEST_PATH_IMAGE184
；
Figure DEST_PATH_IMAGE186
representing the minimum parameter value obtained by PR constraint optimization;
Figure DEST_PATH_IMAGE188
represents a weight constant between 0 and 1;
Figure DEST_PATH_IMAGE190
and
Figure DEST_PATH_IMAGE192
are respectively as
Figure 419165DEST_PATH_IMAGE172
The channel uniformly analyzes the passband cut-off frequency and the stopband cut-off frequency of the filter bank;
the uniform analysis filterbank is constrained by a Perfect Rebinning (PR) of the following equation (2):
Figure DEST_PATH_IMAGE194
（2）
Figure DEST_PATH_IMAGE196
wherein,
Figure DEST_PATH_IMAGE198
which represents a non-zero constant that is,
Figure DEST_PATH_IMAGE200
is a positive integer;
and 4, step 4: design a
Figure DEST_PATH_IMAGE202
Channel uniform recombination CMFB with filter length of
Figure DEST_PATH_IMAGE204
The starting frequency of the stop band is
Figure DEST_PATH_IMAGE206
The prototype filter is
Figure DEST_PATH_IMAGE208
PR constraint optimization is adopted; the weights of the pass band and stop band
Figure 762552DEST_PATH_IMAGE172
The channel CMFB is the same, which ensures that
Figure 515745DEST_PATH_IMAGE202
The channel homogeneous recombination CMFB approximately satisfies the matching condition in the following formula (3):
Figure DEST_PATH_IMAGE210
（3）
and 5: obtain the corresponding CMFB-based PR TMUX of
Figure DEST_PATH_IMAGE212
Wherein:
Figure DEST_PATH_IMAGE214
Figure DEST_PATH_IMAGE216
，
Figure DEST_PATH_IMAGE218
wherein,
Figure DEST_PATH_IMAGE220
representing an imaginary number;
Figure DEST_PATH_IMAGE222
、
Figure DEST_PATH_IMAGE224
all represent intermediate variables;
Figure DEST_PATH_IMAGE226
；
step 6: let us say the second in RNFB
Figure DEST_PATH_IMAGE228
Of a branch
Figure DEST_PATH_IMAGE230
Is sub-band at
Figure 345249DEST_PATH_IMAGE172
The index number in the channel uniform analysis filter bank starts from
Figure DEST_PATH_IMAGE232
If, if
Figure 310930DEST_PATH_IMAGE232
Is even number, then
Figure 961355DEST_PATH_IMAGE228
Is branched at
Figure 151028DEST_PATH_IMAGE172
In a channel uniform analysis filter bank
Figure 519692DEST_PATH_IMAGE230
A sub-band can adopt
Figure 554644DEST_PATH_IMAGE202
Directly combining the channels PR TMUX synthesis filters; if it is
Figure 59575DEST_PATH_IMAGE232
Odd, the corresponding channel is multiplied by the sequence before combining the sub-bands
Figure DEST_PATH_IMAGE234
Wherein
Figure DEST_PATH_IMAGE236
indicating an input data sequence;
and 7: in that
Figure 357832DEST_PATH_IMAGE172
The other branches of the channel uniform analysis filter bank compensate for the delay caused by the insertion of the TMUX.
As shown in FIG. 5, the second layer implements an intra MF-TDMA uniform filter bank using typical polyphase interpolation techniques, where
Figure DEST_PATH_IMAGE238
Is as follows
Figure 948213DEST_PATH_IMAGE228
The interpolation factor and the number of sub-carriers within a frame frequency band,
Figure DEST_PATH_IMAGE240
is a prototypeFilter
Figure DEST_PATH_IMAGE242
Is/are as follows
Figure DEST_PATH_IMAGE244
Phase component of multiple phases, and
Figure DEST_PATH_IMAGE246
second layer prototype filter
Figure 131064DEST_PATH_IMAGE242
Has a length of
Figure DEST_PATH_IMAGE248
。
FIR filter complexity is measured by the number of multiplications per unit time (MPU) and additions per unit time (APU) required, MPUs denoting multiple multiplications per unit time and APUs denoting multiple additions per unit time.
The complexity of the first layer RNFB multiphase implementation designed by the invention is as follows:
Figure DEST_PATH_IMAGE250
；
Figure DEST_PATH_IMAGE252
。
the complexity of implementing the second-layer MF-TDMA intra-frame polyphase interpolated multicarrier uniform filter bank is:
Figure DEST_PATH_IMAGE254
；
Figure DEST_PATH_IMAGE256
。
the total implementation complexity is:
Figure DEST_PATH_IMAGE258
；
Figure DEST_PATH_IMAGE260
。
when the traditional classical scheme is adopted, each subcarrier filter of the total bandwidth MF-TDMA is realized by RNFB polyphase, and the output is output
Figure DEST_PATH_IMAGE262
The number of sub-carriers is such that,
Figure 772392DEST_PATH_IMAGE092
the number of bands for a full band MF-TDMA frame,
Figure 38288DEST_PATH_IMAGE238
is as follows
Figure 381545DEST_PATH_IMAGE228
The number of subcarriers within a frame frequency band; each subcarrier filter is provided with
Figure DEST_PATH_IMAGE264
The input subbands are synthesized based on CMFB PR TMUX, and the classical scheme has a complexity of:
Figure DEST_PATH_IMAGE266
；
Figure DEST_PATH_IMAGE268
。
can be compared when
Figure 690124DEST_PATH_IMAGE092
Number of subcarriers averaged over a frame frequency band
Figure DEST_PATH_IMAGE270
The complexity of the present invention is much lower than the classical scheme.
The present invention is not limited to the above-described embodiments, and any obvious improvements, substitutions or modifications can be made by those skilled in the art without departing from the spirit of the present invention.

Claims (8)

1. A design method of a double-layer filter bank for DVB-RCS2 is characterized in that a first layer adopts PR TMUX based on CMFB to realize RNFB with variable time-frequency resolution between full-frequency-band MF-TDMA frames, the RNFB is realized by a multiphase structure, and a second layer adopts multiphase interpolation technology to realize multi-carrier uniform FB in the MF-TDMA frames;
the first layer design method comprises the following steps:
step 1: designing a prototype filter: the prototype filter is realized by an FIR filter structure based on FRM technology, and a plurality of wide transition band filters are used to form the prototype filter which is a narrow transition band as a whole;
step 2: determining a prototype filter according to the passband cut-off frequency, the stopband starting frequency, the passband fluctuation peak value and the stopband fluctuation peak value of the plurality of wide transition band filters used in the step 1
Figure DEST_PATH_IMAGE002
Length of (2)
Figure DEST_PATH_IMAGE004
；
And step 3: design a
Figure DEST_PATH_IMAGE006
A channel uniform-resolution FB with a prototype filter of
Figure 212155DEST_PATH_IMAGE002
The prototype filter has a length of
Figure 660453DEST_PATH_IMAGE004
The stop band cut-off frequency is
Figure DEST_PATH_IMAGE008
(ii) a Wherein,
Figure DEST_PATH_IMAGE010
representing a decimation factor, the number of channels of the analysis filter is also
Figure 67556DEST_PATH_IMAGE010
，
Figure DEST_PATH_IMAGE012
Which is indicative of a roll-off factor,
Figure DEST_PATH_IMAGE014
；
and 4, step 4: design a
Figure DEST_PATH_IMAGE016
The CMFB with uniform channel recombination has a prototype filter of
Figure DEST_PATH_IMAGE018
The prototype filter has a length of
Figure DEST_PATH_IMAGE020
The starting frequency of the stop band is
Figure DEST_PATH_IMAGE022
(ii) a Wherein,
Figure DEST_PATH_IMAGE024
representing the number of uniform recombination filter channels;
and 5: obtaining a PR TMUX based on the CMFB as
Figure DEST_PATH_IMAGE026
And is and
Figure DEST_PATH_IMAGE028
Figure DEST_PATH_IMAGE030
，
Figure DEST_PATH_IMAGE032
wherein,
Figure DEST_PATH_IMAGE034
representing an imaginary number;
Figure DEST_PATH_IMAGE036
、
Figure DEST_PATH_IMAGE038
all represent intermediate variables;
Figure DEST_PATH_IMAGE040
；
step 6: let us say the second in RNFB
Figure DEST_PATH_IMAGE042
Of a branch
Figure DEST_PATH_IMAGE044
Is sub-band at
Figure 105175DEST_PATH_IMAGE006
Starting from index numbers in a channel uniform parsing FB
Figure DEST_PATH_IMAGE046
，
Figure DEST_PATH_IMAGE048
Is even number, then
Figure 794914DEST_PATH_IMAGE042
Is branched at
Figure 899267DEST_PATH_IMAGE006
Channel uniform resolution in FB
Figure 697459DEST_PATH_IMAGE024
A sub-band can adopt
Figure 693097DEST_PATH_IMAGE016
Directly combining the channels PR TMUX synthesis filters;
Figure 638007DEST_PATH_IMAGE048
odd, the corresponding channel is multiplied by the sequence before combining the sub-bands
Figure DEST_PATH_IMAGE050
Wherein
Figure DEST_PATH_IMAGE052
indicating an input data sequence;
and 7: in that
Figure 490425DEST_PATH_IMAGE006
The channel uniformly analyzes other branches of the FB to compensate the time delay caused by inserting the TMUX;
the second layer design method comprises the following steps: the second layer implements intra-frame MF-TDMA uniform FB using typical polyphase interpolation techniques, where
Figure DEST_PATH_IMAGE054
Is as follows
Figure 323383DEST_PATH_IMAGE042
The interpolation factor and the number of sub-carriers within a frame frequency band,
Figure DEST_PATH_IMAGE056
is a prototype filter
Figure DEST_PATH_IMAGE058
Is/are as follows
Figure DEST_PATH_IMAGE060
Phase component of multiple phases, and
Figure DEST_PATH_IMAGE062
second layer prototype filter
Figure 748811DEST_PATH_IMAGE058
Has a length of
Figure DEST_PATH_IMAGE064
。
2. The method of claim 1, wherein the step 1 specifically comprises:
setting a known sampling rate factor of
Figure DEST_PATH_IMAGE066
Figure DEST_PATH_IMAGE068
，
Figure DEST_PATH_IMAGE070
Is the number of bands of a full band MF-TDMA frame, and
Figure DEST_PATH_IMAGE072
symmetric impulse response linear phase LPF mode
Filter
Figure DEST_PATH_IMAGE074
Is of odd length
Figure DEST_PATH_IMAGE076
Complementary filter thereof
Figure DEST_PATH_IMAGE078
Can be expressed as:
Figure DEST_PATH_IMAGE080
by using
Figure DEST_PATH_IMAGE082
Each delay unit in the LPF modal filter and its complementary filter is replaced by one delay to form
Figure DEST_PATH_IMAGE084
And
Figure DEST_PATH_IMAGE086
two filters, two mask filters
Figure DEST_PATH_IMAGE088
And
Figure DEST_PATH_IMAGE090
are respectively cascaded
Figure 304819DEST_PATH_IMAGE084
And
Figure 265822DEST_PATH_IMAGE086
the transfer function of the entire filter after cascading (i.e., the prototype filter) is:
Figure DEST_PATH_IMAGE092
and is
Figure DEST_PATH_IMAGE094
，
Figure DEST_PATH_IMAGE096
，
Figure DEST_PATH_IMAGE098
，
Figure DEST_PATH_IMAGE100
，
Figure DEST_PATH_IMAGE102
，
Figure DEST_PATH_IMAGE104
，
Figure DEST_PATH_IMAGE106
；
Wherein,
Figure DEST_PATH_IMAGE108
means less than
Figure DEST_PATH_IMAGE110
Of the up-sampling ratio of the LPF modal filter is
Figure 658845DEST_PATH_IMAGE082
，
Figure DEST_PATH_IMAGE112
And
Figure DEST_PATH_IMAGE114
respectively representing the passband cut-off frequency and the stopband start frequency of the prototype filter,
Figure DEST_PATH_IMAGE116
and
Figure DEST_PATH_IMAGE118
respectively representing the passband cut-off frequency and the stopband start frequency of the LPF modal filter,
Figure DEST_PATH_IMAGE120
and
Figure DEST_PATH_IMAGE122
respectively representing two mask filters
Figure 684701DEST_PATH_IMAGE088
And
Figure 610063DEST_PATH_IMAGE090
the passband cut-off frequency of (a),
Figure DEST_PATH_IMAGE124
and
Figure DEST_PATH_IMAGE126
respectively representing two mask filters
Figure 804284DEST_PATH_IMAGE088
And
Figure 815096DEST_PATH_IMAGE090
the stop band start frequency of (1).
3. The method of claim 2, wherein the masking filter is a two-layer filter bank design method for DVB-RCS2
Figure 425069DEST_PATH_IMAGE088
And
Figure 719784DEST_PATH_IMAGE090
are equal in group delay, and
Figure DEST_PATH_IMAGE128
is an even number.
4. The method of claim 1, wherein the step 2 comprises the following steps:
setting up
Figure DEST_PATH_IMAGE130
And
Figure DEST_PATH_IMAGE132
respectively, the passband fluctuation peak value and the stopband fluctuation peak value of the prototype filter, and the order of the FIR prototype filter is:
Figure DEST_PATH_IMAGE134
and (2) substituting the passband cut-off frequency and the stopband starting frequency of each sub-filter in the step (1) into an order calculation formula of the FIR prototype filter, wherein each sub-filter has the same passband and stopband fluctuation peak value as the prototype filter, and the order of each sub-filter can be calculated to determine the length of the prototype filter.
5. The method of claim 4, wherein the prototype filter is implemented using polyphase decomposition, resulting in a polyphase decomposition filter, wherein coefficients of the polyphase decomposition filter are decimated
Figure DEST_PATH_IMAGE136
If the stopband attenuation SA is to be maintained
Figure 439566DEST_PATH_IMAGE132
Then, in the order calculation formula of the FIR prototype filter, the second term on the right side is the extraction of the compensation coefficient
Figure 921363DEST_PATH_IMAGE136
The post polyphase decomposition filter stopband attenuation degrades the number of orders required to be added by the prototype filter.
6. Root of herbaceous plantThe method of claim 1, wherein in step 3,
Figure 351339DEST_PATH_IMAGE006
the prototype filter I-type polyphase decomposition of channel uniform-resolution FB is:
Figure DEST_PATH_IMAGE138
Figure DEST_PATH_IMAGE140
；
wherein,
Figure DEST_PATH_IMAGE142
representing the minimum parameter value obtained by PR constraint optimization;
Figure DEST_PATH_IMAGE144
represents a weight constant between 0 and 1;
Figure DEST_PATH_IMAGE146
and
Figure DEST_PATH_IMAGE148
are respectively as
Figure 454555DEST_PATH_IMAGE006
The channel uniformly resolves the passband cut-off frequency and the stopband cut-off frequency of the FB;
uniformly resolved FB is PR constrained:
Figure DEST_PATH_IMAGE150
wherein,
Figure DEST_PATH_IMAGE152
，
Figure DEST_PATH_IMAGE154
which represents a non-zero constant that is,
Figure DEST_PATH_IMAGE156
is a positive integer.
7. The method of claim 1, wherein in step 4,
Figure 334787DEST_PATH_IMAGE016
prototype filter of channel uniform recombination CMFB
Figure 303880DEST_PATH_IMAGE018
Optimization by PR constraints, weighting of pass band and stop band and
Figure 6387DEST_PATH_IMAGE006
the channel CMFB is the same as the channel CMFB,
Figure 275695DEST_PATH_IMAGE016
the prototype filter of the channel uniform recombination CMFB meets the matching condition:
Figure DEST_PATH_IMAGE158
。
8. the two-layer filter bank design method for DVB-RCS2 of claim 1 wherein the FIR filter complexity is measured by the number of required multiplications per unit time (MPU) and additions per unit time (APU);
the complexity of the first layer RNFB polyphase implementation is
Figure DEST_PATH_IMAGE160
And
Figure DEST_PATH_IMAGE162
；
the complexity of the implementation of the second-layer MF-TDMA intra-frame polyphase interpolating multicarrier uniform filter bank is
Figure DEST_PATH_IMAGE164
And
Figure DEST_PATH_IMAGE166
；
total implementation complexity of
Figure DEST_PATH_IMAGE168
And
Figure DEST_PATH_IMAGE170
；
wherein,
Figure 671035DEST_PATH_IMAGE070
indicating the number of bands of a full band MF-TDMA frame,
Figure DEST_PATH_IMAGE172
(ii) a MPUs denotes a plurality of multiplications per unit time and APUs denotes a plurality of additions per unit time.
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