CN113890559A - Two innovative architectures of multi-mode reconfigurable ultra-wideband integrated transceiver and transmitter - Google Patents
Two innovative architectures of multi-mode reconfigurable ultra-wideband integrated transceiver and transmitter Download PDFInfo
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/02—Transmitters
- H04B1/04—Circuits
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
- H04B1/40—Circuits
- H04B1/401—Circuits for selecting or indicating operating mode
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
- Y02D30/00—Reducing energy consumption in communication networks
- Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks
Abstract
The invention provides a multi-mode reconfigurable ultra-wideband integrated transceiver for realizing time difference ranging, frequency difference ranging, phase difference ranging and wireless communication based on a sub-module integrated technology, and provides two realizable innovative transmitter architectures. The multiplexing degree of the integrated transceiver exceeds 90%, the resolution is higher than that of the existing transceiver, and the impasse that the resolution of the traditional transceiver is low is broken. The purpose is to realize the functions of two chips of communication and radar by the area and power consumption of one chip through the common-framework integrated design of the submodules. The two innovative transmitter structures replace relaxation oscillators with simple digital modules, so that the power consumption is greatly reduced, and the reusability is high. The low-power-consumption design based on current multiplexing enables the invention to be applied to ultra-low power-consumption scenes, innovatively breaks through the advantage of low resolution of the traditional transceiver, and enables the invention to be applied to high-resolution scenes.
Description
Technical Field
The invention provides a multi-mode reconfigurable ultra-wideband integrated transceiver for realizing time difference ranging, frequency difference ranging, phase difference ranging and wireless communication based on a sub-module integrated technology, provides two realizable innovative transmitter architectures, has the advantages of low cost and low power consumption, and belongs to the technical field of wireless communication technology and radar ranging.
Background
In recent years, the ultra-wideband frequency modulation technology is widely applied in the medical field at home and abroad, the combination of medical treatment and communication is becoming more compact, and people begin to look to wireless body area networks and wireless personal networks. Wireless communication transceivers are required in systems such as wireless body area networks and wireless personal networks, and they are required to have the characteristics of low power consumption, short distance and low cost, without requiring data rate. And non-contact heart rate/respiration measurement and other electronic systems need a radar ranging transceiver with high resolution, good penetrability and low radiation. Compared with the common narrow-band technology such as Bluetooth, the ultra-wideband technology can realize lower power consumption and achieve higher ranging resolution by using a simpler transceiver architecture.
The narrow band technology is far inferior to the ultra-wideband in ranging resolution; from the perspective of transceiver architecture, power consumption and cost comparison, the ultra-wideband is superior to the narrowband; from the aspect of system integration, only the ultra-wideband technology can realize radar ranging and wireless communication simultaneously. Therefore, only ultra-wideband technology can be used to develop integrated transceiver chips. Among the existing ultra-wideband schemes, the ultra-wideband frequency modulation scheme has many advantages (no need of radio frequency synchronization, simple transceiving architecture, greatly reduced complexity of the transceiving architecture, relaxed phase noise and antenna requirement, etc.), making it a popular short-distance, low-power consumption, and low-cost technology. Considering the low power consumption, low cost and low radiation characteristics required by the human body special environment, the ultra-wideband frequency modulation technology is preferably used for constructing the communication and radar integrated transceiver, which is the technical background of the invention, and the human body environment is particularly preferred to the ultra-wideband frequency modulation wireless communication and frequency modulation continuous wave radar ranging integrated transceiver.
Disclosure of Invention
Both the ultra-wideband frequency modulation wireless communication transceiver and the frequency modulation continuous wave radar transceiver obtain ultra-wideband signals based on a radio frequency modulation technology. An ultra-wideband frequency modulated wireless communication transceiver is discussed. The transmitter adopts a dual-frequency modulation technology: simulating 2-frequency shift keying modulation and radio frequency modulation; the baseband data 0 and 1 are converted into the frequency f by analog 2-frequency shift keying modulation1And f2Is called 2-frequency shift keying triangular wave(subcarrier) generation; then, the analog triangular wave is sent to a voltage control end of a radio frequency voltage-controlled oscillator, and under the control of amplitude-frequency conversion gain of the voltage-controlled oscillator, radio frequency modulation is carried out to obtain an ultra-wideband signal, and the process is called radio frequency modulation; in order to correct the center frequency of the voltage controlled oscillator, a center frequency correction circuit is introduced. The receiver uses a dual frequency demodulation technique: broadband radio frequency modulation demodulation and frequency shift keying demodulation; the ultra-wideband signal recovers the analog frequency shift keying triangular wave information through a wideband radio frequency discriminator (slope frequency discrimination or phase frequency discrimination), and the frequency f of the demodulated analog signal is1 Represents baseband data 0, and f2Representing baseband data 1, the process is called broadband frequency modulation demodulation, and radio frequency carriers are not needed, and carrier synchronization is not needed; a subsequent frequency shift keying demodulator reconstructs the digital baseband 0 and 1 data from the recovered analog intermediate frequency shift keying triangle wave.
Frequency modulated continuous wave radar transceivers are discussed. The transmitter adopts the ultra wide band radio frequency modulation technology: under the control of the amplitude-frequency conversion gain of the voltage-controlled oscillator, or by controlling the fractional frequency division ratio of the fractional frequency division phase-locked loop, the ultra-wideband signal of which the instantaneous frequency linearly changes along with the amplitude of the triangular wave with the fixed frequency is obtained. The ranging principle of the frequency modulation continuous wave receiver is based on a radio frequency difference technology: the down mixer makes the instantaneous frequency of the local oscillator (transmitting end) frequency modulation continuous wave signal and the receiving end ultra-wideband signal (namely the transmitting end ultra-wideband signal after space transmission delay) as difference frequency, and the difference frequency is directly proportional to space transmission time (ranging distance); the subsequent processing, such as analog filters, analog-to-digital converters, and fourier transforms, is to extract the difference frequency and convert it into range data.
An existing ultra-wideband frequency-modulated wireless communication and frequency-modulated continuous wave radar ranging integrated transceiver structure is shown in fig. 1. The wireless communication part of the system is based on phase frequency discrimination (time delay multiplication structure), so that the receiver is complex to realize and high in power consumption; the radar part of the system is based on a radio frequency difference ranging mode, the ranging resolution is limited by radio frequency bandwidth, and the formula c/2BW is satisfied, wherein c is the speed of light, and BW is the radio frequency bandwidth; that is, in order to obtain a centimeter-level ranging resolution, the radio frequency bandwidth is at least 5GHz, which undoubtedly presents a great challenge to the low-power, low-cost implementation of radar transceivers.
The invention aims to realize the common-structure integrated design of the ultra-wideband frequency modulation transceiver and the frequency modulation continuous wave radar, so that the transceiver system has the functions of time difference ranging, frequency difference ranging, phase difference ranging and wireless communication, and breaks the stiff problem that the ranging resolution of the transceiver with the traditional structure is limited by the radio frequency bandwidth. Under the same bandwidth of 500MHz, the traditional transceiver reaches the resolution of decimeter level, while the integrated transceiver designed by the invention realizes the resolution of millimeter level, and adopts a method of realizing multi-module integration while achieving high resolution, thereby greatly reducing power consumption and cost, achieving the multiplexing degree of more than 90 percent, and realizing the functions of time difference ranging, frequency difference ranging, phase difference ranging and wireless communication.
The architecture of an integrated transceiver designed by the present invention is shown in fig. 2. The ultra-wideband frequency modulation transceiver provided by the invention comprises a transmitter and a receiver. The transmitter comprises modules such as a relaxation oscillator, a three-level annular voltage-controlled oscillator, a single-stage push-pull power amplifier, a successive approximation type frequency automatic correction and the like; the receiver comprises a low noise amplifier, a band-pass filter, an envelope detector and the like. The low-noise amplifier and the band-pass filter in the receiver realize a common structure design based on a radio frequency current multiplexing method, and the power consumption and the design cost of a circuit are greatly reduced.
The transmitter adopts a radio frequency voltage controlled oscillator frequency modulation and ultra wide band frequency band center frequency correction method; the receiver introduces differential slope frequency discrimination and is based on an intermediate frequency time difference ranging mechanism; therefore, the high compatibility of communication and radar is facilitated, the design complexity and the system power consumption are greatly reduced, and the ranging resolution is improved. First, the if time difference ranging mechanism converts the time delay between the receiving and transmitting of the rf ultra-wideband signal into the time delay between the receiving and transmitting of the if subcarrier signal, as shown in fig. 3, the ranging resolution is not limited by the rf bandwidth, but only by the processing accuracy of the time-to-digital converter itself, so that the resolution of millimeter level can be realized. And secondly, the radio frequency discriminator is converted into a differential slope frequency discrimination structure from a time delay multiplication or regeneration structure, so that the power consumption and the cost of a receiver are reduced, and the frequency discrimination linearity is improved.
The controlled-slew-rate relaxation oscillator generates an analog triangular wave signal with 2-frequency shift keying frequency or fixed frequency and a local oscillator intermediate frequency signal of a receiver; the low-cost and low-power consumption dual-channel annular voltage-controlled oscillator realizes radio frequency modulation; the successive approximation type automatic frequency correction loop circuit with single pole and multiple throws works intermittently corrects the central oscillation frequency of the triangular wave generator and the annular voltage-controlled oscillator simultaneously. The slope frequency discriminator based on the differential band-pass filter and the envelope detection realizes the demodulation of the ultra-wideband signal and recovers the intermediate frequency triangular wave information; a subsequent digital frequency shift keying demodulator based on energy detection recovers the transmitted baseband data or a subsequent time-to-digital converter based on intermediate frequency delay sampling decisions produces multi-bit distance data. In order to be compatible with three ranging modes of time difference, frequency difference and phase difference, a mixer is additionally added, and an off-chip Fourier transform processing module is matched to construct a frequency difference ranging mode; then, two-channel frequency difference ranging can be carried out, and a phase difference ranging mode is formed by means of a time-to-digital converter type phase discriminator.
By comparing the structures of the ultra-wideband frequency modulation wireless communication transceiver, the intermediate frequency time difference frequency modulation continuous wave radar transceiver and the radio frequency difference frequency modulation continuous wave radar transceiver, the following can be found easily: the radio frequency heavy current module (including power amplifier, low noise amplifier, radio frequency discriminator, ring voltage controlled oscillator), frequency correction loop, and middle and low frequency module (including intermediate frequency amplifier, subtracter, band gap reference source, crystal oscillator, serial peripheral interface controller, etc.) can be reused completely; even if the intermediate frequency analog triangular wave generator can be multiplexed (2-frequency shift keying frequency modulation is distinguished from fixed frequency); except for low power consumption and low cost passive mixers, only digital frequency shift keying demodulators, time-to-digital converters and fourier transforms need to be switched in parallel or cannot be multiplexed. Therefore, the proposed ultra-wideband frequency modulation wireless communication transceiver and the multi-mode frequency modulation continuous wave radar transceiver have the multiplexing degree of more than 90% in structure and circuit realization; the design of common structure integration can be carried out, and the area and the power consumption of one chip are used for realizing the functions of two chips of communication and radar.
Based on the ranging mechanism of the intermediate frequency time difference, the system gets rid of the dilemma that the ultra-wideband of the impulse radio and the traditional frequency modulation continuous wave transceiver are limited by the radio frequency bandwidth, and also gets rid of the defect that the existing high-precision (or phase difference type) frequency modulation continuous wave radar cannot realize the linear phase tracking in a wider range and the low power consumption performance, and is only limited by the precision of the time-to-digital converter, and the optimization design of the single intermediate frequency digital time-to-digital converter is simpler and more than the bandwidth expansion and power consumption optimization design of a plurality of radio frequency heavy current modules; under the same bandwidth of 500MHz, the traditional or existing type can achieve the resolution of decimeter level and the power consumption of 10mW, while the proposed type can achieve the resolution of millimeter level and the power consumption of 2mW, the resolution is improved by two orders of magnitude, and the power consumption and the cost are reduced by 5 times.
The integrated transceiver designed by the invention can realize time difference ranging and frequency difference ranging, and can realize the function of phase difference ranging by using two or more groups of integrated transceiver structures, and a phase difference ranging mode can be formed by two-channel frequency difference ranging and a time-to-digital converter type phase discriminator. Therefore, the integrated transceiver designed by the invention realizes millimeter-scale resolution, and adopts a method of realizing multi-module integration while achieving high resolution, thereby greatly reducing power consumption and cost and achieving the multiplexing degree of more than 90%. Fig. 4 is a timing diagram of the multi-mode high-reusability reconfigurable ultra-wideband integrated transceiver according to the present invention operating in a wireless communication mode, in which the transmitted data changes between 0 and 1, the frequency of the output signal of the relaxation oscillator changes, and the recovered data after demodulation by the receiver is the same as the transmitted data after a delay. Fig. 5 is a timing diagram of the multi-mode high-reusability reconfigurable ultra-wideband integrated transceiver according to the present invention operating in a ranging mode. A time delay exists between the transmitted signal and the received signal, the time delay is the propagation time delta t of the signal from the transmission to the reception in the space, and the time information can be converted into distance information through a time-to-digital converter, so that the time difference ranging function can be realized. The ultra-wideband signal transmitted by the transmitter and the ultra-wideband signal received by the receiver are sent to the frequency mixer to obtain the frequency difference, and then the frequency difference ranging function is realized through off-chip Fourier transform. The phase difference ranging mode can also be constructed by two-channel frequency difference ranging with the aid of a time-to-digital converter type phase discriminator by using two or more sets of integrated transceiver structures.
The invention also proposes an innovative transmitter architecture, as shown in fig. 6. The transmitter includes two modes, respectively: mode "1" correction and mode "2" operation. In the calibration mode, 25(6 b' 011001) is input to the numerically controlled oscillator to control the numerically controlled oscillator output frequency FVCOIs a sine wave signal of about 4GHz (the output signal fluctuates about 4GHz, and a subsequent correction module is needed to stabilize the output signal to 4 GHz), and at this time, N is1/N2Frequency divider (N)1Is 36; n is a radical of240) operating in a frequency division mode of 40, a sine wave signal of about 4GHz is frequency-divided into a square wave signal of about 100MHz by a frequency divider of 40, the square wave signal of about 100MHz is input into a frequency discriminator based on a digital counter as a high-frequency input clock of the discriminator, FREF(1MHz) as the low frequency input clock of the frequency discriminator, counting the high frequency clock in a low frequency clock, if the output frequency of the digital control oscillator is a sine wave signal less than 4GHz, FREF(1MHz) the counting result of the square wave with the frequency less than 100MHz is less than 100 (F)VCO/FREF100), if the numerically controlled oscillator outputs a sine wave signal having a frequency greater than 4GHz, F isREF(1MHz) the counting result of the square wave with the frequency of more than 100MHz is more than 100 (F)VCO/FREF100). Since the counter outputs the equivalent result of about 100, and due to the influence of temperature, process and power supply voltage, the frequency of the oscillator fluctuates by 20% -30%, FVCO/FREFThe result is a fluctuation of 20-30% on a 100 basis, and the counter needs to be set aside for a certain margin to achieve frequency discrimination even in case of fluctuation, so that an 8-bit counter is needed. The UP/DN signal is controlled by a discriminator comparing the output result of the 8-bit counter with the discriminator built-in 100The 6-bit output of the digital successive approximation register is controlled in one step, so that the aim of correcting the frequency of the digital controlled oscillator to be stabilized at 4GHz is fulfilled. The operating modes of the integrated transceiver are in turn divided into radar and communication operating modes according to the specific functions that it is intended to implement. In the radar operation mode, the 6-bit digital up-down counter is increased from 0 to 50 and decreased from 50 to 0, the trapezoidal wave generator generates a 6-bit output, which is equivalent to a trapezoidal wave form with a frequency of 1MHz (100MHz/1MHz is 100, and 100/2 is 50, so that a 6-bit counter is needed to generate a trapezoidal wave with a frequency of 1MHz), and at this time, N is a counter with a bit number of N1/N2Frequency divider (N)1Is 36; n is a radical of240) is operated in a frequency division 40 mode, and the output signal of the oscillator with the center frequency of 4GHz is divided into clock signals with the frequency jittering around 100MHz to control a trapezoidal wave generator based on a digital two-way counter. The 6-bit output of the trapezoidal wave generator controls the oscillator to generate a sine wave with a center frequency of 4GHz and a frequency varying between 3.75GHz and 4.25GHz (the frequency of the sine wave signal is kept constant by the fixed frequency of the trapezoidal wave generator). The output signal of the digital control oscillator is transmitted out through the push-pull type power amplifier and the antenna, and the ranging function is finally realized through a series of subsequent processing, and the multi-mode functions of time difference ranging, frequency difference ranging and phase difference ranging can be realized. In the communication working mode, when the transmission data is 0, N1/N2Frequency divider (N)1Is 36; n is a radical of240) is operated in a frequency division 40 mode, and the output signal of the oscillator with the center frequency of 4GHz is divided into clock signals with the frequency jittering around 100MHz to control a trapezoidal wave generator based on a digital two-way counter. The 6-bit digital bidirectional counter is increased from 0 to 50 and decreased from 50 to 0, the trapezoidal wave generator generates a 6-bit output, and the output is equivalent to a trapezoidal wave form with the frequency of 1 MHz; when the transmission data is 1, N1/N2Frequency divider (N)1Is 36; n is a radical of240) is operated in a frequency division 36 mode, the oscillator output signal with a center frequency of 4GHz is divided into clock signals with a frequency jittering around 110MHz to control a digital up-down counter based trapezoidal wave generator. 6 bit digital bi-directionalThe counter is self-increased from 0 to 50 and self-decreased from 50 to 0, and the trapezoidal wave generator generates a 6-bit output, which is equivalent to a trapezoidal wave form with the frequency of 1.1 MHz. In summary, in the communication operation mode, the trapezoidal wave generator based on the digital bidirectional counter generates a 6-bit output, which is equivalent to a trapezoidal wave form with a frequency switching back and forth between 1MHz and 1.1MHz, and the 6-bit output of the trapezoidal wave generator controls the oscillator to generate a sine wave with a center frequency of 4GHz and a frequency varying between 3.75GHz and 4.25GHz (the frequency of the sine wave signal varies under the influence of the variation frequency of the trapezoidal wave generator). Finally, the output signal of the digital control oscillator is transmitted out through a push-pull type power amplifier and an antenna, and then the output signal is received by a receiver to finally realize the communication function.
The invention provides an innovative transmitter architecture and also provides an innovative transmitter architecture with high multiplexing degree on the basis of the innovative transmitter architecture. Fig. 7 shows a highly multiplexed transmitter architecture. It is evident from fig. 6 that there are two digital counters which we can multiplex into the structure shown in fig. 7. An 8-bit one-way and two-way selectable digital counter is designed, and 8-bit one-way counting is selected to form a frequency discriminator in the mode of '1'; selecting 6-bit bidirectional count in mode "2" constitutes a trapezoidal wave generator. Therefore, the relaxation oscillator is saved, and the counter is multiplexed, so that the system architecture is further simplified, and the power consumption and the design cost of the circuit are reduced.
The digital modules used by the two innovative transmitters are very simple digital modules, so that the design cost, the circuit power consumption and the architecture complexity are greatly reduced, and are not repeated herein. A detailed circuit description is given of the rf module (a digitally controlled oscillator and a single-stage push-pull type power amplifier).
Fig. 8 is a circuit diagram of a digitally controlled oscillator in the inventive transmitter architecture proposed by the present invention. As shown in FIG. 8, transistor M1-M6The three-level inverter is formed as a core of an oscillator, allowing for ultra-wideThe three-level cascade oscillator structure is favorable for generating larger oscillation frequency, smaller power consumption and better phase noise. Discrete controllable current (I) with total resonant current provided by binary switch current arrayM7) And a discrete controllable current (I) provided by a binary switched current arrayM10) Are formed together. The oscillation frequency of the digitally controlled oscillator is doubly tuned by the multi-bit correction data and the multi-bit modulation data at the same time, where C<5:0>Correcting the control word for 6 bits, T<5:0>The control word is modulated for 6 bits. In summary, the digitally controlled oscillator not only realizes rf frequency modulation, but also realizes center frequency correction through the binary-weighted switch current array and the successive approximation type frequency auto-calibration module. Wherein the successive approximation type frequency automatic calibration module corrects the control word C by 6 bits<5:0>The binary weighted current array output of the digital control oscillator is controlled, the output frequency of the oscillator is reversely adjusted, and the correction of the central frequency of the digital control oscillator is realized. In the process of correction and operation of the loop, the two modes of the correction mode "1" and the operation mode "2" are cyclically alternated, that is, the digital control type oscillator firstly performs the correction of the central frequency in a short time, then performs the modulation in a long time, and then performs the correction of the central frequency again, and the operation is repeated continuously.
Correction current I of the digitally controlled oscillator core after the correction of the center frequency is completedM7Then fix that the total oscillation current only depends on the modulation current IM10And (4) changing. Matched current mirror (M)7、M8、M9、M10) Design, and symmetrical charge and discharge capability of digitally controlled oscillator core (reasonable selection of M)1、M3、M5And M2、M4、M6The size ratio) ensures the tuning linearity of the numerically controlled oscillator.
The output of the digital control oscillator is sent to a frequency mixer at a receiving end as a radio frequency local oscillator on one hand, and is sent to a single-stage push-pull type power amplifier through an isolation inverter on the other hand. FIG. 9 is a drawing of the present inventionThe circuit diagram of a single-stage push-pull type power amplifier in the inventive transmitter architecture. As shown in fig. 9, the output of the digitally controlled oscillator passes through a coupling capacitor C1、C2Input to push-pull tube M1、M2Of the transistor M1、M2The push-pull tubes jointly form a push-pull amplifier stage power amplifier, and the bias voltage is formed by a transistor M3、M4、M6、M7The low-voltage current mirror is formed. The low-voltage current mirror reduces the requirement for external current and can also provide higher bias voltage. The power amplifier is connected with two stages of matching networks in the rear, and the first stage of parasitic inductance capacitance L-shaped matching network (L)1And C4) And a second stage off-chip tunable L-shaped matching network (L)2And C5) And the broadband frequency-selective amplification is realized together. Wherein the inductance L1The inductor and the capacitor C are carried by the chip binding line4The capacitor and inductor L carried by the chip bonding pad2Capacitor C5Capacitor C3Are off-chip inductors and capacitors.
The two innovative transmitter architectures provided by the invention only use two radio frequency modules, namely a digital control oscillator and a push-pull power amplifier, and the rest are digital modules with very simple structures and very low power consumption. The innovative transmitter architecture provided by the invention greatly saves the design cost and the circuit power consumption, reduces the complexity of the architecture, and provides the architecture for multiplexing the counter, thereby greatly improving the multiplexing degree of the whole architecture. In subsequent optimization design, stacking a digital control type oscillator and a push-pull type power amplifier between a power supply and the ground by using a radio frequency current multiplexing technology can be considered, so that the power consumption is further reduced.
Advantageous effects
Compared with the existing transceiver architecture and transmitter architecture, the two innovative architectures of the multi-mode reconfigurable ultra-wideband integrated transceiver and transmitter provided by the invention have the following beneficial effects:
1. the multi-mode high-reusability reconfigurable ultra-wideband integrated transceiver can greatly reduce power consumption. A plurality of modules including a low noise amplifier and a band-pass filter can realize common structure design through a radio frequency current multiplexing technology, and the design requirement of ultra-low power consumption is met;
2. the multi-mode high-reusability reconfigurable ultra-wideband integrated transceiver provides an intermediate frequency time difference ranging mechanism, compared with the existing radio frequency time difference and radio frequency difference mode, the ranging resolution is improved by 2 orders of magnitude, and compared with the existing radio frequency phase difference mode, the power consumption and the cost are obviously reduced;
3. the multi-mode high-reusability reconfigurable ultra-wideband integrated transceiver provided by the invention has multiple functions, can realize multi-mode use of time difference ranging, frequency difference ranging, phase difference ranging and wireless communication, and the reusability of the whole system architecture exceeds 90%;
4. the invention also provides two innovative transmitter structures, one innovative transmitter does not need to use a relaxation oscillator but uses a digital bidirectional counter for replacement, so that the power consumption and the design cost are greatly saved, the structure is very simple, the digital bidirectional counter can be reused with the digital counter in the successive approximation type frequency automatic calibration module, and the invention also provides a highly-multiplexed innovative transmitter, so that the power consumption and the cost are further saved, and the reuse degree of a system architecture is greatly improved. The integration of the transmitter architecture into a transceiver can have all the above advantages: the multi-mode use of time difference ranging, frequency difference ranging, phase difference ranging and wireless communication is realized, the stiff of low resolution of the traditional transceiver is broken, and the transceiver has ultra-low power consumption and ultra-high multiplexing degree.
Drawings
FIG. 1 is a diagram of an existing ultra-wideband frequency modulated wireless communication and frequency modulated continuous wave radar ranging integrated transceiver architecture;
fig. 2 is a block diagram of a multi-mode high-reusability reconfigurable ultra-wideband integrated transceiver according to the present invention;
fig. 3 is a schematic diagram of the transceiver of the present invention using the if time difference ranging mechanism to convert the time delay between the receiving and transmitting of the rf ultra-wideband signal into the time delay between the receiving and transmitting of the if subcarrier signal, thereby breaking the problem that the ranging resolution of the conventional transceiver is limited by the rf bandwidth stiffness;
FIG. 4 is a timing diagram of a multi-mode, high-reuse, reconfigurable ultra-wideband integrated transceiver of the present invention operating in a wireless communication mode;
FIG. 5 is a timing diagram of a multimode, high-reusability, reconfigurable ultra-wideband integrated transceiver according to the present invention operating in a ranging mode;
figure 6 is an innovative transmitter architecture proposed based on a multi-mode high-reuse reconfigurable ultra-wideband integrated transceiver;
fig. 7 is a highly multiplexed new transmitter architecture based on a multi-mode highly multiplexed reconfigurable ultra-wideband integrated transceiver;
fig. 8 is a circuit layout diagram of a digitally controlled oscillator in the inventive transmitter architecture proposed in the present invention;
fig. 9 is a circuit layout diagram of a single-stage push-pull type power amplifier in the inventive transmitter architecture proposed in the present invention.
Detailed Description
The following describes in detail each module of the innovative architecture of a multimode reconfigurable ultra-wideband integrated transceiver and transmitter proposed by the present invention with reference to the architecture diagram, circuit diagram and timing diagram, and further explains the working process of the rf front-end module of the innovative transmitter.
The ultra-wideband frequency modulation transceiver provided by the invention comprises a transmitter and a receiver. The transmitter comprises modules such as a relaxation oscillator, a three-level ring radio frequency oscillator, a single-stage push-pull type power amplifier, a successive approximation type frequency automatic correction and the like; the receiver comprises a low noise amplifier, a band-pass filter, an envelope detector and the like. The low-noise amplifier and the band-pass filter in the receiver realize a common structure design based on a radio frequency current multiplexing method, and the power consumption and the design cost of a circuit are greatly reduced. The transmitter adopts a radio frequency voltage controlled oscillator frequency modulation and ultra wide band frequency band center frequency correction method; the receiver introduces differential slope frequency discrimination and is based on an intermediate frequency time difference ranging mechanism; therefore, the high compatibility of communication and radar is facilitated, the design complexity and the system power consumption are greatly reduced, and the ranging resolution is improved. Firstly, the intermediate frequency time difference ranging mechanism converts the time delay between the receiving and sending of the radio frequency ultra-wideband signal into the time delay between the receiving and sending of the intermediate frequency subcarrier signal, and the ranging resolution is not limited by the radio frequency bandwidth any more, but only by the processing precision of the time-to-digital converter, so that the millimeter-level resolution can be realized. And secondly, the radio frequency discriminator is converted into a differential slope frequency discrimination structure from a time delay multiplication or regeneration structure, so that the power consumption and the cost of a receiver are reduced, and the frequency discrimination linearity is improved.
The invention also provides an innovative transmitter architecture, which adopts a digital counter to replace a relaxation oscillator, thereby greatly reducing the power consumption. And the multi-mode functions of time difference ranging, frequency difference ranging, phase difference ranging and wireless communication can be realized by integrating the functions into a transceiver framework. And on the basis, an innovative transmitter architecture of a high multiplexing type is also provided. An 8-bit single-direction and two-direction selectable digital counter is designed, and 8-bit one-direction counting is selected to form a frequency discriminator in the mode of 1; selecting 6-bit bidirectional count in mode "2" constitutes a trapezoidal wave generator. Therefore, the relaxation oscillator is saved, and the counter is multiplexed, so that the system architecture is further simplified, and the power consumption and the design cost of the circuit are reduced.
The invention provides an innovative method for ultra wide band radio frequency stacking of an oscillator and a power amplifier based on a radio frequency current multiplexing technology. Transistor M1-M6The formed three-level inverter is used as the core of the oscillator, and the three-level cascade oscillator structure is favorable for generating larger oscillation frequency, smaller power consumption and better phase noise in consideration of the requirements of the ultra-wideband frequency modulation system on low power consumption, high radio frequency and low noise. The total resonant current is composed of the modulation current and the correction. The oscillation frequency of the oscillator is subjected to double tuning of the correction data and the modulation data at the same time, so that the oscillator realizes not only radio frequency modulation but also center frequency correction. The output of the oscillator is sent to a frequency mixer at a receiving end as a radio frequency local oscillator on one hand, and is sent to a single-stage push-pull type power amplifier through an isolation phase inverter on the other hand.
The setting of the operating mode of the rf front-end module of the innovative transmitter according to the present invention, in particular in this embodiment, comprises the following steps:
step A: the power supply and signal connection method specifically comprises the following substeps:
step A.1, setting the voltage of a direct current power supply, setting the direct current bias current and setting an input control word. As shown in fig. 8 and 9, first, the power supply voltage V and the bias current are set according to the process variation at the time of chip manufacturing, and the power supply voltage V is set at the standard case (process angle tt, temperature 27 °)DDSet to direct current 1.4V and bias current IBSet to direct current 5 muA. In the correction mode, the current control word C is switched<5:0>Controlling the correction current; in modulation mode, the current control word T is switched<5:0>Controlling the modulation current, at which time the control word C is corrected<5:0>Is in a latched state. The current flowing through the oscillator is determined by the modulation current and the correction current;
step a.2 impedance matching network setup. Wherein, the antenna A1The impedance is generally 50 omega, and the capacitance C in the invention4Set to 90fF, capacitance C5Set to 0.33pF, capacitance C3Set to 2.6pF, inductance L1Set as 2nH and inductance L2The setting was 2.6 nH.
And B: each module starts to work normally, and the specific working process comprises the following substeps:
and B.1, operating the digital control type oscillator. The current flowing through the oscillator is determined by the modulation current and the correction current, and the change of the current can cause the delay change of the inverter, thereby determining the change of the frequency of the oscillator. In the correction mode, the control word T<5:0>Set to 25(6 b' 011001), signal T is applied<5:0>Inputting the signal into a digital control type oscillator to control the output frequency F of the oscillatorVCOThe sine wave signal is a sine wave signal of about 4GHz (the output signal can fluctuate at about 4GHz, and a subsequent correction module is needed only for stabilizing the output signal at 4 GHz), and under the radar working mode, the 6-bit output of the trapezoidal wave generator controls the oscillator to generate a sine wave with the center frequency of 4GHz and the frequency varying between 3.75GHz and 4.25GHz (the frequency of the sine wave signal is kept unchanged under the influence of the fixed frequency of the trapezoidal wave generator); in the mode of operation of the communication system,a 6-bit output control oscillator of the trapezoidal wave generator generates a sine wave with a center frequency of 4GHz and a frequency varying between 3.75GHz and 4.25GHz (the frequency of the sine wave signal varies under the influence of the varying frequency of the trapezoidal wave generator);
and B.2, operating the single-stage push-pull type power amplifier. The output signal of the digital control type oscillator is input into a power amplifier, and the specific working mode of the power amplifier is as follows: in the first half period of the signal, the NMOS transistor M1Is conducted at the moment when the PMOS tube M2Is a load tube. In the lower half period of the signal, the PMOS transistor M2Conducting at this time NMOS tube M1Is a load tube. L-shaped matching network (L) of first-stage parasitic inductance and capacitance connected in back1And C4) And a second stage off-chip tunable L-shaped matching network (L)2And C5) And the broadband frequency-selective amplification is realized together. And finally, the radio-frequency signal output by the power amplifier is transmitted through the antenna, and the radio-frequency modulation work of the transmitter is completed. The power amplifier can carry out power amplification on the output signal of the oscillator, which is beneficial to the propagation in the space of the signal and is beneficial to a receiver to better identify the signal.
While the foregoing is directed to the preferred embodiment of the present invention, it is not intended that the invention be limited to the embodiment and the drawings disclosed herein. Equivalents and modifications may be made without departing from the spirit of the disclosure, which is to be considered as within the scope of the invention.
Claims (7)
1. The multi-mode reconfigurable ultra-wideband integrated transceiver realizes time difference ranging, frequency difference ranging, phase difference ranging and wireless communication based on a sub-module integrated technology, and achieves the multiplexing degree of more than 90%. The ultra-wideband frequency modulation transceiver provided by the invention comprises a transmitter and a receiver. The transmitter comprises modules such as a relaxation oscillator, a three-level annular voltage-controlled oscillator, a single-stage push-pull power amplifier, a successive approximation type frequency automatic correction and the like; the receiver comprises a low noise amplifier, a band-pass filter, an envelope detector and the like. The low-noise amplifier and the band-pass filter in the receiver realize a common structure design based on a radio frequency current multiplexing method, and the power consumption and the design cost of a circuit are greatly reduced.
The transmitter adopts a radio frequency voltage controlled oscillator frequency modulation and ultra wide band frequency band center frequency correction method; the receiver introduces differential slope frequency discrimination and is based on an intermediate frequency time difference ranging mechanism; therefore, the high compatibility of communication and radar is facilitated, the design complexity and the system power consumption are greatly reduced, and the ranging resolution is improved. Firstly, the intermediate frequency time difference ranging mechanism converts the time delay between the receiving and sending of the radio frequency ultra-wideband signal into the time delay between the receiving and sending of the intermediate frequency subcarrier signal, and the ranging resolution is not limited by the radio frequency bandwidth any more, but only by the processing precision of the time-to-digital converter, so that the millimeter-level resolution can be realized. And secondly, the radio frequency discriminator is converted into a differential slope frequency discrimination structure from a time delay multiplication or regeneration structure, so that the power consumption and the cost of a receiver are reduced, and the frequency discrimination linearity is improved.
The controlled-slew-rate relaxation oscillator generates an analog triangular wave signal with 2-frequency shift keying frequency or fixed frequency and a local oscillator intermediate frequency signal of a receiver; the low-cost and low-power consumption dual-channel annular voltage-controlled oscillator realizes radio frequency modulation; the successive approximation type automatic frequency correction loop circuit with single pole and multiple throws works intermittently corrects the central oscillation frequency of the triangular wave generator and the annular voltage-controlled oscillator simultaneously. The slope frequency discriminator based on the differential band-pass filter and the envelope detection realizes the demodulation of the ultra-wideband signal and recovers the intermediate frequency triangular wave information; a subsequent digital frequency shift keying demodulator based on energy detection recovers the transmitted baseband data or a subsequent time-to-digital converter based on intermediate frequency delay sampling decisions produces multi-bit distance data. In order to be compatible with three ranging modes of time difference, frequency difference and phase difference, a mixer is additionally added, and an off-chip Fourier transform processing module is matched to construct a frequency difference ranging mode; then, two-channel frequency difference ranging can be carried out, and a phase difference ranging mode is formed by means of a time-to-digital converter type phase discriminator.
Based on the ranging mechanism of the intermediate frequency time difference, the system gets rid of the dilemma that the ultra-wideband of the impulse radio and the traditional frequency modulation continuous wave transceiver are limited by the radio frequency bandwidth, and also gets rid of the defect that the existing high-precision (or phase difference type) frequency modulation continuous wave radar cannot realize the linear phase tracking in a wider range and the low power consumption performance, and is only limited by the precision of the time-to-digital converter, and the optimization design of the single intermediate frequency digital time-to-digital converter is simpler and more than the bandwidth expansion and power consumption optimization design of a plurality of radio frequency heavy current modules; under the same 500MHz bandwidth, the traditional or existing type can reach the decimeter resolution and 10mW power consumption, but the multi-mode reconfigurable ultra-wideband integrated transceiver provided by the invention can realize the millimeter resolution and 2mW power consumption, the resolution is improved by two orders of magnitude, and the power consumption and the cost are reduced by 5 times.
2. The multimode reconfigurable ultra-wideband integrated transceiver of claim 1, wherein: the power consumption is greatly reduced. The low-noise amplifier and the band-pass filter can realize common structure design through a radio frequency current multiplexing technology, and the design requirement of ultra-low power consumption is met. And the multimode use of time difference ranging, frequency difference ranging, phase difference ranging and wireless communication can be realized based on the submodule integrated technology, and the multiplexing degree of the whole system architecture exceeds 90%.
3. The multimode reconfigurable ultra-wideband integrated transceiver of claim 1, wherein: the intermediate frequency time difference ranging mechanism is provided, compared with the existing radio frequency time difference and radio frequency difference mode, the ranging resolution is improved by two orders of magnitude, the stiff problem that the resolution of the traditional transceiver is low is broken, and compared with the existing radio frequency difference mode, the power consumption and the cost are obviously reduced.
4. The invention also provides an innovative transmitter architecture. The transmitter includes two modes, respectively: mode "1" correction and mode "2" operation. In the calibration mode, 25(6 b' 011001) is input to the digitally controlled oscillator, which is controlled to output a sine wave signal having a frequency of about 4GHz (the output signal fluctuates about 4GHz, and the calibration module is required to stabilize the output signal to 4 GHz), where N is1/N2Frequency divider (N)1Is 36; n is a radical of240) operating in a divide-by-40 mode, the sine wave signal is divided by a divide-by-40 dividerInputting the square wave signal with the frequency of about 100MHz into a frequency discriminator based on a digital counter as a high-frequency input clock of the discriminator, FREF(1MHz) as the low frequency input clock of the frequency discriminator, counting the high frequency clock in a low frequency clock, if the output frequency of the digital control oscillator is a sine wave signal less than 4GHz, FREFThe result of counting square waves with the frequency of less than 100MHz is less than 100 (F)VCO/FREF100), if the numerically controlled oscillator outputs a sine wave signal having a frequency greater than 4GHz, F isREFThe result of counting square waves with the frequency of more than 100MHz is more than 100. The frequency of the oscillator will fluctuate by 20-30% due to the influence of temperature, process, supply voltage, FVCO/FREFThe result is a fluctuation of 20-30% on a 100 basis, and the counter needs to be set aside for a certain margin to achieve frequency discrimination even in case of fluctuation, so that an 8-bit counter is needed. The UP/DN signal is controlled by the frequency discriminator which compares the output result of the 8-bit counter with the built-in 100 of the frequency discriminator, and the 6-bit output of the digital successive approximation register is further controlled, so that the aim of correcting the frequency of the digital controlled oscillator to be stabilized at 4GHz is achieved. The operating modes of the integrated transceiver are in turn divided into radar and communication operating modes according to the specific functions that it is intended to implement. In the radar operation mode, the 6-bit digital up-down counter is increased from 0 to 50 and decreased from 50 to 0, the trapezoidal wave generator generates a 6-bit output, which is equivalent to a trapezoidal wave form with a frequency of 1MHz (100MHz/1MHz is 100, and 100/2 is 50, so that a 6-bit counter is needed to generate a trapezoidal wave with a frequency of 1MHz), and at this time, N is a counter with a bit number of N1/N2The frequency divider works in a frequency division mode of 40, and divides an output signal of the oscillator with the center frequency of 4GHz into a clock signal with the frequency jittering around 100MHz to control the trapezoidal wave generator based on the digital two-way counter. The 6-bit output of the trapezoidal wave generator controls the oscillator to generate a sine wave with a center frequency of 4GHz and a frequency varying between 3.75GHz and 4.25GHz (the frequency of the sine wave signal is kept constant by the fixed frequency of the trapezoidal wave generator). OscillatorThe output signal is transmitted out through the push-pull type power amplifier and then through the antenna, the ranging function is finally realized through a series of subsequent processing, and the multimode functions of time difference ranging, frequency difference ranging and phase difference ranging can be realized. In the communication operation mode, when the transmission data is 0, the frequency divider operates in a frequency division 40 mode, and divides the oscillator output signal with the center frequency of 4GHz into clock signals with the frequency jittering around 100MHz to control the trapezoidal wave generator based on the digital up-down counter. The 6-bit digital bidirectional counter is increased from 0 to 50 and decreased from 50 to 0, the trapezoidal wave generator generates a 6-bit output, and the output is equivalent to a trapezoidal wave form with the frequency of 1 MHz; when the transmission data is 1, the frequency divider works in a 36-frequency division mode, and divides an oscillator output signal with the center frequency of 4GHz into clock signals with the frequency jittering around 110MHz to control the trapezoidal wave generator based on the digital two-way counter. The 6-bit digital up-down counter is self-increased from 0 to 50 and self-decreased from 50 to 0, and the trapezoidal wave generator generates a 6-bit output, which is equivalent to a trapezoidal wave form with the frequency of 1.1 MHz. In summary, in the communication operation mode, the trapezoidal wave generator based on the digital bidirectional counter generates a 6-bit output, which is equivalent to a trapezoidal wave form with a frequency switching back and forth between 1MHz and 1.1MHz, and the 6-bit output of the trapezoidal wave generator controls the oscillator to generate a sine wave with a center frequency of 4GHz and a frequency varying between 3.75GHz and 4.25GHz (the frequency of the sine wave signal varies under the influence of the variation frequency of the trapezoidal wave generator). Finally, the output signal of the digital control oscillator is transmitted out through a push-pull type power amplifier and an antenna, and then the output signal is received by a receiver to finally realize the communication function.
The invention also provides a highly multiplexed innovative transmitter architecture on the basis of the above. The two digital counters may be multiplexed. An 8-bit one-way and two-way selectable digital counter is designed, and 8-bit one-way counting is selected to form a frequency discriminator in the mode of '1'; selecting 6-bit bidirectional count in mode "2" constitutes a trapezoidal wave generator. Therefore, the relaxation oscillator is saved, and the counter is multiplexed, so that the system architecture is further simplified, and the power consumption and the design cost of the circuit are reduced.
5. The radio frequency front end of the innovative transmitter is characterized in that: a digital control oscillator and a single-stage push-pull power amplifier;
the operating mode setting of the radio frequency front end of the inventive transmitter specifically comprises the following steps:
the method comprises the following steps: the power supply and signal connection method specifically comprises the following substeps:
step 1.1, setting the voltage of a direct current power supply, setting a direct current bias current and setting an input control word. First, the supply voltage and the bias current are set according to the process deviation during the chip manufacturing, and the supply voltage V is set under the standard condition (process angle tt, temperature 27 deg.)DDSet to direct current 1.4V and bias current IBSet to direct current 5 muA. In the correction mode, the current control word C is switched<5:0>Controlling the correction current; in modulation mode, the current control word T is switched<5:0>Controlling the modulation current, at which time the control word C is corrected<5:0>Is in a latched state. The current flowing through the oscillator is determined by the modulation current and the correction current;
step 1.2 impedance matching network setup. Wherein, the antenna A1The impedance is generally 50 omega, and the capacitance C in the invention4Set to 90fF, capacitance C5Set to 0.33pF, capacitance C3Set to 2.6pF, inductance L1Set as 2nH and inductance L2The setting was 2.6 nH.
Step two: each module starts to work normally, and the specific working process comprises the following substeps:
and 2.1, operating the digital control type oscillator. The current flowing through the oscillator is determined by the modulation current and the correction current, and the change of the current can cause the delay change of the inverter, thereby determining the change of the frequency of the oscillator. In the correction mode, the control word T<5:0>Set to 25(6 b' 011001), signal T is applied<5:0>Inputting the signal into a digital control type oscillator to control the output frequency F of the oscillatorVCOIs a sine wave signal of about 4GHz (the output signal fluctuates about 4GHz, and a subsequent correction module is needed to stabilize the output signal to 4 GHz),in a radar working mode, a 6-bit output control oscillator of a trapezoidal wave generator generates a sine wave with the center frequency of 4GHz and the frequency of the sine wave is changed between 3.75GHz and 4.25GHz (the frequency of a sine wave signal is kept unchanged under the influence of the fixed frequency of the trapezoidal wave generator); in a communication working mode, a 6-bit output control oscillator of a trapezoidal wave generator generates a sine wave with the center frequency of 4GHz and the frequency of 3.75GHz and 4.25GHz (the frequency of a sine wave signal changes under the influence of the change frequency of the trapezoidal wave generator);
step 2.2 the single stage push-pull power amplifier operates. The output signal of the digital control type oscillator is input into a power amplifier, and the specific working mode of the power amplifier is as follows: in the first half period of the signal, the NMOS transistor M1Is conducted at the moment when the PMOS tube M2Is a load tube. In the lower half period of the signal, the PMOS transistor M2Conducting at this time NMOS tube M1Is a load tube. L-shaped matching network (L) of first-stage parasitic inductance and capacitance connected in back1And C4) And a second stage off-chip tunable L-shaped matching network (L)2And C5) And the broadband frequency-selective amplification is realized together. And finally, the radio-frequency signal output by the power amplifier is transmitted through the antenna, and the radio-frequency modulation work of the transmitter is completed. The power amplifier can carry out power amplification on the output signal of the oscillator, which is beneficial to the propagation in the space of the signal and is beneficial to a receiver to better identify the signal.
6. The radio frequency front end of the inventive transmitter of claim 5, characterized in that: transistor M1-M6The formed three-level inverter is used as the core of the oscillator, and the three-level cascade oscillator structure is favorable for generating larger oscillation frequency, smaller power consumption and better phase noise in consideration of the requirements of the ultra-wideband frequency modulation system on low power consumption, high radio frequency and low noise. Discrete controllable current (I) with total resonant current provided by binary switch current arrayM7) And a discrete controllable current (I) provided by a binary switched current arrayM10) Are formed together. The oscillation frequency of the digitally controlled oscillator is subjected to both multi-bit correction data and multi-bit modulationDouble tuning of data, wherein C<5:0>Correcting the control word for 6 bits, T<5:0>The control word is modulated for 6 bits. In summary, the digitally controlled oscillator not only realizes rf frequency modulation, but also realizes center frequency correction through the binary-weighted switch current array and the successive approximation type frequency auto-calibration module. Wherein the successive approximation type frequency automatic calibration module corrects the control word C by 6 bits<5:0>The binary weighted current array output of the digital control oscillator is controlled, the output frequency of the oscillator is reversely adjusted, and the correction of the central frequency of the digital control oscillator is realized. The two modes of the correction mode "1" and the working mode "2" are cyclically alternated, namely, the center frequency correction is carried out on the digital control type oscillator in a short time, then the modulation is carried out in a long time, then the center frequency correction is carried out again, and the steps are repeated continuously.
7. The radio frequency front end of the inventive transmitter of claim 5, characterized in that: correction current I of the digitally controlled oscillator core after the correction of the center frequency is completedM7Then fix that the total oscillation current only depends on the modulation current IM10And (4) changing. Matched current mirror (M)7、M8、M9、M10) And the design and the symmetrical charge and discharge capacity of the core of the digital control type oscillator ensure the tuning linearity of the digital control type oscillator.
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