CN113765393B - DAB converter current mode modulation method - Google Patents
DAB converter current mode modulation method Download PDFInfo
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- CN113765393B CN113765393B CN202110902593.0A CN202110902593A CN113765393B CN 113765393 B CN113765393 B CN 113765393B CN 202110902593 A CN202110902593 A CN 202110902593A CN 113765393 B CN113765393 B CN 113765393B
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- 238000013178 mathematical model Methods 0.000 claims abstract description 8
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- 239000003990 capacitor Substances 0.000 claims description 4
- 230000006698 induction Effects 0.000 abstract 1
- 238000010586 diagram Methods 0.000 description 8
- 238000005457 optimization Methods 0.000 description 6
- 230000002457 bidirectional effect Effects 0.000 description 5
- 230000001276 controlling effect Effects 0.000 description 5
- 230000004044 response Effects 0.000 description 5
- 230000009977 dual effect Effects 0.000 description 3
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33584—Bidirectional converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
- Rectifiers (AREA)
Abstract
The invention discloses a current mode modulation method of a DAB converter, which takes an inductance current equation as a starting point, establishes a relation between a current instruction and an actual phase shift ratio, obtains a switching state under different current instructions, and realizes phase shift between primary and secondary sides of the converter by the current instruction; then, establishing a dynamic mathematical model of the converter to obtain a control output transfer function in a current mode; finally, a discrete controller is designed to realize an inductance current tracking current instruction, and the control of output voltage is realized through current modulation, adjustment and phase shift. The invention provides a simple and effective current mode modulation method for the DAB converter, can carry out current mode modulation on the DAB converter under phase shift control, effectively reduces the induction current stress during starting, can provide a week-by-week current limiting protection function, and has higher reliability.
Description
Technical Field
The invention relates to the technical field of power electronics, in particular to a current mode modulation method of a DAB converter.
Background
In the fields of distributed power generation, electric automobiles, UPS (Uninterruptible Power Supply) uninterruptible power supplies, SST (Solid State Transformer) solid-state transformers and the like, the switch converter with the isolated bidirectional working capacity has wide prospect, the transmission power level of the isolated bidirectional DC-DC converter is proportional to the number of switches, and the DAB (Dual Active Bridge) bidirectional active bridge with eight switches has the advantages of symmetrical structure, bidirectional energy circulation, easiness in realizing soft switches and the like, and is widely studied.
The main research content of the current bidirectional active bridge DAB (Dual Active Bridge, DAB) is to optimize the efficiency, including current stress optimization, reactive power backflow optimization, loss optimization for analyzing ZVS (Zero Voltage Swicth) characteristics, and the like, and the optimization strategies are based on DPS (Dual Phase Shift), EPS (Extend Phase Shift extended Phase Shift) and TPS (Triple Phase Shift triple Phase Shift) control methods, so that the converter is controlled and optimized by calculating the required internal and external Phase Shift ratio. The method is mainly characterized in that an optimization strategy algorithm is adopted to calculate the internal shift ratio of the primary and secondary side H bridges to perform target optimization, and a controller is adopted to calculate the external shift ratio to perform output control. Because most DAB converters are in a constant-voltage output working state, no additional filter inductor is needed after secondary side rectification, and therefore output voltage single closed-loop feedback control is adopted in most cases. The single voltage loop has poor anti-interference capability when in operation, the disturbance of the primary side of the converter can be regulated after waiting for the change of the output side, the dynamic response speed is low, the inductance current of the converter is large when the converter is started, and the requirement on the stress of a device is high.
In general, there is a need for a current mode modulation method that further optimizes the DAB converter. Conventional switching converter current loops typically employ ACM (Average Current Mode) average current control or (Peak Current Mode) peak current control, which requires control of the average value of the converter inductor current, and an outer loop output current command in the control loop tracks the inductor current average value. In the DAB converter topology, the inductance is the sum of the leakage inductance of the transformer and the added inductance, the average value of one switching cycle of the inductance current is zero, and the secondary side has no additional filter inductance, so that average current control cannot be used. The peak current control tracks the peak value of the inductor current through the output current command of the controller to adjust the duty ratio, the switch is turned on at the initial moment of each switching period, and the switch is turned off after the peak current command is reached, however, the DAB converter needs to control the phase shift ratio between the primary side and the secondary side, and the direct relation between the peak value of the inductor current and the actual phase shift does not exist, so that the method cannot be realized.
Disclosure of Invention
The invention aims to provide a DAB converter current mode modulation method which is small in calculation amount and easy to realize, and the current command is used for directly controlling the primary side and secondary side of the converter to shift the phase, so that the DAB converter current mode modulation method has quick dynamic response capability and can provide a week current limiting protection function.
The technical solution for realizing the purpose of the invention is as follows: a current mode modulation method of a DAB converter comprises the following steps:
step 1, establishing an inductance current equation by using a DAB converter working mode under phase shift control, and determining the relation between a current instruction and an actual phase shift;
step 2, analyzing the switching states under different current instructions, and performing phase shift control on the primary side and the secondary side of the DAB converter through the current instructions to realize a current modulation function;
step 3, establishing a dynamic mathematical model of the converter to obtain a control output transfer function in a current mode;
and 4, designing a discrete controller, and realizing current instruction adjustment and actual phase shift by current modulation in the step 2 to complete control of output voltage.
Further, the inductor current equation described in step 1 is specifically:
the relation between the inductor current command and the actual phase shift ratio is:
wherein: i.e L Is inductor current, V 1 Input voltage for DAB converter, V 2 For the output voltage of the converter,for the actual shift, L is the sum of the leakage inductance of the transformer and the added inductance, f s For the switching frequency of the converter, n is the turn ratio of the transformer, Q is the secondary side switching state, i c Is a current command, t 0 Is the initial moment of the switching cycle.
Further, the switch states under the different current instructions described in step 2 are specifically:
when the converter is in a starting state, a current instruction is positive, and the secondary side switch state at the stage is as follows:
after the converter enters a steady state, the actual phase shift is smaller than a set value, so that a current instruction is negative, and the secondary side switch state at the stage is as follows:
wherein: i.e L For inductive current, i c For current command, v L For the inductance voltage, Q represents the secondary side switch state;
further, the dynamic mathematical model of the converter described in step 3 is specifically:
the control output transfer function in the current mode is specifically:
wherein:for outputting a small-signal AC component of the voltage, +.>Is the real part of the alternating current component of the first-order small signal of the inductive current,for controlling the small signal ac component, +.>For the imaginary part, R, of the alternating current component of the inductive current first-order small signal t For the line impedance, f s For the converter switching frequency ω=2pi f s R is a load resistor, D is a steady-state direct current component with actual phase shift, C is an output side filter capacitor, L is the sum of leakage inductance and an additional inductance of a transformer, I 0I To output the steady-state DC component imaginary part of the current, I 0R For outputting the real part of the steady-state DC component of the current, V 0 To output steady-state DC component of voltage G vc And(s) is a control output transfer function in a current mode, and s is a frequency domain expression symbol.
Further, the discrete controller in step 4 specifically includes:
wherein: k (k) p To control gain coefficient, k i To integrate the coefficients, T s For the value of the switching period of the converter, G c (z) is a discrete controller, z is a z-domain expression of discrete signals;
the discrete controller outputs a current command, and controls the secondary side switch state according to the current command, so that the phase shift ratio is adjusted, and the output control is completed.
Compared with the prior art, the invention has the remarkable advantages that: (1) The current mode modulation can be carried out on the DAB converter, so that the inductance current stress during starting is effectively reduced, a week-by-week current limiting protection function can be provided, and the reliability is higher; (2) The converter voltage outer loop outputs a current instruction to control the turning point of the inductive current, the control of the phase shift outside the primary side and the secondary side of the converter is realized through current mode modulation, the calculated amount is small, the realization is easy, and the quick dynamic response capability is realized.
Drawings
Fig. 1 is a flowchart of a current mode modulation method of the DAB converter of the present invention.
Fig. 2 is an overall control block diagram of the DAB converter.
Fig. 3 is a modal waveform diagram of a DAB converter.
Fig. 4 is a schematic diagram of a current mode modulation method.
Fig. 5 is a schematic diagram of a current mode modulation method under a practical small phase shift ratio.
Fig. 6 is a graph of the control output transfer function Bode in the converter current mode.
Fig. 7 is a diagram of inductor current simulation versus waveform.
Fig. 8 is a simulated waveform diagram of the relationship between the current command and the actual phase shift.
Detailed Description
Referring to fig. 1, the invention provides a current mode modulation method of a DAB converter, which specifically comprises the following steps:
step 1, establishing an inductance current equation by using a DAB converter working mode under phase shift control, and determining the relation between a current instruction and an actual phase shift;
step 2, analyzing the switching states under different current instructions, and performing phase shift control on the primary side and the secondary side of the DAB converter through the current instructions to realize a current modulation function;
step 3, establishing a dynamic mathematical model of the converter to obtain a control output transfer function in a current mode;
and 4, designing a discrete controller, and realizing current instruction adjustment and actual phase shift by current modulation in the step 2 to complete control of output voltage.
Further, the inductor current equation in step 1 is:
the relation between the inductor current command and the actual shift is:
wherein: i.e L Is inductor current, V 1 Input voltage for DAB converter, V 2 For the output voltage of the converter,for the actual shift, L is the sum of the leakage inductance of the transformer and the added inductance, f s For the switching frequency of the converter, n is the turn ratio of the transformer, Q is the secondary side switching state, i c Is a current command, t 0 Is the initial moment of the switching cycle.
Further, in step 2, the switching state under the inductor current command is:
wherein: i.e L For inductive current, i c For current command, v L For the inductance voltage, Q represents the secondary side switch state;
further, the dynamic mathematical model of the converter in step 3 is specifically:
the control output transfer function in the current mode is specifically:
wherein:for outputting a small-signal AC component of the voltage, +.>Is the real part of the alternating current component of the first-order small signal of the inductive current,for the imaginary part of the inductive current first order small signal alternating current component, < ->For controlling the small-signal alternating-current component, R t For the line impedance, f s For the converter switching frequency ω=2pi f s R is a load resistor, D is a steady-state direct current component with actual phase shift, C is an output side filter capacitor, L is the sum of leakage inductance and an additional inductance of a transformer, I 0I To output the steady-state DC component imaginary part of the current, I 0R For outputting the real part of the steady-state DC component of the current, V 0 To output steady-state DC component of voltage G vc And(s) is a control output transfer function in a current mode, and s is a frequency domain expression symbol.
Further, in step 4, the discrete controller realizes the actual phase shift of current command adjustment through current modulation, and specific parameters for completing the control of the output voltage are as follows:
wherein: k (k) p To control gain coefficient, k i To integrate the coefficients, T s For the value of the switching period of the converter, G c (z) is a discrete controller, z is the z-domain expression of the discrete signal.
The controller outputs a current command, and controls the secondary side switch state according to the current command, so that the phase shift ratio is adjusted, and the output control is completed.
Examples
The invention will be further described with reference to the accompanying drawings.
FIG. 2 is a block diagram showing the overall control of the DAB converter, HB1 is an input side H-bridge, HB2 is an output side H-bridge, V h1 At HB1 midpoint voltage, V h2 Is HB2 midpoint voltage, S 1 ～S 4 The driving signal is HB1 switched. Sampling the output voltage and a reference value V 2ref After comparison, the current enters an outer ring controller, the controller outputs an inductance current instruction, and the current instruction is adjusted to the actual phase shift ratio through a current modulation module. The working mode of the converter is shown in fig. 3, wherein T is hs Is half a switching period. The diagonal switches of the two H-bridges are switched on and off simultaneously, the upper switch and the lower switch of the same bridge arm are complementarily conducted for 180 degrees, and the primary side switch S and the secondary side switch S are used for switching on and off 1 The opening delay between Q and Q is the actual shift.
First, an inductor current equation obtained from the modal waveform is as follows:
the current command is an inductance current turning point, and the value controls the secondary side switch state, namely, the relation between the current command and the actual movement is as follows:
wherein: i.e L Is inductor current, V 1 Input voltage for DAB converter, V 2 For the output voltage of the converter,for the actual shift, L is the sum of the leakage inductance of the transformer and the added inductance, f s For the switching frequency of the converter, n is the turn ratio of the transformer, Q is the secondary side switching state, i c Is a current command, t 0 Is the initial moment of the switching cycle.
And secondly, analyzing the action state of the switch according to different working conditions of the converter. As shown in fig. 4 and 5, D eff In order to actually shift the phase, when the converter is in a starting stage, the output side voltage is lower, so that the controller outputs a larger current instruction and reaches the limiting upper limit value, namely the current instruction is larger than zero, the output voltage needs to be increased in the stage, the limiting upper limit value of the controller needs to consider the influence of the current instruction on the actual phase shift ratio, the actual phase shift ratio is reduced due to the fact that the upper limit value is too large, the output voltage is difficult to increase, the upper limit value is required to be reduced, and the response speed in starting is improved, and the secondary side switch state of the converter in the stage is as follows:
wherein: i.e L For inductive current, i c For current command, v L For the inductance voltage, Q represents the secondary side switch state;
when the voltage at the output side gradually rises and exceeds V ref Then, the controller outputs a decrease in the current command value to decrease the output, and since the actual phase shift in the steady state is smaller, the current command is negative in the steady state according to the expression (3):
the lower limit value of the amplitude limit of the controller at this stage can be lower, the adjusting range of the controller is enlarged, and the secondary side switch state of the converter at this stage is as follows:
wherein: i.e L For inductive current, i c For current command, v L For the inductance voltage, Q represents the secondary side switch state;
further, a dynamic mathematical model of the converter is established, specifically as follows:
obtaining a small signal state space equation
Wherein:for outputting a small-signal AC component of the voltage, +.>Is the real part of the alternating current component of the first-order small signal of the inductive current,for the imaginary part of the inductive current first order small signal alternating current component, < ->For controlling the small-signal alternating-current component, R t For the line impedance, f s For the converter switching frequency ω=2pi f s R is a load resistor, D is a steady-state direct current component with actual phase shift, C is an output side filter capacitor, L is the sum of leakage inductance and an additional inductance of a transformer, I 0I To output the steady-state DC component imaginary part of the current, I 0R For outputting the real part of the steady-state DC component of the current, V 0 For the steady-state DC component of the output voltage, the state variable +.>A is a state matrix, B is an input matrix, and output +.>Control amount->C is the output matrix.
The current mode control output transfer function can be derived as:
the amplitude-frequency characteristic of the transfer function is shown in fig. 6.
Fig. 7 shows the comparison of the inductance current of the two methods in actual operation, and compared with the single voltage loop mode, the current mode has small starting current and higher response speed. FIG. 8 is a simulated waveform diagram of the relationship between the current command and the actual phase shift, wherein on delay is the on delay generated by the digital controller.
And finally, designing a discrete controller according to the transfer function of the current mode control output, wherein the output of the controller is a current instruction, and controlling the secondary side switch state by the current instruction to realize the adjustment of the actual phase shift ratio and complete the control of the output.
The foregoing is only a preferred embodiment of the invention, it being noted that: it will be apparent to those skilled in the art that various modifications and adaptations can be made without departing from the principles of the present invention, and such modifications and adaptations are intended to be comprehended within the scope of the invention.
Claims (1)
1. A DAB converter current mode modulation method characterized by comprising the steps of:
step 1, establishing an inductance current equation by using a DAB converter working mode under phase shift control, and determining the relation between a current instruction and an actual phase shift;
step 2, analyzing the switching states under different current instructions, and performing phase shift control on the primary side and the secondary side of the DAB converter through the current instructions to realize a current modulation function;
step 3, establishing a dynamic mathematical model of the converter to obtain a control output transfer function in a current mode;
step 4, designing a discrete controller, and realizing current instruction adjustment and actual phase shift by current modulation in the step 2 to complete control of output voltage;
the inductive current equation described in step 1 specifically includes:
the relation between the inductor current command and the actual phase shift ratio is:
wherein: primary and secondary side switch S 1 The opening delay between the two Q values is the actual shift; i.e L Is inductor current, V 1 Input voltage for DAB converter, V 2 For the output voltage of the converter,for the actual shift, L is the sum of the leakage inductance of the transformer and the added inductance, f s For the switching frequency of the converter, n is the turn ratio of the transformer, Q is the secondary side switching state, i c Is a current command, t 0 The initial moment of the switching period is;
the switch states under the different current instructions in the step 2 are specifically as follows:
when the converter is in a starting state, a current instruction is positive, and the secondary side switch state at the stage is as follows:
after the converter enters a steady state, the actual phase shift is smaller than a set value, so that a current instruction is negative, and the secondary side switch state at the stage is as follows:
the dynamic mathematical model of the converter in the step 3 is specifically:
the control output transfer function in the current mode is specifically:
wherein:for outputting a small-signal AC component of the voltage, +.>For the real part of the alternating current component of the inductive current first order small signal, < +.>For controlling the small signal ac component, +.>For the imaginary part, R, of the alternating current component of the inductive current first-order small signal t For line impedance, ω=2pi f s R is a load resistor, D is a steady-state direct current component with actual phase shift, C is an output side filter capacitor, I 0I To output the steady-state DC component imaginary part of the current, I 0R For outputting the real part of the steady-state DC component of the current, V 0 To output steady-state DC component of voltage G vc (s) is a control output transfer function in a current mode, and s is a frequency domain expression symbol;
the discrete controller in step 4 specifically comprises:
wherein: k (k) p For the controller gain coefficient, ki is the controller integral coefficient, ts is the converter switching period value, G c (z) is a discrete controller, z is a z-domain expression of discrete signals;
the discrete controller outputs a current command, and controls the secondary side switch state according to the current command, so that the phase shift ratio is adjusted, and the output control is completed.
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| CN114884360B (en) * | 2022-04-22 | 2023-04-14 | 电子科技大学 | Optimal reactive power bidirectional modulation strategy applicable to wide-range scene |
| CN115149818B (en) * | 2022-07-27 | 2024-05-03 | 山东大学 | Current-free bias magnetic quick start control method and system based on expansion phase shift modulation |
| CN116087595A (en) * | 2023-02-01 | 2023-05-09 | 苏州大学 | Leakage inductance parameter estimation method for high-frequency transformer of DAB converter |
| CN116680897A (en) * | 2023-05-31 | 2023-09-01 | 广东电网有限责任公司 | Frequency domain steady-state modeling method and device for double-active-bridge converter |
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| CN106849668A (en) * | 2017-02-24 | 2017-06-13 | 南京南瑞集团公司 | The double active bridge DC/DC converters novel bicyclic control methods of two-track phase control |
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| CN106849668A (en) * | 2017-02-24 | 2017-06-13 | 南京南瑞集团公司 | The double active bridge DC/DC converters novel bicyclic control methods of two-track phase control |
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