CN113647021A - Circuit arrangement for operating a converter - Google Patents
Circuit arrangement for operating a converter Download PDFInfo
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- CN113647021A CN113647021A CN202080025083.3A CN202080025083A CN113647021A CN 113647021 A CN113647021 A CN 113647021A CN 202080025083 A CN202080025083 A CN 202080025083A CN 113647021 A CN113647021 A CN 113647021A
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- 238000000034 method Methods 0.000 claims description 22
- 230000000295 complement effect Effects 0.000 claims description 14
- 239000003990 capacitor Substances 0.000 claims description 13
- 230000001960 triggered effect Effects 0.000 claims description 7
- 238000004590 computer program Methods 0.000 claims description 3
- 230000008878 coupling Effects 0.000 claims description 2
- 238000010168 coupling process Methods 0.000 claims description 2
- 238000005859 coupling reaction Methods 0.000 claims description 2
- 230000008569 process Effects 0.000 description 9
- 239000004065 semiconductor Substances 0.000 description 4
- 238000007599 discharging Methods 0.000 description 3
- 230000000694 effects Effects 0.000 description 3
- 230000000903 blocking effect Effects 0.000 description 2
- 230000001276 controlling effect Effects 0.000 description 2
- 238000007667 floating Methods 0.000 description 2
- 230000008859 change Effects 0.000 description 1
- 230000003111 delayed effect Effects 0.000 description 1
- 230000001419 dependent effect Effects 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 230000005669 field effect Effects 0.000 description 1
- 230000003993 interaction Effects 0.000 description 1
- 230000003071 parasitic effect Effects 0.000 description 1
- 230000001105 regulatory effect Effects 0.000 description 1
- 238000000926 separation method Methods 0.000 description 1
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
- H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
- H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
- H03K17/6871—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors the output circuit comprising more than one controlled field-effect transistor
- H03K17/6872—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors the output circuit comprising more than one controlled field-effect transistor using complementary field-effect transistors
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/08—Modifications for protecting switching circuit against overcurrent or overvoltage
- H03K17/081—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit
- H03K17/0812—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit by measures taken in the control circuit
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/08—Modifications for protecting switching circuit against overcurrent or overvoltage
- H03K17/082—Modifications for protecting switching circuit against overcurrent or overvoltage by feedback from the output to the control circuit
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/16—Modifications for eliminating interference voltages or currents
- H03K17/161—Modifications for eliminating interference voltages or currents in field-effect transistor switches
- H03K17/162—Modifications for eliminating interference voltages or currents in field-effect transistor switches without feedback from the output circuit to the control circuit
- H03K17/163—Soft switching
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/16—Modifications for eliminating interference voltages or currents
- H03K17/168—Modifications for eliminating interference voltages or currents in composite switches
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0029—Circuits or arrangements for limiting the slope of switching signals, e.g. slew rate
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
- H03K2217/0054—Gating switches, e.g. pass gates
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Inverter Devices (AREA)
- Power Conversion In General (AREA)
Abstract
The invention relates to a circuit arrangement (10) for controlling a converter (30) and for at least two different operating modes of the converter (30), having: an input connection (25) for connecting a gate drive output stage (20); an output connection (31) for connection with a control connection of the converter (30); at least two resistors (27, 32); a switching unit (35) having two switching states, wherein the switching unit (35) is electrically connected to the at least two resistors (27, 32) in such a way that at least two different resistance values act between the input connection (25) and the output connection (31) depending on the switching state of the switching unit (35); and a control unit (34) configured to: the switching units (35) are controlled into respective switching states in dependence on the operating mode of the converter (30).
Description
Technical Field
The invention relates to a circuit arrangement which improves the control of a converter for different operating modes.
Background
Electric drive systems, for example, in electric and hybrid vehicles, use an inverter which supplies current for operating an electric machine by means of a direct voltage. A direct voltage intermediate circuit with an intermediate circuit capacitor is located at the input of such an inverter.
In the event of a fault, it can be necessary: the connected electric machine is brought into a reliable operating mode. Such a reliable operation mode can for example comprise an active short circuit of the converter, wherein all high-side switches or all low-side switches of the converter are closed. Alternatively, the freewheeling mode can also be set to a reliable operating mode in which all switches of the full bridge are open.
In addition, the dc voltage intermediate circuit should be discharged quickly and reliably in such a case. For an active rapid discharge of the intermediate circuit of the converter, a half-bridge short circuit can be provided in a targeted manner in the phase of the operation of the converter.
Document DE 102016207373 describes the discharge of an intermediate circuit capacitor in an inverter device. During operation of the electric machine connected to the inverter in idle mode as a reliable state, the intermediate circuit capacitor can be discharged, for example. The discharge of the intermediate circuit capacitor is performed by timing the triggering of the semiconductor switches within the inverter. In this case, the following bridge branches of the inverter are respectively selected for the timing triggering: the phase voltage of the bridge branch is minimal.
It is difficult to use this method to adjust the intensity of the short-circuit current by means of a half-bridge short circuit during the time instants.
Disclosure of Invention
The invention relates to a circuit arrangement for operating a converter, a method for operating a converter, a computer program product, a computer-readable storage medium and a drive system, which have at least in part the stated effects. Advantageous embodiments are the subject matter of the dependent claims and of the following description.
In order to make it possible to more easily adjust the intensity of the short-circuit current during the timed triggering by means of a half-bridge short-circuit for rapid discharge of the intermediate circuit capacitor, it is proposed according to the invention that: when the converter is operated in a fast discharging mode, the current is limited by means of an increased resistance through the control connection of the switching elements of said converter. The relevant switching elements of the converter are switched in more slowly due to the increased series resistance and can therefore be adjusted more easily. In normal mode operation of the converter, i.e. in an operating mode in which the converter drives, for example, an electric machine, rapid switching is desired for reducing the power loss of the converter, so that for this purpose a low-impedance series resistance is connected between the gate driver stage and the control terminals of the switching elements of the converter in normal mode operation. The series resistance of the control terminals of the switching elements of the converter is increased only for the active, fast-discharging mode of operation of the intermediate circuit. However, such a variation of the series resistance can also be used to optimize the operating state of the converter.
Two series resistors of different required sizes for such a switching device can be connected to the controllable switches in such a way for normal mode operation of the converter that a higher resistance is then bridged. However, for the switching in of such a controllable switch, several 10ns are required for switching in the switching elements of the converter, so that each switching in process of the controllable switch of the converter will take place via a high-resistance series resistance during the first x 10ns before the low-resistance series resistance acts. Furthermore, conventional actuation of such controllable switches with a voltage triggered at the control terminal in a timed manner would be complicated in terms of circuit technology and therefore more expensive.
With a significantly faster switching behavior for future power semiconductors for the converter switching elements, such as for example SiC-MOSFETs or wide bandgap power semiconductors in general, the access delay of the controllable switches can no longer be ignored, since it has an effect on the higher access losses of the switching elements of the converter, which leads to higher overall losses of the converter.
The invention is based on the following considerations: the series resistance switching device has been actively switched with a simple circuit in the switched-off state of the switching elements of the converter and thus the gate series resistance of the low impedance has been made active at the beginning of the customary switching-in process of the switching elements of the converter.
The circuit arrangement according to the invention for operating a converter and for at least two different operating modes of the converter has input terminals for connecting a gate drive output stage, wherein the gate drive output stage provides a voltage for switching in a switching element of the converter. Furthermore, the circuit arrangement has an output connection for connecting the circuit arrangement to a control connection of one of a large number of switching elements of the converter. The converter can therefore also have a large number of such circuit arrangements according to the invention due to its large number of switching elements.
Furthermore, the circuit arrangement has at least two resistors, with which at least two different operating modes of the converter can be switched. However, the switching speed can limit the small resistance of, for example, 1 ohm for normal mode operation (which supports fast switching), for example, due to electromagnetic compatibility or loading limitations of the switching elements of the converter. Furthermore, a higher resistance, e.g. 25 ohms, is used to reduce the switching speed of the switching elements of the converter, so that the timing of the triggering of the switching elements of the converter can be adjusted more easily in a fast discharging mode of the intermediate circuit of the converter.
Furthermore, the circuit arrangement has a switching unit which can assume two switching states. In one of the switching states the switching unit blocks a current through the switching unit, in a further switching state a current is able to flow through the switching unit. The switching unit is electrically connected to the at least two resistors in such a way that at least two different resistance values act between the input connection and the output connection depending on the switching state of the switching unit. Such a co-action of the switching unit and the resistor can be realized in different ways. The circuit arrangement also has a control unit which is set up to control the switching units into the respective switching states as a function of the operating mode of the converter. For this purpose, the control unit derives a signal in analog or digital form either from the converter or from a control device of the converter, which causes the switching unit to set the switching unit according to the mode of the converter.
With the circuit arrangement: resistors of different sizes can act between the gate drive output stage and the control terminals of the switching elements of the converter to limit the current so that the switching elements switch at different speeds depending on the mode of the converter.
According to the design scheme of the invention, the method comprises the following steps: the switching unit is configured to change the switching state as a function of different, in particular non-time-triggered, control signals of the control unit. That is, the switching unit is switched by a corresponding control signal. In particular, the control signal is not switched in and out with a period of operation of the converter or of the switching elements of the converter. The control signal is for example a voltage, the value of which is not changed as long as the operating mode of the converter is not changed.
The circuit complexity for the circuit arrangement is therefore low and therefore inexpensive. The control of the timing trigger for the switching unit may require, for example, potential separation and additional circuit complexity.
According to a measure that improves the invention, it is proposed that the switching unit is configured to: the control signals of the control unit cooperate with the four units during operation of the circuit arrangement and also when both the gate driver stage and the converter are in operation and are connected in such a way that the switching unit is permanently switched conductive in one of the at least two operating modes of the converter.
The advantages are that: no additional switching delay is added in the normal mode-operational operating state of the converter due to the permanent conduction of the switching cells.
According to a further embodiment of the invention, the following is provided: the switching unit has two complementary controllable switches, which are connected in anti-parallel.
As controllable switching elements, capacitively connected switching elements, such as, for example, unipolar components, can be used. Examples of such controllable switching elements include HEMTs (high-electron-mobility transistors), jfets (junction field effect transistors), MOSFETs, IGBTs (bipolar transistors with insulated gates), and thyristors. Furthermore, a cascode (Kaskoden), that is to say a series circuit of normally-on components and low-voltage semiconductors, can be used to control the current. Such complementary parallel circuits can also be realized with bipolar transistors.
In a further embodiment of the invention, it is proposed that the switching unit is configured to: at least one of the two complementary controllable switches of the switching unit is switched to be always conductive in one of the at least two operating modes of the converter in order to switch the switching unit to be permanently conductive.
As is also explained in more detail in the exemplary embodiments of the invention below, in normal mode operation of the converter one of the complementary controllable switches connected in anti-parallel is switched in at the beginning of the switching-in process of the switching elements of the converter, and the second controllable switch is switched in close proximity to the end of the switching-in process of the switching elements. In normal mode operation, the switching unit is therefore permanently switched to be conductive, and therefore a correspondingly lower series resistance of the circuit arrangement is effective over the entire phase of the switching-in process of the switching element of the converter. The possibility of switching the at least two different resistances by means of the functional circuit arrangement for rapid intermediate circuit discharge can therefore be set without limiting the customary switching behavior.
According to a further embodiment of the invention, the following is provided: the respective control terminals of the two complementary controllable switches are loaded by the control unit with different, in particular non-time-triggered, switching terminal pre-voltages as control signals in one of the at least two operating modes.
Thus, it is achieved that: in each case one of the antiparallel controlled switches of the switching unit is reliably switched on both at the beginning of the switching-in of the switching element and also towards the end of the switching-in phase by the interaction of the switching voltage of the gate drive output stage and the gate potential of the control unit of the converter and the control signal of the control unit. This is also explained in more detail below for one embodiment.
According to a further embodiment of the invention, the following is provided: the two complementary controllable switches have a parallel circuit of a capacitor together with a discharge resistor between the control terminal and the switching terminal in order to increase the effective capacitance of the control terminal of the controllable switch. Thereby it is achieved that: in an operating mode of the converter, which is provided for rapid discharge of the intermediate capacitor with timed triggering operation, the complementary controllable switches are reliably held closed. The steep voltage edge occurring in this operating mode of the converter can, furthermore, switch the complementary controllable switches off on account of the small gate capacitance.
According to a further embodiment of the invention, the following is provided: the smaller of the at least two resistances is arranged in series with the switching unit, and the series circuit electrically connects the input terminal and the output terminal, and the series circuit is connected in parallel with the larger of the at least two resistances. In this way, in normal mode operation, when the switching unit is switched on, the parallel circuit of the two resistors is obtained as an effective resistor of the circuit arrangement, and when the switching unit is switched off, only the larger resistor is active.
According to a further embodiment of the invention, it is provided that the control unit is configured to: the control signal or, in particular, the non-clocked switching terminal pre-voltage is changed when the converter is switched into another of the at least two operating modes. The control of the complementary controllable switch therefore does not have to be effected with a clocked voltage, but is satisfied by a simple switching of the dc voltage at the control connection of the controllable switch.
According to the invention, a method for controlling a converter and for at least two different operating modes of the converter is proposed, which method, depending on the operating mode of the converter, controls a control unit of a circuit arrangement according to one of claims 1 to 10 such that it interacts with the switching unit in such a way that a different resistance value in each of the at least two operating modes of the converter acts between the input connection and the output connection.
All considerations and advantages which apply to the circuit arrangement according to the invention are therefore also applicable to the method for operating a converter which can be operated in at least two different operating modes. In particular, the method enables a circuit arrangement to be controlled which has the same structural features as the different embodiments of the circuit arrangement according to the invention shown above.
A computer program product is proposed, which comprises instructions which, when the program is executed by a computer, cause the computer to carry out the above-mentioned method.
Furthermore, a computer-readable storage medium is proposed, which comprises instructions which, when executed by a computer, cause the computer to carry out the above-mentioned method.
According to the invention, a drive system is proposed with a direct current source, a drive unit and an inverter for electrically coupling the direct current source to the drive unit. The converter is electrically connected to a circuit arrangement for operating the converter, as described above. The drive system with such a structure has the following advantages: the converter can be operated in at least two operating modes of the converter and can be better regulated in particular in the operating mode for a rapid discharge of the intermediate circuit capacitor with a timed triggering of the switching elements of the converter.
Drawings
An embodiment of the present invention is shown in fig. 1 and explained in more detail below.
Wherein:
fig. 1 shows a circuit arrangement 10 for operating an inverter 30 together with the inverter 30 and a gate drive output stage 20.
Detailed Description
It is characteristic for the invention that antiparallel-connected, complementary controllable switches 11, 12 are used for switching the effective resistance value between the input 25 and the output 31 of the circuit arrangement 10. This is implemented in fig. 1 as a parallel circuit of an N-channel MOSFET and a P-channel MOSFET, wherein the source connection of one MOSFET is in contact with the drain connection of the other MOSFET.
The output of the gate drive output stage 20, which provides the power for switching in the switching elements of the inverter 30, is connected to the input 25 of the circuit arrangement 10. The switching element of said converter 30 is one of a plurality of switching elements of said converter 30 and is here only indicated by a connection to said converter 30, which connection is in the converter 30 connected with a control electrode of said switching element. At this input 25, the drain terminal of the N-channel MOSFET 11 is electrically connected to the source terminal of the P-channel MOSFET 12. The two MOSFET transistors 11, 12 are electrically connected to one another with their respective other source and drain connections and are therefore connected in anti-parallel. A first contact 21 of a first resistor 32 is connected to a connection of the parallel circuit of the MOSFET transistors 11, 12 opposite the input 25. The first resistor 32 can be smaller than the second resistor 27. The second contact 31 of the first resistor 32 is shown as an output of the circuit arrangement 10 and is connected to a control terminal 29 of the converter 30, which is connected to a control electrode of a switching element of the converter 30. The second resistor 27 is connected with its first connection 26 to the input 25 of the circuit arrangement 10 and with its second connection 28 to the second connection 31 of the first resistor 32, i.e. to the output of the circuit arrangement 10.
The parallel circuit formed by the gate discharge resistors 13, 18 and the capacitors 14, 17 makes electrical contact between the respective gate and source connections for the two transistors 11, 12. The gate capacitor 14 increases the capacitance of the gate terminal for reliably blocking the MOS transistors 11, 12 in the rapid discharge operation of the converter 30, as described above. Electrical connections from the gate connections of the two transistors 11, 12, respectively, to a control unit 34, into which resistors 15, 16 for current limiting are inserted, respectively.
The control unit 34 is connected with a first output terminal 23 to the gate terminal of the N-MOSFET 12, and the second output terminal 24 of the control unit 34 is connected with the gate terminal of the P-MOSFET 11. In normal mode operation of the converter 30, i.e. when the converter 30 is driving a motor, for example, the converter 30 sends a signal via the control connection 33, which causes the control unit 34 to place the first terminal at a potential slightly above the base potential, for example, 5V, so that the N-MOSFET is reliably switched in. In normal mode operation, the control unit 34 sets the potential of the second output terminal 24 to the base potential. For the operating mode of the converter 30, in which the intermediate circuit capacitor should discharge rapidly with the timed triggering (antekten) of the switching elements of the converter, the control unit 34 switches its first and second output terminals into a floating state, for example by means of an "open collector circuit".
In order to switch the N-channel MOSFET 11 on, its gate must be placed at a positive potential. The positive gate-source voltage of N-channel MOSFET 11 is obtained in the switched-off state of the switching elements of inverter 30, i.e. without a voltage from gate drive output stage 20. This N-channel-MOSFET is switched in because the potential at a level slightly exceeding the base potential is located at the gate of the N-channel-MOSFET 11 via the first output terminal 23 of the control unit 34 and the typically negative voltage of the control terminal of the switching element of the converter 30 is located at the source terminal of the N-channel-MOSFET.
In the switched-in state of the switching elements of inverter 30, the gate-source voltage of N-channel MOSFET 11 is conversely negative or zero, so that N-channel MOSFET 11 is switched off. Since the source potential of the N-channel MOSFET is very positive due to the access voltage of the gate driven output stage 20.
For the P-channel MOSFET 12, a negative gate-source-voltage must be applied for switching to conduction. In normal mode operation of the inverter 30, the gate of the P-channel MOSFET 12 is at the base potential due to the second output of the control unit 34. In the switched-in state of the switching elements of inverter 30, that is to say with a positive voltage of gate drive output stage 20, a negative gate source voltage of P-channel MOSFET 12 is obtained, so that P-channel MOSFET 12 is switched in. In the switched-off state of the switching elements of the inverter 30, the gate-source-voltage of the P-channel MOSFET 12 is conversely positive or zero, so that the P-channel MOSFET 12 is switched off.
The N-channel MOSFET 11 is thus switched in at the beginning of the switching-in process of the switching element of the converter 30 and the P-channel MOSFET 12 is switched in near the end of the switching-in process of the control element of the converter 30. The crossover of the second resistor 27, which is caused by the parallel circuit of the MOSFET transistors 11, 12 together with the series-connected first resistor 32, is therefore actively conductive during the entire switching-in process of the switching elements of the converter 30, so that the overall resistance of the first resistor 32, which is usually much smaller in normal mode operation of the converter, does not have a negative effect on the switching times of the switching elements of the converter.
The circuit arrangement 10 described serves for controlling the converter 30 and for the switching of at least two different operating modes with an effective resistance of the circuit arrangement 10, which functions as a series resistance of the control terminals of the switching elements of the converter, whereby the correct series resistance is set for the functionality of a rapid intermediate circuit discharge, so that it can be implemented without limiting the switching-in behavior in the normal mode operation of the converter 30.
The switching over of the control unit 34 to the operating mode of rapid discharge of the intermediate circuit capacitor is effected, for example, by a signal from the converter 30 via the signal lead 33 to the control unit 34. The gate connections of the latter two transistors are then switched to be floating, for example by means of an open collector circuit.
Due to the gate discharge resistors 13, 18, the input capacitances of the MOSFET- transistors 11, 12 are discharged, so that their control voltage (gate-source-voltage for the MOSFETs) is zero and they are switched off. By means of the external gate capacitances 14, 17, the MOSFET transistors 11, 12 are protected against parasitic access as a result of the switching process of the gate driver output stage 20. The control voltage of the MOSFET transistor 11, 12 therefore does not remain switched off as a function of the switching operation of the gate drive output stage 20 and therefore also as a function of the switching state of the controlled converter 30. Therefore, during all switching-in operations of the gate drive output stage 20, only the second resistor 27 between the input connection 25 and the output connection 31 is active, so that the inverter 30 is switched in a delayed manner with respect to normal mode operation.
Thereby blocking both MOSFET- transistors 11, 12 and current flows from the gate drive output stage through the second resistor 27 having a larger value than the first resistor 32. Due to the resulting smaller current, the switching elements of the converter 30 are switched in more slowly, which is advantageous for the regulation of the time-triggered operation in the fast discharge operating mode of the converter 30.
Claims (13)
1. Circuit arrangement (10) for controlling a converter (30) and for at least two different operating modes of the converter (30), having: an input connection (25) for connecting a gate drive output stage (20); an output connection (31) for connection to a control connection (29) of the converter (30);
at least two resistors (27, 32);
a switching unit (35) having two switching states, wherein the switching unit (35) is electrically connected to the at least two resistors (27, 32) in such a way that at least two different resistance values act between the input connection (25) and the output connection (31) depending on the switching state of the switching unit (35); and
a control unit (34) configured to: controlling the switching unit (35) into a respective switching state in dependence on an operating mode of the converter (30).
2. The circuit arrangement (10) according to claim 1, wherein the switching unit (35) is configured to: the switching states are changed as a function of different, in particular non-time-triggered, control signals of the control unit (34).
3. Circuit arrangement (10) according to claim 1 or 2, characterized in that the switching unit (35) is set for: the control signals of the control unit (34) are used and cooperate with the connected gate drive output stage (20) and the connected converter (30) in the operation of the circuit arrangement (10) in such a way that the switching unit (35) is permanently switched into conduction in one of at least two operating modes of the converter (30).
4. Circuit arrangement (10) according to one of the preceding claims, characterized in that the switching unit (35) has two complementary controllable switches (11, 12) which are connected in anti-parallel.
5. Circuit arrangement (10) according to claims 3 and 4, characterized in that the switching unit (35) is set for: at least one of the two complementary controllable switches (11, 12) of the switching unit (35) is switched to be always conductive in one of the at least two operating modes of the converter (30) in order to permanently switch the switching unit (35) to be conductive.
6. Circuit arrangement (10) according to claim 4 or 5, characterised in that the respective control terminals of the two complementary controllable switches (11, 12) are loaded by the control unit (34) with different, in particular non-time-triggered, switching terminal pre-voltages as control signals in one of at least two operating modes.
7. Circuit arrangement (10) according to one of claims 4 to 6, characterised in that the two complementary controllable switches (11, 12) have a parallel circuit of a capacitor (14, 17) together with a gate discharge resistor (13, 17) between the control and switching connections in order to increase the effective capacitance of the control connections of the controllable switches (11, 12).
8. Circuit arrangement (10) according to one of the preceding claims, characterized in that the smaller of the at least two resistances (27, 32) is arranged in series with the switching unit (35) and in that the series circuit electrically connects the input connection (25) with the output connection (31) and in that the series circuit is connected in parallel with the larger of the at least two resistances (27, 32).
9. Circuit arrangement (10) according to one of the preceding claims, characterized in that the control unit (34) is set up for: -changing the control signal or, in particular, a non-time-triggered switching terminal pre-voltage when the converter (30) is switched into the mode of the other of the at least two operating modes.
10. Method for operating a converter (30) and for at least two different operating modes of the converter (30), which method controls a control unit (34) of a circuit arrangement (10) according to one of claims 1 to 9 depending on the operating mode of the converter (30) to co-operate with the switching unit (35) in such a way that in each of the at least two operating modes of the converter (30) a different resistance value acts between the input connection (25) and the output connection (31).
11. Computer program product comprising instructions which, when the program is executed by a computer, cause the computer to carry out the method according to claim 10.
12. A computer-readable storage medium comprising instructions that, when executed by a computer, cause the computer to perform the method of claim 10.
13. A drive system having: a direct current power source, a drive unit, an inverter (30) for electrically coupling the direct current power source with the drive unit, wherein the inverter is electrically connected with a circuit arrangement (10) for operating the inverter (30) according to any one of claims 1 to 10.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| DE102019201004.0 | 2019-01-28 | ||
| DE102019201004.0A DE102019201004A1 (en) | 2019-01-28 | 2019-01-28 | Circuit arrangement for the control of an inverter |
| PCT/EP2020/050983 WO2020156820A1 (en) | 2019-01-28 | 2020-01-16 | Circuit assembly for controlling an inverter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN113647021A true CN113647021A (en) | 2021-11-12 |
| CN113647021B CN113647021B (en) | 2024-06-14 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202080025083.3A Active CN113647021B (en) | 2019-01-28 | 2020-01-16 | Circuit arrangement for operating an inverter |
Country Status (4)
| Country | Link |
|---|---|
| EP (1) | EP3918713A1 (en) |
| CN (1) | CN113647021B (en) |
| DE (1) | DE102019201004A1 (en) |
| WO (1) | WO2020156820A1 (en) |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| DE102022103848A1 (en) | 2022-02-18 | 2023-08-24 | Audi Aktiengesellschaft | Method for operating an inverter device of an electric drive device, control unit, electric drive device and motor vehicle |
| US20240103559A1 (en) | 2022-09-28 | 2024-03-28 | Delphi Technologies Ip Limited | Systems and methods for oscillator calibrator for inverter for electric vehicle |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH1117510A (en) * | 1997-06-25 | 1999-01-22 | New Japan Radio Co Ltd | High frequency switch circuit |
| CN104201709A (en) * | 2014-08-15 | 2014-12-10 | 浙江大学 | Off-line control method for mixed direct current transmission system |
| JP2016073069A (en) * | 2014-09-29 | 2016-05-09 | キヤノン株式会社 | Power supply unit and control method of the same |
| JP2017051049A (en) * | 2015-09-04 | 2017-03-09 | 富士電機株式会社 | Driving device for semiconductor element |
| US20180205372A1 (en) * | 2017-01-18 | 2018-07-19 | Fuji Electric Co., Ltd. | Power semiconductor module and drive circuit |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE102016207373A1 (en) | 2016-04-29 | 2017-11-02 | Robert Bosch Gmbh | Inverter arrangement, electric drive system and method for discharging a DC link capacitor in an inverter arrangement |
-
2019
- 2019-01-28 DE DE102019201004.0A patent/DE102019201004A1/en active Pending
-
2020
- 2020-01-16 WO PCT/EP2020/050983 patent/WO2020156820A1/en unknown
- 2020-01-16 EP EP20701018.2A patent/EP3918713A1/en active Pending
- 2020-01-16 CN CN202080025083.3A patent/CN113647021B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH1117510A (en) * | 1997-06-25 | 1999-01-22 | New Japan Radio Co Ltd | High frequency switch circuit |
| CN104201709A (en) * | 2014-08-15 | 2014-12-10 | 浙江大学 | Off-line control method for mixed direct current transmission system |
| JP2016073069A (en) * | 2014-09-29 | 2016-05-09 | キヤノン株式会社 | Power supply unit and control method of the same |
| JP2017051049A (en) * | 2015-09-04 | 2017-03-09 | 富士電機株式会社 | Driving device for semiconductor element |
| US20180205372A1 (en) * | 2017-01-18 | 2018-07-19 | Fuji Electric Co., Ltd. | Power semiconductor module and drive circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| DE102019201004A1 (en) | 2020-07-30 |
| CN113647021B (en) | 2024-06-14 |
| WO2020156820A1 (en) | 2020-08-06 |
| EP3918713A1 (en) | 2021-12-08 |
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