CN113541489A - Composite type staggered parallel direct current conversion circuit and control method - Google Patents

Composite type staggered parallel direct current conversion circuit and control method Download PDF

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CN113541489A
CN113541489A CN202110748906.1A CN202110748906A CN113541489A CN 113541489 A CN113541489 A CN 113541489A CN 202110748906 A CN202110748906 A CN 202110748906A CN 113541489 A CN113541489 A CN 113541489A
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circuit
main
semiconductor device
ripple
ripple compensation
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CN113541489B (en
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孙乐
郭小强
刘兆国
卢志刚
华长春
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Yanshan University
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Yanshan University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H02M1/143—Arrangements for reducing ripples from dc input or output using compensating arrangements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention relates to a composite type staggered parallel direct current conversion circuit which comprises a main DC/DC circuit, a ripple compensation circuit and an energy supplementing circuit, wherein an input port of the main DC/DC circuit forms a total input port, a positive terminal of an output port of the main DC/DC circuit is connected with a positive terminal of an output port of the ripple compensation circuit to form a positive terminal of the total output port, and a negative terminal of the positive terminal is connected with a negative terminal of the output port of the ripple compensation circuit to form a negative terminal of the total output port; the output port of the energy supplementing circuit is connected with the input port of the ripple compensating circuit, the input voltage of the ripple compensating circuit is maintained at a certain level lower than the total input voltage, and a control method is provided based on the input voltage. The invention is superior to the traditional staggered parallel DC/DC converter, is suitable for occasions with extremely high current ripple requirements, and can realize the optimization of loss, cost, efficiency and volume.

Description

Composite type staggered parallel direct current conversion circuit and control method
Technical Field
The invention belongs to the technology of power electronic converters, and particularly relates to a composite type staggered parallel direct current conversion circuit and a control method.
Background
In recent years, a high-power direct-current power supply with low voltage, large current and low ripple characteristics is required to be adopted in many application occasions, for example, in the occasion of hydrogen production by electrolysis which is concerned in recent years, the hydrogen production direct-current power supply with low voltage, large current and low ripple is required to supply power to an electrolytic cell; in the field of energy storage of high-power storage batteries, in order to prolong the service life of the batteries, the charging and discharging current ripples are required to be as small as possible. To implement a low voltage, high current, low ripple dc power supply, two techniques are generally available: firstly, a staggered parallel DC/DC conversion circuit is adopted, and secondly, an additional ripple compensation circuit is added.
The staggered parallel DC/DC circuit, such as a typical staggered parallel Buck circuit, can realize large-current output, and the staggered parallel DC/DC circuit can effectively reduce the size of output current ripples if adopting carrier phase shift modulation, so the staggered parallel DC/DC circuit is widely applied to the field of high-power direct-current power supplies. For example, journal papers on the topology structure of a high-power hydrogen production converter and the research on the control strategy thereof (Yangwen, Schchenwen, Wangshun break, Power electronic technology, 2020, 54 (12): 5-8) the electrolytic hydrogen production power supply shown in FIG. 2 adopts a staggered parallel Buck circuit. However, in order to achieve a larger current output and a lower output current ripple, more parallel Buck circuit units are required. The increase of parallel units will lead to three problems: 1) the number of devices is increased, and the cost is increased; 2) the control signals are increased, and the control complexity is increased; 3) the signal that needs to be sampled increases. Because the current balance of each branch needs to be controlled and the inductive current information of each branch needs to be acquired, a current sensor needs to be added for each branch, the device cost is greatly increased, and the sensor connecting line is easy to break down, so that the reliability is influenced. In addition, even if the number of the parallel Buck circuit units is increased, theoretically, the output current ripple can only be reduced, but the output current ripple cannot be completely eliminated.
Another way to reduce the ripple is to use a special compensation branch to eliminate the ripple of the output current of the main converter, such as the circuit shown in FIG. 2 of journal paper AHigh-Efficiency DC-DC converter using 2nH Integrated Inductors (Wibbenj, Harjani R,2008,43(4):844 and 854), and use a stacked Buck circuit to eliminate the ripple of the output current. The method comprises the following steps that a Buck circuit is used as a main DC/DC converter and is responsible for power transmission; and the other path of Buck circuit is used as a ripple compensation converter, and the output end of the Buck circuit is connected with a capacitor in series and then is connected with the main DC/DC in parallel. The ripple compensating converter outputs a current opposite to the main DC/DC output ripple current, so that the ripple of the final total output current is 0. However, although the purpose of eliminating the output current ripple is achieved, only one path of Buck circuit transmits power, and the requirement of large current output is difficult to adapt. On the basis, the circuit shown in fig. 1 of the conference paper ALow-co-multi-phase 3ABuck converter with Improved Ripple compensation for wide supply range (HafeezKT, DuttaA, Single S G, et al 2016IEEE International Symposium on Circuits and Systems (ISCAS),2016: 1618-. However, this solution has the disadvantages that: the input port of the ripple compensating converter is directly connected with the input port of the interleaved Buck converter, so that a Buck circuit serving as the ripple compensating converter needs to adopt a switching device with higher withstand voltage, and the cost is higher; because the loss of the ripple compensation circuit is mainly high-frequency switching loss, and the switching loss is directly related to the turn-off voltage, the voltage resistance of the device in the scheme is increased to cause larger switching loss; in order to completely eliminate the ripple, the inductance of the ripple compensation circuit needs to be as large as that of the interleaved Buck circuit, so that the volume and the cost of equipment are increased.
In summary, in the current high-power DC power supply capable of realizing low-voltage, large-current and low-ripple output characteristics, the interleaved parallel DC/DC converter without the ripple compensation branch cannot completely eliminate the current ripple, and needs more main DC/DC converters; the ripple compensation branch of the interleaved parallel DC/DC converter with the ripple compensation branch still needs to adopt high voltage stress, high switching loss, high-cost switching devices and large inductance value filter inductors. The above limitations directly result in a device that is difficult to further increase in terms of cost, volume, efficiency, etc. Therefore, it is necessary and urgent to design a composite interleaved dc-dc converter circuit to further reduce the cost, reduce the size, and improve the efficiency.
Disclosure of Invention
In view of the above situation, the present invention provides a composite interleaved parallel direct current conversion circuit, which includes a main DC/DC circuit input port constituting a total input port, a positive terminal of a main DC/DC circuit output port connected to a positive terminal of a ripple compensation circuit output port to constitute a positive terminal of the total output port, and a negative terminal connected to a negative terminal of the ripple compensation circuit output port to constitute a negative terminal of the total output port; the output port of the energy supplementing circuit is connected with the input port of the ripple compensating circuit, the input voltage of the ripple compensating circuit is maintained at a certain level lower than the total input voltage, and a control method is provided based on the input voltage. The invention is superior to the traditional staggered parallel DC/DC converter, is suitable for occasions with extremely high current ripple requirements, and can realize the optimization of loss, cost, efficiency and volume.
The invention provides a composite type staggered parallel direct current conversion circuit which comprises a main DC/DC circuit, a ripple compensation circuit and an energy supplementing circuit, wherein an input port of the main DC/DC circuit forms a total input port, a positive terminal of an output port of the main DC/DC circuit is connected with a positive terminal of an output port of the ripple compensation circuit to form a positive terminal of the total output port, and a negative terminal of the main DC/DC circuit is connected with a negative terminal of the output port of the ripple compensation circuit to form a negative terminal of the total output port; the output port of the energy compensating circuit is connected with the input port of the ripple compensating circuit, and the input voltage of the ripple compensating circuit is maintained at a certain level U lower than the total input voltagerefThe main DC/DC circuit comprises a first half-bridge circuit and a first filter inductor, the first half-bridge circuit comprises a first semiconductor device and a second semiconductor device, a first end of the first semiconductor device forms a positive terminal of the input port of the main DC/DC circuit, and a second end of the first semiconductor device and a first end of the second semiconductor device and a first filter respectivelyThe first ends of the wave inductors are connected, the second end of the second semiconductor device forms a negative terminal of the input port of the main DC/DC circuit and is a negative terminal of the output port of the main DC/DC circuit, and the second end of the first filter inductor forms a positive terminal of the output port of the main DC/DC circuit;
the ripple compensation circuit comprises a second half-bridge circuit, a second filter inductor and a blocking capacitor, the second half-bridge circuit comprises a third semiconductor device and a fourth semiconductor device, a first end of the third semiconductor device forms a positive terminal of an input port of the ripple compensation circuit, a second end of the third semiconductor device is respectively connected with a first end of the fourth semiconductor device and a first end of the second filter inductor, a second end of the fourth semiconductor device forms a negative terminal of the input port of the ripple compensation circuit and is a negative terminal of an output port of the ripple compensation circuit, a first end of the blocking capacitor is connected with a second end of the second filter inductor, and a second end of the blocking capacitor forms a positive terminal of the output port of the ripple compensation circuit;
the energy supplementing circuit is an isolated DC/DC conversion circuit or a passive voltage dividing circuit without a semiconductor switch device.
Further, when the energy compensating circuit is an isolated DC/DC conversion circuit, the energy compensating circuit includes a first input port, an input side DC-AC converter, an isolation transformer, an output side AC-DC converter, and a first output port, where the first input port is connected to both sides of the blocking capacitor, and the first output port is connected to the input port of the ripple compensation circuit.
Preferably, when the energy compensating circuit is a passive voltage dividing circuit, the energy compensating circuit comprises a second input port, a first passive branch, a second passive branch and a second output port, the first passive branch and the second passive branch are connected in series, one end of the first passive branch connected in series with the second passive branch forms a positive terminal of the second output port, and the other end of the first passive branch connected in series with the second passive branch forms a positive terminal of the second input port; the end of the second passive branch not connected with the first passive branch in series forms a negative terminal of a second input port and is a negative terminal of a second output port; the first passive branch and the second passive branch are both formed by connecting a plurality of resistors in series or in parallel, or formed by connecting a plurality of capacitors in series or in parallel, or formed by connecting a plurality of resistors and capacitors in series or in parallel, or only comprise one resistor, or only comprise one capacitor; the second input port is connected to the input port of the composite type interleaving parallel direct current conversion circuit, and the second output port is connected to the input port of the ripple compensation circuit.
Preferably, the first semiconductor device, the third semiconductor device and the fourth semiconductor device are all-control semiconductor switching devices, and the second semiconductor device is an all-control semiconductor switching device or a diode.
Preferably, the number of the main DC/DC circuit, the ripple compensation circuit and the energy compensation circuit is at least 1; the number of the first half-bridge circuit and the number of the first filter inductor are respectively 1; and the number of the second half-bridge circuit, the second filter inductor and the blocking capacitor is 1.
In another aspect of the present invention, a control method using the aforementioned composite interleaved parallel DC conversion circuit is provided, where for a composite interleaved parallel DC conversion circuit including N main DC/DC circuits and 1 ripple compensation circuit, switching signals of the main DC/DC circuits and the ripple compensation circuit are generated by a control method in each control cycle, and the control method includes the following steps:
s1, according to the control demand of the concrete application occasion, generating the duty ratio command D of each main DC/DC circuitk(k＝1～N)；
S2, carrying out carrier phase shift modulation to generate each switching signal of the main DC/DC circuit;
s3, respectively detecting the input voltage u of each current main DC/DC circuitinAnd an output voltage uoBased on the current inductance current sum i of each main DC/DC circuitmainRate of change dimain/dt：
Figure BDA0003145381430000041
Wherein: l represents a first filter inductor of each main DC/DC circuit; skRepresenting a switching function of a first half-bridge circuit in a kth main DC/DC circuit;
s4, if dimain/dt>0, go to step S5; otherwise, executing step S6;
s5, turning on a fourth power semiconductor device of the ripple compensation circuit, turning off a third power semiconductor device of the ripple compensation circuit, and ending the period control;
and S6, turning off the fourth power semiconductor device of the ripple compensation circuit, turning on the third power semiconductor device of the ripple compensation circuit, and ending the period control.
Preferably, the step S2 specifically includes the following steps:
s21, respectively commanding duty ratio command D1～DNThe phase difference of the N phase is 2 pi/N, the minimum value is 0, the maximum value is 1, and the frequency is the switching frequency fsIf D is the triangular wave ofkIf the second semiconductor device is a full-control type switching device, executing step S24;
s22 switching function S of half-bridge of kth main DC/DC circuitkWhen the voltage is 1, the first semiconductor device is turned on;
s23 switching function S of half-bridge of kth main DC/DC circuitkWhen the value is 0, the first semiconductor device is turned off;
s24, the second semiconductor device is turned off when the first semiconductor device is turned on, and is turned on after the first semiconductor device is turned off.
Preferably, when the energy supplementing circuit is the isolated DC/DC conversion circuit, the isolated DC/DC conversion circuit is controlled in each control cycle by the following steps:
s71, sampling the voltage of the input end of the ripple compensation circuit;
s72, subtracting the sampling value obtained in S71 from the voltage reference value of the input end of the ripple compensation circuit to obtain a voltage control error;
s73, obtaining a power instruction of the isolated DC/DC conversion circuit by the control error through a PI controller;
and S74, obtaining the switch control signals of the input side DC/AC circuit and the output side AC/DC circuit according to the relation between the power of the isolated DC/DC conversion circuit and the circuit switch control signals.
The invention has the characteristics and beneficial effects that:
1. compared with the traditional staggered parallel DC/DC converter without the compensation branch, the composite staggered parallel DC/DC conversion circuit provided by the invention can adopt fewer staggered parallel DC-DC units under the same output current ripple index, and can theoretically completely eliminate the output current ripple, thereby reducing the inductance value of the filter inductor and being suitable for occasions with extremely high requirements on the current ripple; the switching frequency of the interleaved parallel DC/DC circuit can be reduced, so that a main DC/DC circuit can be formed by adopting a low-frequency switching device with higher power level, smaller on-state loss and higher switching loss, a ripple compensation circuit is formed by adopting a high-frequency switching device with lower power level, smaller switching loss and higher on-state loss, the advantages of different devices are exerted, and the optimization of loss and cost is realized under the same performance; because the number of the main DC/DC circuits is reduced, the control and sampling systems can be greatly simplified, the number of sensors is reduced, the operation time of a control algorithm is saved, and the cost and the realization difficulty are reduced.
2. Compared with the traditional staggered parallel DC/DC converter with the compensation branch, the composite staggered parallel DC/DC conversion circuit provided by the invention has the advantages that the ripple compensation circuit does not need to adopt a high-price switching device with high voltage withstanding capability, so that the cost is saved; the voltage resistance of the ripple compensation circuit is reduced, so that the switching loss is reduced, and the efficiency of the device is improved; under the condition of reasonable design, the reduction of the input voltage of the ripple compensation circuit can reduce the peak value of the filter inductance voltage, thereby reducing the required inductance value and reducing the volume of the device.
Drawings
FIG. 1 is a schematic diagram of an overall circuit of a composite interleaved DC-DC converter circuit according to the present invention;
FIG. 2 is a second embodiment of the overall circuit of the composite interleaved DC-DC converter circuit according to the present invention;
FIG. 3a is a first embodiment of a main DC/DC converter circuit according to the present invention;
FIG. 3b is a second embodiment of the main DC/DC converter circuit of the present invention;
FIG. 4 is a diagram illustrating an embodiment of a ripple compensation circuit according to the present invention;
FIG. 5a is a first embodiment of the power up circuit of the present invention;
FIG. 5b is a second embodiment of the power up circuit of the present invention;
FIG. 6 is a flowchart of a method for controlling the main DC/DC and ripple compensation circuit of the composite interleaved parallel DC-DC converter circuit according to the present invention;
FIG. 7 is a flowchart of a control method of the energy compensating circuit using the isolated DC/DC converter circuit according to the present invention;
fig. 8a is a schematic diagram of an embodiment of a first prior art solution (interleaved Buck circuit without ripple compensation) in a specific application scenario;
fig. 8b is a schematic diagram of an embodiment of a second prior art solution (interleaved Buck circuit with ripple compensation) in a specific application scenario;
FIG. 9a is a diagram illustrating a first embodiment of the present invention in a specific application scenario;
fig. 9b is a schematic diagram illustrating an implementation of the second embodiment of the present invention in a specific application scenario.
In the figure:
1-positive terminal of total input port; 2-a complementary energy circuit; 3-a ripple compensation circuit; 4-positive terminal of total output port; 5-negative terminal of total output port; 6-main DC/DC circuit; 7-negative terminal of total input port; 8-positive terminal of input port of primary DC/DC circuit; 9-a first semiconductor device; 10-a first filter inductance; 11-the positive terminal of the output port of the primary DC/DC circuit; 12-negative terminal of output port of main DC/DC circuit; 13-negative terminal of input port of primary DC/DC circuit; 14-a second semiconductor device; 15-positive terminal of input port of ripple compensation circuit; 16-a third semiconductor device; 17-a second filter inductance; 18-a dc blocking capacitance; 19-the positive terminal of the ripple compensation circuit output port; 20-negative terminal of output port of ripple compensation circuit; 21-negative terminal of ripple compensation circuit input port; 22-a fourth semiconductor device; 23-a first input port; 24-input side DC-AC converter; 25-an isolation transformer; 26-output side AC-DC converter; 27-a first output port; 28-a second input port; 29-a first passive leg; 30-a second output port; 31-second passive branch.
Detailed Description
The technical contents, structural features, attained objects and effects of the present invention are explained in detail below with reference to the accompanying drawings.
In a specific embodiment, as shown in fig. 1, the composite interleaved parallel DC converter circuit provided by the present invention includes a main DC/DC circuit 6, a ripple compensation circuit 3, and an energy compensation circuit 2, where the main DC/DC circuit 6, the ripple compensation circuit 3, and the energy compensation circuit 2 are all at least 1, an input port of the main DC/DC circuit 6 forms a total input port, a positive terminal of an output port of the main DC/DC circuit 6 is connected to a positive terminal of an output port of the ripple compensation circuit 3 to form a positive terminal 4 of the total output port, and a negative terminal thereof is connected to a negative terminal of the output port of the ripple compensation circuit 3 to form a negative terminal 5 of the total output port; the output port of the energy compensating circuit 2 is connected with the input port of the ripple compensating circuit 3, and the input voltage of the ripple compensating circuit 3 is maintained at a certain level U lower than the total input voltageref。
The main DC/DC circuit 6 comprises a first half-bridge circuit and a first filter inductor 10, wherein the number of the first half-bridge circuit and the number of the first filter inductor 10 are respectively 1; the first half-bridge circuit comprises a first semiconductor device 9 and a second semiconductor device 14, a first end of the first semiconductor device 9 forms a positive terminal 8 of the input port of the main DC/DC circuit, a second end of the first semiconductor device 9 is respectively connected with a first end of the second semiconductor device 14 and a first end of a first filter inductor 10, a second end of the second semiconductor device 14 forms a negative terminal 13 of the input port of the main DC/DC circuit and is a negative terminal 12 of the output port of the main DC/DC circuit, and a second end of the first filter inductor 10 forms a positive terminal 11 of the output port of the main DC/DC circuit. The main DC/DC circuit 6 may adopt a Buck circuit with unidirectional energy transmission according to the requirement of the application, that is, the first semiconductor device 9 is a fully-controlled semiconductor switching device, and the second semiconductor device 14 is a diode, as shown in fig. 3 a; alternatively, a Buck/Boost bidirectional converter with bidirectional energy transmission may be used, i.e., the first semiconductor device 9 is a fully-controlled semiconductor switching device, and the second semiconductor device 14 is a fully-controlled semiconductor switching device, as shown in fig. 3 b.
The ripple compensation circuit 3 comprises a second half-bridge circuit, a second filter inductor 17 and a blocking capacitor 18, wherein the number of the second half-bridge circuit, the second filter inductor 17 and the blocking capacitor 18 is 1; the second half-bridge circuit comprises a third semiconductor device 16 and a fourth semiconductor device 22, a first end of the third semiconductor device 16 forms a positive terminal 15 of an input port of the ripple compensation circuit, a second end of the third semiconductor device is connected with a first end of the fourth semiconductor device 22 and a first end of the second filter inductor 17 respectively, a second end of the fourth semiconductor device 22 forms a negative terminal 21 of the input port of the ripple compensation circuit and is a negative terminal 20 of an output port of the ripple compensation circuit, a first end of the blocking capacitor 18 is connected with a second end of the second filter inductor 17, and a second end of the blocking capacitor forms a positive terminal 19 of the output port of the ripple compensation circuit. As shown in fig. 4, the ripple compensation circuit 3 adopts a Buck/Boost bidirectional converter with bidirectional energy transmission, that is, the third semiconductor device and the fourth semiconductor device are all-controlled semiconductor switching devices, and a dc blocking capacitor is connected in series at the output end.
In this embodiment, as shown in fig. 5a, the energy compensating circuit 2 is an isolated DC/DC converting circuit, and includes a first input port 23, an input side DC-AC converter 24, an isolation transformer 25, an output side AC-DC converter 26, and a first output port 27, where the first input port 23 is connected to two sides of the blocking capacitor 18, and the first output port 27 is connected to the input port of the ripple compensating circuit 3.
In another aspect of the present invention, a control method using the aforementioned composite interleaved parallel DC converting circuit is provided, where for a composite interleaved parallel DC converting circuit including N main DC/DC circuits and 1 ripple compensating circuit, switching signals of the main DC/DC circuits and the ripple compensating circuit are generated in each control cycle by a control method, and a flowchart thereof is shown in fig. 6, where the control method includes the following steps:
s1, according to the control demand of the concrete application occasion, generating the duty ratio command D of each main DC/DC circuitk(k＝1～N)；
S2, carrying out carrier phase shift modulation to generate each switching signal of the main DC/DC circuit;
s21, respectively commanding duty ratio command D1～DNThe phase difference of the N phase is 2 pi/N, the minimum value is 0, the maximum value is 1, and the frequency is the switching frequency fsIf D is the triangular wave ofkIf the second semiconductor device is a full-control type switching device, executing step S24;
s22 switching function S of half-bridge of kth main DC/DC circuitkWhen the voltage is 1, the first semiconductor device is turned on;
s23 switching function S of half-bridge of kth main DC/DC circuitkWhen the value is 0, the first semiconductor device is turned off;
s24, the second semiconductor device is turned off when the first semiconductor device is turned on, and is turned on after the first semiconductor device is turned off.
S3, respectively detecting the input voltage u of each current main DC/DC circuitinAnd an output voltage uoBased on the current inductance current sum i of each main DC/DC circuitmainRate of change dimain/dt：
Figure BDA0003145381430000091
Wherein: l represents a first filter inductor of each main DC/DC circuit; skRepresenting a switching function of a first half-bridge circuit in a kth main DC/DC circuit;
s4, if dimain/dt>0, go to step S5; otherwise, executing step S6;
s5, turning on a fourth power semiconductor device of the ripple compensation circuit, turning off a third power semiconductor device of the ripple compensation circuit, and ending the period control;
and S6, turning off the fourth power semiconductor device of the ripple compensation circuit, turning on the third power semiconductor device of the ripple compensation circuit, and ending the period control.
As shown in fig. 7, when the energy compensating circuit is the isolated DC/DC converting circuit, the isolated DC/DC converting circuit is controlled in each control cycle through the following steps:
s71, sampling the voltage of the input end of the ripple compensation circuit;
s72, subtracting the sampling value obtained in S71 from the voltage reference value of the input end of the ripple compensation circuit to obtain a voltage control error;
and S73, obtaining a power instruction of the isolated DC/DC conversion circuit by the control error through the PI controller.
And S74, obtaining the switch control signals of the input side DC/AC circuit and the output side AC/DC circuit according to the relation between the power of the isolated DC/DC conversion circuit and the circuit switch control signals.
In another embodiment, as shown in fig. 2, the main DC/DC circuit 6 and the ripple compensation circuit 3 are the same as the previous embodiment, and the energy compensation circuit 2 is a passive voltage division circuit without a semiconductor switching device, as shown in fig. 5b, and includes a second input port 28, a first passive branch 29, a second output port 30, and a second passive branch 31, where the first passive branch 29 is connected in series with the second passive branch 31, one end of the first passive branch 29 connected in series with the second passive branch 30 forms a positive terminal of the second output port 30, and the other end of the first passive branch 29 connected in series with the second passive branch 30 forms a positive terminal of the second input port 28; the end of the second passive branch 31 not in series with the first passive branch 29 constitutes the negative terminal of the second input port 28 and is the negative terminal of the second output port 30; the first passive branch 29 and the second passive branch 31 are both formed by connecting a plurality of resistors in series or in parallel, or formed by connecting a plurality of capacitors in series or in parallel, or formed by connecting a plurality of resistors and capacitors in series or in parallel, or only comprise one resistor, or only comprise one capacitor, the first passive branch 29 is formed by connecting a resistor R1, the second passive branch 31 is formed by connecting a resistor R2 and a capacitor C2 in parallel, and the output voltage of the energy compensating circuit is equal to U through the voltage division function of the resistorsref. The second input port 28 is connected to the input port of the composite interleaved parallel dc converter circuit, and the second output port 30 is connected to the input port of the ripple compensation circuit 3.
The energy compensating circuit based on this embodiment does not need to be controlled, and the control method of the main DC/DC circuit and the ripple compensating circuit based on this embodiment is the same as that of the previous embodiment, and is not repeated.
The invention can be applied to the application occasions of direct current power supplies which need low voltage, large current and low ripple output characteristics, such as electrolytic hydrogen production, large-capacity battery energy storage systems and the like. Specific embodiments of the present invention are described below in conjunction with an electrolytic hydrogen production application scenario with access to a dc microgrid.
In the application scene, the hydrogen production direct-current power supply is required to be designed, the input of the hydrogen production direct-current power supply can be connected with a 1.5kV direct-current bus, the output of the hydrogen production direct-current power supply can provide about 400V voltage for an electrolytic cell for hydrogen production, the maximum output current is required to reach 1500A, and the ripple peak-to-peak value of the output current is required to be less than 10A.
If the above requirement is realized by adopting the first prior art scheme, i.e. the interleaved Buck circuit without ripple compensation, the circuit topology is as shown in fig. 8 a. The circuit comprises N Buck circuits which are connected in parallel in an interlaced mode, and each Buck circuit adopts carrier phase shift modulation, namely, the phase difference between carriers is 120 degrees. If the requirement of output current 1500A and withstand voltage 1.5kV is only needed, the requirement can be met by selecting the IGBT and the diode with the specification of 3300V/1000A and adopting 3 Buck circuits, for example, the British flying FD1000R33HE3 module (including the IGBT and the diode) can be selected, and the price is about $ 2211. According to journal article ALow-costMultiphase 3A Buck Converter With Improved Ripple Cancellation for Wide Supply Range, (Hafeez K T, DuttaA, Singh S G, et al 2016IEEE International Symposium on Circuits and Systems (ISCS), 2016:1618-o＝DuinI can be calculated by the following formulaoRipple peak-to-peak value delta Io：
Figure BDA0003145381430000111
The number N of Buck circuits is 3, and the input voltage uinWhen the duty ratio D is 400/1500 is 0.2667 at 1000V, the inductance L is 0.5mH, and the switching frequency f is assumed to bes1kHz, Δ I can be calculatedo160A. It can be seen that the requirement that the ripple current is less than 50A cannot be satisfied at this time. If the current ripple is further reduced, the number of branches N, the inductance L or the switching frequency is increasedThe magnitude of the rate. Increasing the switching frequency may result in a large increase in switching losses, which is undesirable. Therefore, if N is corrected to 4, L is made to be 2.5mH, and the switching frequency is not changed, Δ I can be calculatedo9.3A, meets the requirement. However, this is at the expense of increased number of branches and inductance, which increase the cost, volume and weight of the device. In the case of N-4 and L-2.5 mH, only IGBTs with a current rating of 3300V/1200A can be selected among currently available 3300V devices, despite the reduced branch currents. It can be seen that the unit price is not reduced, while the number of devices is increased by 33%; in addition, the inductance value of the inductor is increased to 5 times, and the cost and the volume are greatly increased.
If the above requirement is realized by adopting the second prior art scheme, i.e. the interleaved Buck circuit with ripple compensation, the circuit topology is as shown in fig. 8 b. In the figure, 3 Buck circuits which are connected in parallel in a staggered mode are used as a main DC/DC conversion circuit, a bidirectional Buck/Boost series blocking capacitor is used for forming a ripple compensation circuit, and the input end of the ripple compensation circuit is connected with the main DC/DC in parallel and is connected with a 1.5kV direct current bus. The main DC/DC conversion circuit part adopts devices with the same specification as the first scheme, namely 3300V/1000A IGBT and diode, and can meet the requirements of input voltage 1.5kV and output voltage 1500A. Output current i of the main DC/DC conversion circuit at this timemainSize of ripple Δ ImainIt can also be calculated according to equation (2), and can be obtained under the same parameters:
Figure BDA0003145381430000112
the output of the ripple compensation circuit and i can be enabled by controlling the ripple compensation circuitmainCurrent i with medium AC component in opposite phasecompCounteract imainSo that the final output current i fluctuatesoThe ripple of (2) is completely eliminated. The journal articles are described in journal articles A Low-cost Multi-phase 3A Buck Converter With Improved Ripple Cancellation for Wide Supply Range, (Hafeez K T, Dutta A, Singh S G, et al 2016IEEE International Symposium on Circuits and Systems (ISCS), 2016:1618-The scheme determines the switching signals of the ripple compensation circuit according to the switching signals of each main DC/DC circuit, but only provides a specific generation method under the condition that the main DC/DC circuit comprises 2 Buck circuits. Compared with the prior art, the ripple compensation branch is added, the IGBT half bridge used by the ripple compensation branch still needs to bear the high voltage of 1.5kV, a device with the rated voltage of 3300V needs to be adopted, and after looking up the product of the England flying IGBT half bridge module, the 3300V half bridge module which can be normally shipped currently has the generally higher rated current which is 450A at the minimum and the unit price of the module is 1470 dollar; and due to the main DC/DC output current imainOne switching period TsThe internal pulsation is 3 times, the switching frequency of the ripple compensation circuit is 3 times that of the main DC/DC circuit, and the switching period is TsAnd 3, which means that the switching frequency of the IGBT used by the ripple compensation circuit needs to reach 3 kHz.
On the other hand, according to the volt-second balance equation of the ripple compensation circuit inductance, and considering that the tube on time on the ripple compensation circuit should be imainThe fall time, is readily obtained:
ucc+uo＝(1-ND+floor(ND))uin (4)
wherein u iscc、uoRespectively representing the dc blocking capacitor voltage and the output voltage. From this, the ripple compensation current i can be determinedcompPeak to peak value Δ I ofcompComprises the following steps:
Figure BDA0003145381430000121
if it is required to fully compensate the ripple, let Δ Icomp＝ΔImainFrom the formulae (3) and (5), L is obviously requiredcL, i.e. the inductance of the compensation circuit must be equal to the filter inductance of the main DC/DC circuit.
In conclusion, the second technical scheme can completely eliminate harmonic waves and meet the requirements. On the basis of the prior art scheme I with N being 3, only one ripple compensation circuit with small power is added in the scheme; compared with the first prior art scheme of N-4, the device cost and the inductance size are obviously reduced. Therefore, the scheme is superior to the first technical scheme.
An implementation of the first embodiment of the present invention in the above application scenario is shown in fig. 9 a. The topology of the main DC/DC circuit and the ripple compensation circuit is consistent with the second technical scheme, and the difference is as follows: in the first embodiment of the invention, the input voltage of the ripple compensation circuit is not provided by a 1.5kV direct current bus, but is provided by an energy supplementing circuit formed by an isolated DC/DC circuit. The isolated DC/DC circuit adopts a double-active-bridge circuit, the input ends of the double-active-bridge circuit are connected to two sides of a blocking capacitor of the ripple compensation circuit, and the input voltage of the ripple compensation circuit can be controlled at u by implementing output voltage closed-loop control on the isolated DC/DC circuitin1＝uinThe specific control flow is shown in fig. 7 when the/5 is 300V.
In fig. 9a, the main DC/DC conversion circuit uses the same components and parameters as those in the second prior art, and also uses carrier phase shift control, and the output current ripple size is the same as that in the second prior art. In terms of control of the ripple compensation circuit, i is stillmainWhen the ripple compensation circuit is lowered, the upper tube of the ripple compensation circuit is switched on, and the upper tube is switched off; at imainAnd when the voltage rises, the upper tube of the ripple compensation circuit is turned off, and the lower tube is turned on. However, the specific control method is different from the second prior art in that the second prior art determines the switching state of the ripple circuit only according to the switching state of each main DC/DC conversion circuit, and a specific implementation method when the main DC/DC conversion circuit includes more than 3 Buck branches is not given, and the influence of the input voltage and the output voltage on the change rate of the output current of the main DC/DC circuit is not considered. The invention comprehensively considers the influence of the switch state, the input voltage and the output voltage of each main DC/DC conversion circuit and provides imainRate of change estimation:
Figure BDA0003145381430000131
if dimain/dt>0, switching on a lower tube and switching off an upper tube of the ripple compensation circuit; if dimainAnd the/dt is less than or equal to 0, the lower tube of the ripple compensation circuit is switched on, and the upper tube is switched off. The control method is suitable for the condition that N is equal to any value, and takes into considerationThe influence of input voltage and output voltage fluctuation is achieved.
In fig. 9a, the tube on time should be i according to the volt-second balance equation of the ripple compensation circuit inductance and considering that the tube on time should be imainThe fall time, is readily obtained:
ucc+uo＝(1-ND+floor(ND))uin1 (7)
can calculate to obtain icompPeak to peak ripple value Δ IcompComprises the following steps:
Figure BDA0003145381430000132
if it is required to fully compensate the ripple, let Δ Icomp＝ΔImainFrom the formulae (6) and (8), L is obviously requiredc＝(uin1/uin) L ═ (1/5) L, i.e., the inductance of the compensation circuit need only be equal to the filter inductance 1/5 of the main DC/DC circuit; further, according to the formula (3), u is easily obtainedcc-340V. Therefore, in the first embodiment of the scheme of the present invention, the input voltage of the energy compensation circuit, that is, the voltage of the blocking capacitor is 340V; the output voltage of the energy compensation circuit, namely the input voltage of the ripple compensation circuit, is 300V. Therefore, the switching devices of the power compensation circuit and the ripple compensation circuit do not need to bear 1.5kV voltage, and devices with lower rated voltage, such as 650V/300A half-bridge module, can be used, and the unit price is about $ 130; the total IGBT cost for the power up circuit and the ripple compensation circuit is about $ 650, which is only half that of the second prior art solution.
It can be seen that the first embodiment of the present invention can completely eliminate the output current ripple as in the second prior art. Although the first embodiment of the invention adopts more devices than the second technical scheme, the first embodiment of the invention does not need to bear 1.5kV high voltage, so that cheap low-voltage devices can be adopted; the inductance value of the ripple compensation circuit in the first embodiment of the invention is only 1/5 in the second technical scheme, thus further reducing the cost, volume and weight; the energy compensating circuit of the first embodiment of the invention is easy to realize high frequency, so the volume increase is not large; the reduction of the voltage level also greatly reduces the switching loss; moreover, the energy compensating circuit can adopt a soft switching technology, and the loss is not high. Therefore, the cost, volume, weight and loss of the invention are all better than those of the second technical proposal.
An implementation of the second embodiment of the present invention in the above application scenario is shown in fig. 9 b. The topology of its main DC/DC circuit and ripple compensation circuit is consistent with the first embodiment of the present invention, with the difference that: in the second embodiment of the invention, the input voltage of the ripple compensation circuit is provided by an energy compensation circuit consisting of a passive voltage division circuit without a semiconductor switching device. The passive voltage division circuit adopts a resistor and capacitor voltage division network, and the input end of the passive voltage division circuit is connected with a 1.5kV direct current bus. In fig. 9b, the passive voltage divider network parameters are: r1 ═ 4k Ω, R2 ═ 1k Ω, and C2 ═ 400 μ F. The input voltage of the ripple compensation circuit can be stabilized at u through the action of resistance voltage divisionin1＝uin/5＝300V。
In fig. 9b, the main DC/DC conversion circuit and the ripple compensation circuit all use the same devices, parameters and control methods as those of the embodiment of the present invention. According to the foregoing analysis, the second embodiment of the present invention can completely eliminate the output current ripple as the first embodiment of the present invention, and the semiconductor devices of the ripple compensation circuit do not need to bear the high voltage of 1.5kV, and the inductance of the ripple compensation circuit is only 1/5 of the second prior art. Although the input of the energy compensating circuit of the second embodiment of the invention is connected with the 1.5kV direct current bus, no semiconductor power device is adopted, and the manufacturing cost of the divider resistor is lower. Therefore, the second embodiment of the present invention is lower in cost than the first embodiment of the present invention, but the voltage dividing resistor of the second embodiment of the present invention needs to consume a certain amount of power.
In summary, the two embodiments of the present invention have advantages over the prior art in terms of cost and size, since the ripple compensation circuit is not implemented by using high voltage semiconductor devices and the size of the filter inductor is reduced.
Compared with the traditional staggered parallel DC/DC converter without the compensation branch, the composite staggered parallel DC/DC conversion circuit provided by the invention can adopt fewer staggered parallel DC-DC units under the same output current ripple index, and can theoretically completely eliminate the output current ripple, thereby reducing the inductance value of the filter inductor and being suitable for occasions with extremely high requirements on the current ripple; the switching frequency of the interleaved parallel DC/DC circuit can be reduced, so that a main DC/DC circuit can be formed by adopting a low-frequency switching device with higher power level, smaller on-state loss and higher switching loss, a ripple compensation circuit is formed by adopting a high-frequency switching device with lower power level, smaller switching loss and higher on-state loss, the advantages of different devices are exerted, and the optimization of loss and cost is realized under the same performance; because the number of the main DC/DC circuits is reduced, the control and sampling systems can be greatly simplified, the number of sensors is reduced, the operation time of a control algorithm is saved, and the cost and the realization difficulty are reduced. In addition, compared with the traditional staggered parallel DC/DC converter with the compensation branch, the ripple compensation circuit does not need to adopt a high-price switching device with high voltage withstanding capability, so that the cost is saved; the voltage resistance of the ripple compensation circuit is reduced, so that the switching loss is reduced, and the efficiency of the device is improved; under the condition of reasonable design, the reduction of the input voltage of the ripple compensation circuit can reduce the peak value of the filter inductance voltage, thereby reducing the required inductance value and reducing the volume of the device.
The above-mentioned embodiments are merely illustrative of the preferred embodiments of the present invention, and do not limit the scope of the present invention, and various modifications and improvements made to the technical solution of the present invention by those skilled in the art without departing from the spirit of the present invention shall fall within the protection scope defined by the claims of the present invention.

Claims (8)

1. A composite type staggered parallel direct current conversion circuit is characterized by comprising a main DC/DC circuit, a ripple compensation circuit and an energy supplementing circuit, wherein an input port of the main DC/DC circuit forms a total input port, a positive terminal of an output port of the main DC/DC circuit is connected with a positive terminal of an output port of the ripple compensation circuit to form a positive terminal of the total output port, and a negative terminal of the ripple compensation circuit is connected with a negative terminal of the output port of the ripple compensation circuit to form a negative terminal of the total output port; the output port of the energy compensating circuit is connected with the input port of the ripple compensating circuitThen, the input voltage of the ripple compensation circuit is maintained at a certain level U lower than the total input voltageref，
The main DC/DC circuit comprises a first half-bridge circuit and a first filter inductor, the first half-bridge circuit comprises a first semiconductor device and a second semiconductor device, a first end of the first semiconductor device forms a positive terminal of the input port of the main DC/DC circuit, a second end of the first semiconductor device is respectively connected with a first end of the second semiconductor device and a first end of the first filter inductor, a second end of the second semiconductor device forms a negative terminal of the input port of the main DC/DC circuit and is a negative terminal of the output port of the main DC/DC circuit, and a second end of the first filter inductor forms a positive terminal of the output port of the main DC/DC circuit;
the ripple compensation circuit comprises a second half-bridge circuit, a second filter inductor and a blocking capacitor, the second half-bridge circuit comprises a third semiconductor device and a fourth semiconductor device, a first end of the third semiconductor device forms a positive terminal of an input port of the ripple compensation circuit, a second end of the third semiconductor device is respectively connected with a first end of the fourth semiconductor device and a first end of the second filter inductor, a second end of the fourth semiconductor device forms a negative terminal of the input port of the ripple compensation circuit and is a negative terminal of an output port of the ripple compensation circuit, a first end of the blocking capacitor is connected with a second end of the second filter inductor, and a second end of the blocking capacitor forms a positive terminal of the output port of the ripple compensation circuit;
the energy supplementing circuit is an isolated DC/DC conversion circuit or a passive voltage dividing circuit without a semiconductor switch device.
2. The composite type interleaved parallel direct current conversion circuit according to claim 1, wherein when the energy compensating circuit is an isolated DC/DC conversion circuit, the energy compensating circuit comprises a first input port, an input side DC-AC converter, an isolation transformer, an output side AC-DC converter, and a first output port, the first input port is connected to both sides of the blocking capacitor, and the first output port is connected to the ripple compensation circuit input port.
3. The composite type interleaved parallel direct current conversion circuit according to claim 1, wherein when the energy compensating circuit is a passive voltage dividing circuit, the energy compensating circuit comprises a second input port, a first passive branch, a second passive branch and a second output port, the first passive branch and the second passive branch are connected in series, one end of the first passive branch and one end of the second passive branch connected in series form a positive terminal of the second output port, and the other end of the first passive branch and the second passive branch form a positive terminal of the second input port; the end of the second passive branch not connected with the first passive branch in series forms a negative terminal of a second input port and is a negative terminal of a second output port; the first passive branch and the second passive branch are both formed by connecting a plurality of resistors in series or in parallel, or formed by connecting a plurality of capacitors in series or in parallel, or formed by connecting a plurality of resistors and capacitors in series or in parallel, or only comprise one resistor, or only comprise one capacitor; the second input port is connected to the input port of the composite type interleaving parallel direct current conversion circuit, and the second output port is connected to the input port of the ripple compensation circuit.
4. A composite interleaved parallel dc converter circuit according to claim 1 wherein said first, third and fourth semiconductor devices are fully controlled semiconductor switching devices and said second semiconductor device is a fully controlled semiconductor switching device or a diode.
5. The composite interleaved parallel Direct Current (DC) conversion circuit of claim 1, wherein the number of the main DC/DC circuit, the ripple compensation circuit and the energy compensation circuit is at least 1; the number of the first half-bridge circuit and the number of the first filter inductor are respectively 1; and the number of the second half-bridge circuit, the second filter inductor and the blocking capacitor is 1.
6. A control method using the composite interleaved parallel DC converting circuit according to any one of claims 1 to 5, wherein for the composite interleaved parallel DC converting circuit including N main DC/DC circuits and 1 ripple compensating circuit, switching signals of the main DC/DC circuits and the ripple compensating circuit are generated by a control method at each control cycle, the control method comprising the steps of:
s1, according to the control demand of the concrete application occasion, generating the duty ratio command D of each main DC/DC circuitk(k＝1～N)；
S2, carrying out carrier phase shift modulation to generate each switching signal of the main DC/DC circuit;
s3, respectively detecting the input voltage u of each current main DC/DC circuitinAnd an output voltage uoBased on the current inductance current sum i of each main DC/DC circuitmainRate of change dimain/dt：
Figure FDA0003145381420000021
Wherein: l represents a first filter inductor of each main DC/DC circuit; skRepresenting a switching function of a first half-bridge circuit in a kth main DC/DC circuit;
s4, if dimain/dt>0, go to step S5; otherwise, executing step S6;
s5, turning on a fourth power semiconductor device of the ripple compensation circuit, turning off a third power semiconductor device of the ripple compensation circuit, and ending the period control;
and S6, turning off the fourth power semiconductor device of the ripple compensation circuit, turning on the third power semiconductor device of the ripple compensation circuit, and ending the period control.
7. The method of claim 6, wherein the step S2 specifically includes the following steps:
s21, respectively commanding duty ratio command D1～DNThe phase difference of the N phase is 2 pi/N, the minimum value is 0, the maximum value is 1, and the frequency is the switching frequency fsIf D is the triangular wave ofkIf the second semiconductor device is larger than the kth triangular wave, executing step S22, otherwise executing step S23, if the second semiconductor device is fully-controlled onIf the device is turned off, step S24 is executed;
s22 switching function S of half-bridge of kth main DC/DC circuitkWhen the voltage is 1, the first semiconductor device is turned on;
s23 switching function S of half-bridge of kth main DC/DC circuitkWhen the value is 0, the first semiconductor device is turned off;
s24, the second semiconductor device is turned off when the first semiconductor device is turned on, and is turned on after the first semiconductor device is turned off.
8. The method for controlling a composite interleaved parallel Direct Current (DC) conversion circuit according to claim 6, further comprising controlling the isolated DC/DC conversion circuit in each control cycle by:
s71, sampling the voltage of the input end of the ripple compensation circuit;
s72, subtracting the sampling value obtained in S71 from the voltage reference value of the input end of the ripple compensation circuit to obtain a voltage control error;
s73, obtaining a power instruction of the isolated DC/DC conversion circuit by the control error through a PI controller;
and S74, obtaining the switch control signals of the input side DC/AC circuit and the output side AC/DC circuit according to the relation between the power of the isolated DC/DC conversion circuit and the circuit switch control signals.
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Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114301279A (en) * 2021-12-16 2022-04-08 河北建投新能源有限公司 Switch modulation method and device of boost converter
CN114337278A (en) * 2021-12-16 2022-04-12 河北建投新能源有限公司 Method and device for modulating switch of converter, storage medium and electronic equipment
CN117614256A (en) * 2024-01-24 2024-02-27 西北工业大学 Input current ripple optimization method after floating interleaved converter faults

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103441659A (en) * 2013-09-18 2013-12-11 矽力杰半导体技术(杭州)有限公司 Control circuit applied to interlaced parallel switching power supply
CN208707520U (en) * 2018-07-27 2019-04-05 珠海九源电力电子科技有限公司 DC bus ripple compensation device
CN110690812A (en) * 2019-09-02 2020-01-14 华为技术有限公司 Current compensation method, power decoupling circuit and power converter system
CN111371297A (en) * 2020-03-11 2020-07-03 杭州电子科技大学 Current ripple compensation circuit and method adopting wide bandgap device and silicon-based device
CN111869069A (en) * 2018-01-15 2020-10-30 金斯顿女王大学 Power-controlled capacitor circuit and control method thereof
CN112821792A (en) * 2021-02-23 2021-05-18 湖南大学 Double-frequency staggered hybrid half-bridge circuit and control method thereof

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103441659A (en) * 2013-09-18 2013-12-11 矽力杰半导体技术(杭州)有限公司 Control circuit applied to interlaced parallel switching power supply
CN111869069A (en) * 2018-01-15 2020-10-30 金斯顿女王大学 Power-controlled capacitor circuit and control method thereof
CN208707520U (en) * 2018-07-27 2019-04-05 珠海九源电力电子科技有限公司 DC bus ripple compensation device
CN110690812A (en) * 2019-09-02 2020-01-14 华为技术有限公司 Current compensation method, power decoupling circuit and power converter system
CN111371297A (en) * 2020-03-11 2020-07-03 杭州电子科技大学 Current ripple compensation circuit and method adopting wide bandgap device and silicon-based device
CN112821792A (en) * 2021-02-23 2021-05-18 湖南大学 Double-frequency staggered hybrid half-bridge circuit and control method thereof

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
杜雄等: "直流侧APF主电路参数与补偿性能的关系", 《中国电机工程学报》 *

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114301279A (en) * 2021-12-16 2022-04-08 河北建投新能源有限公司 Switch modulation method and device of boost converter
CN114337278A (en) * 2021-12-16 2022-04-12 河北建投新能源有限公司 Method and device for modulating switch of converter, storage medium and electronic equipment
CN114301279B (en) * 2021-12-16 2024-01-09 河北建投新能源有限公司 Switch modulation method and device of boost converter
CN114337278B (en) * 2021-12-16 2024-04-23 河北建投新能源有限公司 Switching modulation method and device of converter, storage medium and electronic equipment
CN117614256A (en) * 2024-01-24 2024-02-27 西北工业大学 Input current ripple optimization method after floating interleaved converter faults
CN117614256B (en) * 2024-01-24 2024-03-22 西北工业大学 Input current ripple optimization method after floating interleaved converter faults

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