CN113507214A - Three-active-bridge converter power decoupling phase-shifting control and current effective value optimization method - Google Patents

Three-active-bridge converter power decoupling phase-shifting control and current effective value optimization method Download PDF

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CN113507214A
CN113507214A CN202110654523.8A CN202110654523A CN113507214A CN 113507214 A CN113507214 A CN 113507214A CN 202110654523 A CN202110654523 A CN 202110654523A CN 113507214 A CN113507214 A CN 113507214A
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port
effective value
phase shift
current effective
value
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CN113507214B (en
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肖凡
涂春鸣
罗莹超
陈堃
刘贝
郭祺
胡兴洋
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Hunan University
Electric Power Research Institute of State Grid Hubei Electric Power Co Ltd
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Hunan University
Electric Power Research Institute of State Grid Hubei Electric Power Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33561—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having more than one ouput with independent control

Abstract

The three-active-bridge converter power decoupling phase-shifting control and current effective value optimization method comprises the following steps: (1) setting the requirements 2D for power decoupled phase-shift control4+D2＝2D5+D3(ii) a (2) Setting the precision Delta D of each phase shift ratio, and taking the numerical value of each phase shift ratio meeting the precision requirement; (3) screening the phase comparison values meeting the requirements through a constraint function; (4) calculating the square sum of the transmission power and the current effective value of each port; (5) collecting actual transmission power, and screening a numerical value of transmission power of each port, a phase shift comparison numerical value and a current effective value square sum numerical value which accord with an allowable error delta P; (6) finding the least current effective value square sum and the corresponding phase shift ratio D2、D3、D4(ii) a (7) And generating PWM control signals for controlling the on-off of the switch tubes of the ports. Hair brushThe control freedom degree of the converter is obviously improved, and the transmission power range of each port is ensured; the minimum current effective value control is realized, and the operation efficiency of the converter is improved.

Description

Three-active-bridge converter power decoupling phase-shifting control and current effective value optimization method
Technical Field
The invention relates to the technical field of power electronic control, in particular to a method for power decoupling phase shift control and current effective value optimization of a three-active-bridge converter.
Background
The direct-current power distribution network has no problems of reactive fluctuation, harmonic degradation, frequency fluctuation, synchronous oscillation and the like, has a plurality of advantages compared with an alternating-current power distribution network, and is an effective way for distributed power consumption. The direct current transformer is used as core equipment of a direct current distribution network, and has important significance for the direct current distribution network in efficient and reliable operation. The existing direct current transformer mostly adopts a two-port topological structure, and a plurality of two-port direct current transformers need to be equipped when a direct current power distribution network carries out multi-voltage grade energy conversion. The co-operation of a plurality of direct current transformers not only increases the energy conversion times and the construction cost, but also generates circulation among ports, thereby causing great difficulty in coordination control and reducing the stability of the system. The problem can be effectively solved by adopting a multi-port direct current transformer to replace a plurality of two-port direct current transformers.
In a multi-port direct current transformer topological structure, a Three-Active Bridge (TAB) converter has higher research value and application potential due to the advantages of electrical isolation, wide voltage range, flexible and controllable power flow direction and the like. The three active bridge converters are used as important power units in the direct-current power distribution network, and the better energy coordination and energy conversion efficiency among the ports of the three active bridge converters have great significance to the direct-current power distribution network. However, under the control of the conventional Single Phase Shift (SPS), the Phase difference between the input and output ports of the three-active-bridge converter can cause generation of coupling power, and the generation of the coupling power can enhance the interaction between the ports, increase the voltage fluctuation of the ports in a dynamic process, and influence the dynamic performance of the converter. In addition, the single phase-shift control is limited by the control freedom degree, and the inductive current cannot be controlled, so that the problem of large effective current value in the operation process of the converter exists, and the operation efficiency of the converter is low. Therefore, when the operation efficiency of the three active bridge converters is optimized and improved, the control method capable of simultaneously realizing decoupling between the converter ports and current effective value optimization is selected, and the control method has very important significance for reducing the operation loss of the three active bridge converters.
Disclosure of Invention
The technical problem to be solved by the invention is to overcome the defects of the background technology, and provide a method for power decoupling phase shift control and current effective value optimization of a three-active-bridge converter, thereby improving the control freedom of the three-active-bridge converter and ensuring the transmission power range of each port; power coupling between input ports or output ports is eliminated, and mutual influence between the ports is eliminated; the minimum current effective value mode selection mode based on power decoupling phase shifting is determined, the minimum current effective value control of the three-active-bridge converter is realized, and the operation efficiency of the three-active-bridge converter is improved.
The invention solves the technical problem by adopting the technical scheme that a three-active-bridge converter power decoupling phase-shifting control and current effective value optimization method comprises the following steps:
(1) setting the necessary condition of power decoupling phase shift control, wherein the necessary condition is 2D4+D2＝2D5+D3；D2Is an AC side voltage square wave v of port twoH2D is a shift in phase3Is the AC side voltage square wave v of port threeH3D is a shift in phase4Is the outward shift ratio of one and two ports, D5Is the ratio of outward displacement between port one and port three;
(2) setting the precision delta D of each phase shift, and taking the value of each phase shift meeting the precision requirement;
(3) screening the phase comparison values meeting the requirements through a constraint function;
(4) calculating the square sum of the transmission power and the current effective value of each port;
(5) acquiring actual transmission power, determining an allowable error delta P of the power, and screening a numerical value of transmission power of each port, a numerical value of phase shift ratio of each port and a square sum of effective current values which meet requirements by taking the allowable error delta P as a constraint condition;
(6) finding the least current effective value square sum and the corresponding phase shift ratio D2、D3、D4；
(7) And generating PWM control signals for controlling the on-off of the switch tubes of the ports.
Further, the specific process of the step (2) is as follows:
setting the precision DeltaD of a phase shift ratio D, including D, according to the period counter value of a DSP controller2、D3、D4、D5D is more than or equal to the phase shift ratio of 0 and less than or equal to 1 under the constraint conditions of accuracy delta D2All values meeting the conditions are taken and stored in an array D2[l]，D3All values meeting the conditions are taken and stored in an array D3[l]，D4All values meeting the conditions are taken and stored in an array D4[l]。
Further, the specific process of the step (3) is as follows:
setting constraint function screening array D2[l]、D3[l]、D4[l](ii) a Constraint function of Fk(D) Not less than 0, wherein
Figure BDA0003112074280000031
By a constraint function Fk(D) Screening for more than or equal to 0 to obtain an array D2[m]、D3[m]、D4[m]。
Further, the specific process of the step (4) is as follows:
calculating to obtain the transmission power P of the second port according to the transmission power expression of each port and the current effective value square sum expression2Transmission power P of port three3And current effectiveSum of squared values Σ Irms 2Storing the calculated transmission power value of the second port into the array P2*[m]Storing the calculated transmission power value of a group of ports III into an array P3*[m]Storing the calculated sum of squares of the effective current values into an array Σ Irms 2[m]。
Further, in the step (4), the transmission power expression and the current effective value square sum expression of each port are as follows:
Figure BDA0003112074280000041
Figure BDA0003112074280000042
wherein: intermediate variables
Figure BDA0003112074280000043
Figure BDA0003112074280000044
Figure BDA0003112074280000045
V1Is the DC side voltage of port one, V2Is the DC side voltage of port two, V3Is the DC side voltage of the port three, and the transformation ratio of the three-winding high-frequency transformer is N1/N2/N3，n12＝N1/N2、n13＝N1/N3，V2' converting the DC side voltage of port two to the value of port one, V3' converting the DC side voltage at port three to the value at port one, V2'＝n12V2、V3'＝n13V3；L1Equivalent inductance of port one, L2Equivalent inductance of port two, L3Equivalent inductance of port three, L2' converting the equivalent inductance of port two to the value of port one, L3' converting the equivalent inductance of Port three to the value of Port one, L2'＝n12 2L2、L3'＝n13 2L3；
Figure BDA0003112074280000051
The effective value of the current of the port one;
Figure BDA0003112074280000052
the effective value of the current of the port II is;
Figure BDA0003112074280000053
the effective value of the current of the port three; l is12Is the equivalent inductance parameter of the first port and the second port; l is13Is the equivalent inductance parameter of port one and three; l is23Is the equivalent inductance parameter of port two and port three.
Further, the specific process of the step (5) is as follows:
acquiring actual transmission power P of a second port of the three-active-bridge converter under a given working condition2NAnd actual transmission power P of port three3NDetermining the allowable error delta P of the power according to the sampling precision, and eliminating the array P by taking the allowable error delta P as a constraint condition2*[m]、P3*[m]The value which is not qualified in the range is obtained to obtain the array P in the allowable error range delta P2*[i]、P3*[i]According to the array P2*[i]、P3*[i]And (1) eliminating the array D2[m]、D3[m]、D4[m]Obtaining new array D from the value not meeting the requirement2[i]、D3[i]、D4[i](ii) a According to array D2[i]、D3[i]、D4[i]And formulas (2), (3), (4) and (5), removing the arrays Σ Irms 2[m]Obtaining new array sigma I by using the numerical value which does not meet the requirementrms 2[i]。
Further, the specific process of the step (6) is as follows:
for array Σ Irms 2[i]Optimizing numerical value to obtain the minimum current effective value square sum min (Sigma I) of the three-active-bridge converter under the given working conditionrms 2) And obtaining a minimum current effective value sum of squares min (∑ I)rms 2) Lower corresponding phase shift ratio D2、D3、D4。
Further, in the step (7), the sum of squared minimum current effective values min (Σ I) is obtainedrms 2) And corresponding phase shift ratio D2、D3、D4And generating PWM control signals for controlling the on-off of the switch tubes of the ports.
Compared with the prior art, the invention has the following advantages:
according to the invention, the small signal model, the parameter precision and the like of the three-active-bridge converter are not considered, and the power decoupling is directly carried out on two output ports (port two and port three) of the three-active-bridge converter; the control freedom degree of the three-active-bridge converter is increased, and the power decoupling is realized, and meanwhile, the transmission power range of the three-active-bridge converter can be ensured; by utilizing the power decoupling phase-shifting control, the current effective value in the running process of the three-active-bridge converter can be optimized while the power decoupling between the ports is realized, and the running efficiency of the three-active-bridge converter is improved.
Drawings
Fig. 1 is a topology of a three-active bridge converter of an embodiment of the present invention.
Fig. 2 is an internal power flow diagram of a three-active-bridge converter of an embodiment of the present invention.
Fig. 3 is a schematic diagram of the connection between the DSP controller and the three-active-bridge converter according to the embodiment of the present invention.
Fig. 4 is a square wave diagram of the voltage of each port under the control of power decoupling and phase shifting according to the embodiment of the present invention.
Fig. 5 is a flowchart of the minimum current effective value control of a three-active-bridge converter based on power decoupling phase shift control according to an embodiment of the present invention.
Fig. 6 is a control diagram of a three-active-bridge converter to realize current effective value optimization according to an embodiment of the invention.
Fig. 7 is a graph of the load switching result under the conventional single phase shift control method.
Fig. 8 is a diagram of a load switching result under power decoupling phase shift control according to an embodiment of the present invention.
Fig. 9 is a diagram of the optimization effect of current effective values with different voltage modulation ratios under the control of power decoupling and phase shifting in the embodiment of the present invention.
Fig. 10 is a waveform diagram of the inductor current of each port under the prior art single phase shift control method.
FIG. 11 is a waveform diagram of the inductive current of each port under the control of power decoupling and phase shifting in the embodiment of the present invention.
Detailed Description
The present invention will be described in further detail with reference to the drawings and specific embodiments, and it should be understood that the described embodiments are only a few, but not all, embodiments of the present invention. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
The topological structure of the three-active-bridge converter is composed of a three-winding high-frequency transformer, three H-bridge power units and three direct-current side capacitors C as shown in figure 11、C2、C3And three port equivalent inductance L1、L2、L3And (4) forming. V in FIG. 11Is the DC side voltage of port one, V2Is the DC side voltage of port two, V3Is the DC side voltage of the port three, and the transformation ratio of the three-winding high-frequency transformer is N1/N2/N3，n12＝N1/N2、n13＝N1/N3，vH1Is an alternating side voltage square wave of port one, vH2Is an AC side voltage square wave of port two, vH3Is a square wave of the AC side voltage of port three, and the single phase shift control is realized by changing vH1、vH2、vH3The phase difference of (2) adjusts the magnitude and direction of the transmission power among the three ports.
The invention adopts the DSP controller to control the three-active-bridge converter, and realizes the power decoupling phase-shifting control and the current effective value optimization of the three-active-bridge converter. The connection relationship between the DSP controller and the three-active-bridge converter is shown in fig. 2. The DSP controller is connected with the direct current sides of the ports of the three active bridge converters through the acquisition conditioning circuit, and generates PWM control signals through a closed-loop control program after acquiring signals of the ports. The software part is realized in a CCS8.0 programming environment, the DSP controller is connected with the CCS of the computer end through an emulator, and a closed-loop control program is downloaded to the DSP controller through the emulator to realize debugging and programming. The DSP controller is connected with the switch tubes of the ports of the three active bridge converters through a driving circuit, and drives the switch tubes to be switched on and off through PWM signals.
The power decoupling phase-shifting control is based on single phase-shifting control, and adds an internal shift ratio to the voltage square waves of the two output ports, so that no power flows between the ports by controlling the center lines of the voltage square waves of the two ports to be superposed. The internal power flow of the three-active-bridge converter under the power decoupling phase-shifting control is shown in fig. 3, and can be regarded as the power superposition of two-port converters. FIG. 4 is a diagram of voltage square waves of each port when lines of voltage square waves of the ports of a three-active-bridge converter coincide, and a necessary condition for realizing a power decoupling phase-shifting control strategy is that the port phase-shifting is compared with 2D4+D2＝2D5+D3，D2Is an AC side voltage square wave v of port twoH2D is a shift in phase3Is the AC side voltage square wave v of port threeH3D is a shift in phase4Is the outward shift ratio of one and two ports, D5Is the ratio of the outward shift between port one and port three.
A three-active-bridge converter power decoupling phase-shifting control and current effective value optimization method is shown in figure 5 and specifically comprises the following steps:
step 1: setting the necessary condition of power decoupling phase shift control, wherein the necessary condition is 2D4+D2＝2D5+D3；
Step 2: setting the precision DeltaD of a phase shift ratio D, including D, according to the period counter value of a DSP controller2、D3、D4、D5D is more than or equal to the phase shift ratio of 0 and less than or equal to 1 under the constraint conditions of accuracy delta D2All values meeting the conditions are taken and stored in an array D2[l]，D3All values meeting the conditions are taken and stored in an array D3[l]，D4All values meeting the conditions are taken and stored in an array D4[l]；D5Can be according to formula 2D4+D2＝2D5+D3Calculating to obtain;
and step 3: setting constraint function screening array D2[l]、D3[l]、D4[l](ii) a Constraint function of Fk(D) Not less than 0, wherein
Figure BDA0003112074280000091
By a constraint function Fk(D) Screening for more than or equal to 0 to obtain an array D2[m]、D3[m]、D4[m]；Fk(D) The constraint condition that the three active bridge converters work in a mode with the minimum current effective value is adopted;
and 4, step 4: calculating according to the transmission power expression (1) of each port and the square sum expressions (2), (3), (4) and (5) of the current effective value to obtain the transmission power P of the second port2Transmission power P of port three3Sum of squares of current effective values Σ Irms 2Storing the calculated transmission power value of the second port into the array P2*[m]Storing the calculated transmission power value of a group of ports III into an array P3*[m]Storing the calculated sum of squares of the effective current values into an array Σ Irms 2[m]；
Figure BDA0003112074280000092
Figure BDA0003112074280000093
Wherein: intermediate variables
Figure BDA0003112074280000094
Figure BDA0003112074280000101
Figure BDA0003112074280000102
V2' converting the DC side voltage of port two to the value of port one, V3' converting the DC side voltage at port three to the value at port one, V2'＝n12V2、V3'＝n13V3；L2' converting the equivalent inductance of port two to the value of port one, L3' converting the equivalent inductance of Port three to the value of Port one, L2'＝n12 2L2、L3'＝n13 2L3；
Figure BDA0003112074280000103
The effective value of the current of the port one;
Figure BDA0003112074280000104
the effective value of the current of the port II is;
Figure BDA0003112074280000105
the effective value of the current of the port three; l is12Is the equivalent inductance parameter of the first port and the second port; l is13Is the equivalent inductance parameter of port one and three; l is23Is the equivalent inductance parameter of port two and port three. The current effective value expression is derived by high-frequency Fourier series decomposition, and consists of components with different frequencies, wherein n is 1,3,5 ….
And 5: acquiring actual transmission power P of a second port of the three-active-bridge converter under a given working condition2NAnd actual transmission power P of port three3NDetermining the allowable error delta P of the power according to the sampling precision, and eliminating the array by taking the allowable error delta P as a constraint conditionP2*[m]、P3*[m]The value which is not qualified in the range is obtained to obtain the array P in the allowable error range delta P2*[i]、P3*[i]According to the array P2*[i]、P3*[i]And (1) eliminating the array D2[m]、D3[m]、D4[m]Obtaining new array D from the value not meeting the requirement2[i]、D3[i]、D4[i](ii) a According to array D2[i]、D3[i]、D4[i]And formulas (2), (3), (4) and (5), removing the arrays Σ Irms 2[m]Obtaining new array sigma I by using the numerical value which does not meet the requirementrms 2[i]；
Step 6: for array Σ Irms 2[i]Optimizing numerical value to obtain the minimum current effective value square sum min (Sigma I) of the three-active-bridge converter under the given working conditionrms 2) And obtaining a minimum current effective value sum of squares min (∑ I)rms 2) Lower corresponding phase shift ratio D2、D3、D4；
And 7: as shown in fig. 6, the minimum current effective value sum of squares min (Σ I) is obtainedrms 2) And corresponding phase shift ratio D2、D3、D4And generating PWM control signals for controlling the on-off of the switch tubes of the ports.
The three-active-bridge converter works under the existing single phase-shift control, and the voltage waveform of the direct current side of each port when the two ports are switched is shown in fig. 7. At time t-0.8 s, the port two load suddenly increases, resulting in a port voltage V2Sag, port voltage V3Rises under the influence of coupled power; at time t-1.6 s, the port two load suddenly decreases, resulting in a port voltage V2Rising, port voltage V3Falls off under the influence of the coupled power. The three-active-bridge converter works under the power decoupling phase-shifting control, and the voltage waveform of the direct current side of each port when the two-port load is switched is as shown in fig. 8. At time t-0.8 s, the port two load suddenly increases, resulting in a port voltage V2Sag, port voltage V3Keeping 500V unchanged; at the moment t is 1.6s, the load of the port two is suddenly reduced, so that the port is electrifiedPressure V2Rising, port voltage V3Keeping 500V unchanged. Comparing fig. 7 and 8, it can be known that the three-active-bridge converter works under the power decoupling phase-shifting control, and when the voltage of the second port fluctuates, the third port is not affected, so that the effectiveness of the power decoupling phase-shifting control for eliminating the coupling power between the ports is verified.
In fig. 9, (a) to (c) are voltage modulation ratios (voltage ratio k of port one to port two)12And the voltage ratio k of port one to port three13) When k is equal to 0.4, P is respectively taken as the three transmission powers of the port3 *The effective value of the decoupling phase-shifting control current is optimized under the working conditions of 0.4, 0.6 and 0.8; (d) "f" is the voltage modulation ratio (voltage ratio k of port one to port two)12And the voltage ratio k of port one to port three13) When k is equal to 0.6, P is respectively taken as the three transmission powers of the port3 *The effective value of the decoupling phase-shifting control current is optimized under the working conditions of 0.4, 0.6 and 0.8; (g) (ii) is the voltage modulation ratio (voltage ratio k of port one to port two)12And the voltage ratio k of port one to port three13) When k is equal to 0.8, P is respectively taken as the three transmission powers of the port3 *Under the working conditions of 0.4, 0.6 and 0.8, the effective value of the decoupling phase-shifting control current is optimized. As can be seen from a transverse comparison of fig. 9, the three-active-bridge converter has a better optimization effect on the current effective value working in the medium-low power range and a larger optimization range under the power decoupling phase-shifting control; as can be seen from the longitudinal comparison of fig. 9, when the three-active-bridge converter operates under the working condition of smaller voltage modulation ratio under the control of power decoupling and phase shifting, the current effective value has a better optimization effect and a larger optimization range. Therefore, compared with the existing single phase-shift control strategy, the power decoupling phase-shift has certain optimization effect on the current effective value of the three-active-bridge converter, and the voltage modulation ratio k is12、k13And when the working condition of medium and low power is smaller, the optimized power range is larger, and the current effective value optimization effect is better.
The waveforms of the inductive currents at the ports of the three-active-bridge converter under the single-phase-shift control are shown in FIG. 10, where the sum of the squares of the effective current values at the three ports is Irms1 2＝1.23kA2. Under the control of power decoupling and phase shiftingThe waveforms of the inductive currents at the ports of the three-active-bridge converter are shown in FIG. 11, where the sum of the squares of the effective current values at the three ports is Irms1 2＝1.11kA2. Comparing fig. 10 and 11, it can be known that the sum of squares of the effective current values under the power decoupling phase shift control is smaller, and the optimization of the effective current values is realized.
The invention provides a three-active-bridge converter power decoupling phase-shifting control method, which can eliminate coupling power between ports and simultaneously ensure that the transmission power range of a converter is not limited; the method for controlling the minimum current effective value based on power decoupling phase shifting is provided, and by optimizing the current effective value expression of the three-active-bridge converter under the control of power decoupling phase shifting, power decoupling and minimum current effective value control among ports of the three-active-bridge converter are realized, and the operating efficiency of the three-active-bridge converter is improved.
Various modifications and variations of the present invention may be made by those skilled in the art, and they are also within the scope of the present invention provided they are within the scope of the claims of the present invention and their equivalents.
What is not described in detail in the specification is prior art that is well known to those skilled in the art.

Claims (8)

1. A three-active-bridge converter power decoupling phase-shifting control and current effective value optimization method is characterized by comprising the following steps:
(1) setting the necessary condition of power decoupling phase shift control, wherein the necessary condition is 2D4+D2＝2D5+D3；D2Is an AC side voltage square wave v of port twoH2D is a shift in phase3Is the AC side voltage square wave v of port threeH3D is a shift in phase4Is the outward shift ratio of one and two ports, D5Is the ratio of outward displacement between port one and port three;
(2) setting the precision delta D of each phase shift, and taking the value of each phase shift meeting the precision requirement;
(3) screening the phase comparison values meeting the requirements through a constraint function;
(4) calculating the square sum of the transmission power and the current effective value of each port;
(5) acquiring actual transmission power, determining an allowable error delta P of the power, and screening a numerical value of transmission power of each port, a numerical value of phase shift ratio of each port and a square sum of effective current values which meet requirements by taking the allowable error delta P as a constraint condition;
(6) finding the least current effective value square sum and the corresponding phase shift ratio D2、D3、D4；
(7) And generating PWM control signals for controlling the on-off of the switch tubes of the ports.
2. The three-active-bridge converter power decoupling phase shift control and current effective value optimization method of claim 1, characterized in that: the specific process of the step (2) is as follows:
setting the precision DeltaD of a phase shift ratio D, including D, according to the period counter value of a DSP controller2、D3、D4、D5D is more than or equal to the phase shift ratio of 0 and less than or equal to 1 under the constraint conditions of accuracy delta D2All values meeting the conditions are taken and stored in an array D2[l]，D3All values meeting the conditions are taken and stored in an array D3[l]，D4All values meeting the conditions are taken and stored in an array D4[l]。
3. The three-active-bridge converter power decoupling phase shift control and current effective value optimization method of claim 2, characterized in that: the specific process of the step (3) is as follows:
setting constraint function screening array D2[l]、D3[l]、D4[l](ii) a Constraint function of Fk(D) Not less than 0, wherein
Figure FDA0003112074270000021
By a constraint function Fk(D) Screening for more than or equal to 0 to obtain an array D2[m]、D3[m]、D4[m]。
4. The three-active-bridge converter power decoupling phase shift control and current effective value optimization method of claim 1 or 2, characterized in that: the specific process of the step (4) is as follows:
calculating to obtain the transmission power P of the second port according to the transmission power expression of each port and the current effective value square sum expression2Transmission power P of port three3Sum of squares of current effective values Σ Irms 2Storing the calculated transmission power value of the second port into the array P2*[m]Storing the calculated transmission power value of a group of ports III into an array P3*[m]Storing the calculated sum of squares of the effective current values into an array Σ Irms 2[m]。
5. The three-active-bridge converter power decoupling phase shift control and current effective value optimization method of claim 4, characterized in that: in the step (4), the transmission power expression and the current effective value square sum expression of each port are as follows:
Figure FDA0003112074270000022
Figure FDA0003112074270000031
wherein: intermediate variables
Figure FDA0003112074270000032
Figure FDA0003112074270000033
Figure FDA0003112074270000034
V1Is the DC side voltage of port one, V2Is the DC side voltage of port two, V3Is the DC side voltage of the port three, and the transformation ratio of the three-winding high-frequency transformer is N1/N2/N3，n12＝N1/N2、n13＝N1/N3，V2' converting the DC side voltage of port two to the value of port one, V3' converting the DC side voltage at port three to the value at port one, V2'＝n12V2、V3'＝n13V3；L1Equivalent inductance of port one, L2Equivalent inductance of port two, L3Equivalent inductance of port three, L2' converting the equivalent inductance of port two to the value of port one, L3' converting the equivalent inductance of Port three to the value of Port one, L2'＝n12 2L2、L3'＝n13 2L3；
Figure FDA0003112074270000035
The effective value of the current of the port one;
Figure FDA0003112074270000037
the effective value of the current of the port II is;
Figure FDA0003112074270000036
the effective value of the current of the port three; l is12Is the equivalent inductance parameter of the first port and the second port; l is13Is the equivalent inductance parameter of port one and three; l is23Is the equivalent inductance parameter of port two and port three.
6. The three-active-bridge converter power decoupling phase shift control and current effective value optimization method of claim 5, characterized in that: the specific process of the step (5) is as follows:
acquiring actual transmission power P of a second port of the three-active-bridge converter under a given working condition2NAnd actual transmission power P of port three3NDetermining the allowable error delta P of the power according to the sampling precision, and eliminating the array P by taking the allowable error delta P as a constraint condition2*[m]、P3*[m]The value which is not qualified in the range is obtained to obtain the array P in the allowable error range delta P2*[i]、P3*[i]According to the array P2*[i]、P3*[i]And (1) eliminating the array D2[m]、D3[m]、D4[m]Obtaining new array D from the value not meeting the requirement2[i]、D3[i]、D4[i](ii) a According to array D2[i]、D3[i]、D4[i]And formulas (2), (3), (4) and (5), removing the arrays Σ Irms 2[m]Obtaining new array sigma I by using the numerical value which does not meet the requirementrms 2[i]。
7. The three-active-bridge converter power decoupling phase shift control and current effective value optimization method of claim 6, characterized in that: the specific process of the step (6) is as follows:
for array Σ Irms 2[i]Optimizing numerical value to obtain the minimum current effective value square sum min (Sigma I) of the three-active-bridge converter under the given working conditionrms 2) And obtaining a minimum current effective value sum of squares min (∑ I)rms 2) Lower corresponding phase shift ratio D2、D3、D4。
8. The three-active-bridge converter power decoupling phase shift control and current effective value optimization method of claim 7, characterized in that: in the step (7), the sum of squares of the obtained minimum current effective values min (Σ I) is usedrms 2) And corresponding phase shift ratio D2、D3、D4And generating PWM control signals for controlling the on-off of the switch tubes of the ports.
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