CN113507207B - Control circuit and control method for multiphase series capacitor DC-DC converter - Google Patents

Control circuit and control method for multiphase series capacitor DC-DC converter Download PDF

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CN113507207B
CN113507207B CN202110754199.7A CN202110754199A CN113507207B CN 113507207 B CN113507207 B CN 113507207B CN 202110754199 A CN202110754199 A CN 202110754199A CN 113507207 B CN113507207 B CN 113507207B
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phase
circuit
control
signal
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CN113507207A (en
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程林
刘泽国
吴枫
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Chen Song
Cheng Lin
Hefei Chengling Microelectronics Co ltd
Wu Feng
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University of Science and Technology of China USTC
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output

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  • Dc-Dc Converters (AREA)

Abstract

The present disclosure provides a multiphase series capacitor dc-dc converter control circuit, comprising: the power stage circuit at least comprises two-phase inductors, the current of each phase inductor has a preset phase difference, and the load is charged by controlling the inductors of each phase in an alternating manner so as to convert the input direct-current voltage into the stable direct-current voltage required by the load; and the pulse width modulation control circuit is used for generating control signals for controlling the switches of the power tubes of all phases, wherein when the load has transient jump, the duty ratio of the power tube control signal of the circuit where the current inductor for charging the load is located is expanded so as to quickly respond to the transient jump of the load. The disclosure also provides a corresponding control method. The control circuit and the control method can be applied to an N-phase series capacitor direct current-direct current converter, can realize the conduction time expansion of a power tube larger than T/N when a load generates transient jump, greatly expands the continuous charging time of the equivalent inductive current for the output load in a single period, and improves the speed of transient response.

Description

Control circuit and control method for multiphase series capacitor DC-DC converter
Technical Field
The disclosure relates to the technical field of electronics, and in particular relates to a control circuit and a control method for a multiphase series capacitor direct current-direct current converter.
Background
Under the application environment of high voltage and large conversion ratio, an N-phase series capacitor direct current-direct current converter is generally adopted, the existing N-phase series capacitor direct current-direct current converter adopts current mode control, a current sampling circuit is needed, and output voltage and inductive current are used as feedback quantity to control the converter; in order to avoid the overlapping of conduction time of the N-phase power tube, the N-phase control signal needs to keep a fixed phase difference of 360 DEG/N, the conduction time expansion of the power tube control signal which is larger than T/N cannot be realized, and the transient response speed of a load is limited; the existing current mode control needs a current sampling circuit and a complex phase shift generation circuit because the switching frequency is not fixed and the output voltage ripple is large.
BRIEF SUMMARY OF THE PRESENT DISCLOSURE
In view of the above problems, the present disclosure provides a control circuit and a control method for a multiphase series capacitor dc-dc converter to solve the above technical problems.
One aspect of the present disclosure provides a multiphase series capacitance dc-dc converter control circuit, comprising: the power level circuit at least comprises two phases of inductors, the current of each phase of inductor has a preset phase difference, and the inductors of each phase are used for alternately charging the load by controlling the power tubes of the circuit where the inductors of each phase are located to be alternately switched on and off so as to convert the input direct-current voltage into the stable direct-current voltage required by the load; and the pulse width modulation control circuit is used for generating a control signal for controlling the power tube switch of the circuit where the inductor of each phase is located, wherein when the load generates transient jump, the duty ratio of the power tube control signal for charging the load at present is correspondingly expanded so as to quickly respond to the transient jump of the load.
Optionally, if the duty ratio of the current power tube control signal for charging the load is greater than 1/N, the pwm control circuit shields the control signals of the power tubes of the circuit where the inductors of other phases are located until the control signals with the duty ratio greater than 1/N are expanded, and recovers the control signals of the phases, where N represents the number of phases of the inductors.
Optionally, the pwm control circuit includes: the error signal generating circuit is used for comparing the difference value of the output voltage of the power level circuit and the reference voltage to obtain an error signal; the control signal generating circuit is used for generating control signals of all phases according to the error signals and a periodic ramp signal, wherein when the load has transient jump, the error signals are larger than the preset periodic ramp signal, and the duty ratio of the control signals of the power tube of the circuit where the inductor which charges the load is located is correspondingly expanded; and the control signal logic circuit is used for shielding the control signals of the power tubes of the circuits where the inductors of other phases are located when the load has transient jump and if the duty ratio of the current power tube control signal for charging the load is greater than 1/N, and restoring the control signals of the phases until the control signals with the duty ratio greater than 1/N are expanded, so that the control signals of the power tubes of the phases are prevented from being overlapped, and N represents the phase number of the inductor.
In another aspect, the present disclosure provides a method for controlling a multiphase series capacitor dc-dc converter, including: respectively generating control signals of each phase of power tube in a power stage circuit of the multi-phase series capacitor DC-DC converter so as to control the inductors of each phase to charge the load in turn and alternately; when the load has transient jump, expanding the duty ratio of the power tube control signal which charges the load at present so as to quickly respond to the transient jump of the load.
Optionally, comprising: if the duty ratio of the power tube control signal for charging the load at present is larger than 1/N, shielding other power tube control signals of each phase; and recovering the control signals of all phases until the control signal expansion with the duty ratio larger than 1/N is finished, wherein N represents the phase number of the inductor in the power level circuit.
Optionally, comprising: comparing the difference value of the output voltage of the power level circuit and the reference voltage to obtain an error signal; and when the error signal is greater than the lowest potential of a preset period ramp signal, correspondingly expanding the duty ratio of the power tube control signal for charging the load at present.
The at least one technical scheme adopted in the embodiment of the disclosure can achieve the following beneficial effects:
the multiphase series capacitor direct current-direct current converter control circuit and the control method can be applied to an N-phase series capacitor direct current-direct current converter, the switching frequency of each phase control signal is fixed, the output voltage ripple is small, a current sampling circuit and a complex phase shift generating circuit are not needed, the circuit structure is simple, when the load has transient jump, the conduction time of a power tube larger than T/N can be expanded, the continuous charging time of equivalent inductive current for the output load in a single period is greatly expanded, and the speed of transient response is improved.
Drawings
For a more complete understanding of the present disclosure and the advantages thereof, reference is now made to the following descriptions taken in conjunction with the accompanying drawings, in which:
FIG. 1 schematically illustrates a two-phase series capacitor DC-DC converter control circuit diagram;
FIG. 2 schematically illustrates a signal diagram of a two-phase series capacitor DC-DC converter control circuit;
fig. 3 schematically illustrates a schematic diagram of a control circuit of a multiphase series capacitor dc-dc converter provided by an embodiment of the present disclosure;
fig. 4 schematically illustrates a signal diagram of a control circuit of a multiphase series capacitor dc-dc converter provided in an embodiment of the present disclosure;
fig. 5 schematically shows a flow of a control method of a multiphase series capacitor dc-dc converter provided by the embodiment of the present disclosure.
Detailed Description
Hereinafter, embodiments of the present disclosure will be described with reference to the accompanying drawings. It should be understood that the description is illustrative only and is not intended to limit the scope of the present disclosure. In the following detailed description, for purposes of explanation, numerous specific details are set forth in order to provide a thorough understanding of the embodiments of the disclosure. It may be evident, however, that one or more embodiments may be practiced without these specific details. Moreover, in the following description, descriptions of well-known structures and techniques are omitted so as to not unnecessarily obscure the concepts of the present disclosure.
The terminology used herein is for the purpose of describing particular embodiments only and is not intended to be limiting of the disclosure. The terms "comprises," "comprising," and the like, as used herein, specify the presence of stated features, steps, operations, and/or components, but do not preclude the presence or addition of one or more other features, steps, operations, or components.
All terms (including technical and scientific terms) used herein have the same meaning as commonly understood by one of ordinary skill in the art unless otherwise defined. It is noted that the terms used herein should be interpreted as having a meaning that is consistent with the context of this specification and should not be interpreted in an idealized or overly formal sense.
Some block diagrams and/or flow diagrams are shown in the figures. It will be understood that some blocks of the block diagrams and/or flowchart illustrations, or combinations thereof, can be implemented by computer program instructions. These computer program instructions may be provided to a processor of a general purpose computer, special purpose computer, or other programmable data processing apparatus, such that the instructions, which execute via the processor, create means for implementing the functions/acts specified in the block diagrams and/or flowchart block or blocks.
Accordingly, the techniques of this disclosure may be implemented in hardware and/or software (including firmware, microcode, etc.). In addition, the techniques of this disclosure may take the form of a computer program product on a computer-readable medium having instructions stored thereon for use by or in connection with an instruction execution system. In the context of this disclosure, a computer-readable medium may be any medium that can contain, store, communicate, propagate, or transport the instructions. The computer readable medium can include, for example but not limited to, an electronic, magnetic, optical, electromagnetic, infrared, or semiconductor system, apparatus, device, or propagation medium. Specific examples of the computer readable medium include: magnetic storage devices, such as magnetic tape or Hard Disk Drives (HDDs); optical storage devices, such as compact disks (CD-ROMs); a memory, such as a Random Access Memory (RAM) or a flash memory; and/or wired/wireless communication links.
Fig. 1 schematically shows a control circuit diagram of a two-phase series capacitor dc-dc converter.
As shown in fig. 1, a control circuit of a conventional two-phase series capacitor dc-dc converter includes: power stage circuit 101, control loop 102. According to the conventional power stage circuit 101, the charging slope m1 and the discharging slope m2 of the Phase1 and Phase2 inductor currents are as follows:
Figure BDA0003142312440000041
Figure BDA0003142312440000051
the total equivalent inductor current charging slope, discharging slope and ripple of Phase1 and Phase2 are (3), (4) and (5), respectively:
Figure BDA0003142312440000052
Figure BDA0003142312440000053
Δi L ＝m ch ×DT (5)
as can be seen from equation (3), the slope of the inductor current represents the capability of the inductor current to charge the load when the load has a transient jump, and the larger the slope is, the faster the load is charged, the faster the recovery speed of the output voltage is, the smaller the voltage drop is, and the faster the transient response speed of the load is. According to the formula (5), when the load has transient jump, the larger the duty ratio D is, the longer the charging time DT to the load capacitor in a single period is, the faster the recovery speed of the output voltage is, and the faster the transient response speed of the load is.
The working principle of the control method of the traditional two-phase series capacitor DC-DC converter is as follows: adopting current mode control to output feedback voltage V FB And a reference voltage V REF The difference is made by an error amplifier EA to generate an error signal V EA . The inductive current detection circuit is used for detecting the inductive current I LB The detected voltage V SEN And an error signal V EA Comparing to determine the rising Edge (EN) of SBH conduction time of Phase2 power tube oNM ). Using a T/2 phase shift generation circuit to generate EN ONM The signal delay T/2 generates the rising Edge (EN) of the SAH conduction time of the Phase1 power tube ONs ) To conduct two phasesThe rising edges of the time signals pass through an elastic on-time modulator (EOM) to generate respective on-time signals T ONM And T ONS . To avoid overlap of the two-phase power tube pilot signals, the signal V is controlled M And Vs are both less than 0.5.
Fig. 2 schematically shows a signal diagram of a control circuit of a two-phase series capacitor dc-dc converter.
As shown in fig. 2, for the two-phase capacitive buck dc-dc converter, when a load transient response occurs, the conventional transient response control circuit shown in fig. 1 expands the rising time of the two-phase inductor current by alternately expanding the duty ratio of the two-phase control signal, increases the charging time of the load capacitor in a single period, and accelerates the recovery speed of the output voltage, thereby increasing the load transient response speed.
However, according to the control method for the current mode of the two-phase series capacitor dc-dc converter shown in fig. 1, the converter is controlled by using the output voltage and the inductor current as feedback quantities, and an additional current sampling circuit is required; because the switching frequency is not fixed, in order to avoid the control signal overlapping of the two-phase power tube, a complex phase shift generating circuit and an additional control circuit are also needed, and the control circuit is complex; the two-phase control signal of the power tube can not realize the conduction time expansion more than T/2, and the two-phase equivalent inductive current i in a single period L The continuous charging time for the load capacitor is limited, and the transient response speed of the load is limited.
Based on the above disadvantages, the present disclosure provides a voltage mode control circuit of a multiphase series capacitor dc-dc converter, which does not require a current sampling circuit and a phase shift generating circuit and is simple. Meanwhile, the transient response speed of the load can be improved on the premise of not increasing the switching frequency.
In the embodiment of the present disclosure, a two-phase series capacitive dc-dc converter is used for illustration, but the technical solution of the present disclosure is not limited to be applied to the two-phase series capacitive dc-dc converter, and details thereof are not described below.
Fig. 3 schematically illustrates a schematic diagram of a control circuit of a multiphase series capacitor dc-dc converter provided in an embodiment of the present disclosure.
As shown in fig. 3, the control circuit includes a power stage circuit 310 and a pulse width modulation control circuit 320.
The power stage circuit 310 at least comprises two-phase inductors, the inductor current of each phase has a preset phase difference, and the inductors of each phase are used for alternately charging the load by controlling the power tubes of the circuit where the inductors of each phase are located to be alternately switched on and off, so that the input direct-current voltage is converted into the stable direct-current voltage required by the load.
And the pwm control circuit 320 is configured to generate a control signal for controlling the power transistor switch of the circuit in which the inductor of each phase is located, wherein when the load undergoes a transient jump, the duty ratio of the control signal of the power transistor of the circuit in which the inductor is currently charged to the load is correspondingly expanded, so as to quickly respond to the transient jump of the load.
Specifically, at least one phase of the inductance circuit in the power stage circuit 310 includes: power switch SAH, capacitor C FLY SAL and a filter inductor L A Sequentially connecting; at least another phase of the inductive circuit in the power stage circuit includes: power switch SBH, power switch SBL and filter inductor L B Are connected in sequence; wherein the power switch SAH and the power switch SBH are both connected with the capacitor C F The power switches SAH and SBH are used to control the voltage input of each phase of the power stage circuit; the filter inductor L A And a filter inductance L B The output ends of the power stage circuits are connected with the output port of the power stage circuit; and the output port of the power level circuit is also provided with a grounded filter capacitor C. In addition, the capacitor C is connected in parallel with a load resistor RL.
The pwm control circuit 320 includes: an error signal generating circuit 321 for comparing the output voltage V of the power stage circuit OUT And a reference voltage V REF To obtain an error signal V EA (ii) a A control signal generation circuit 322 for generating a control signal based on the error signal V EA Generating phase control signals in conjunction with a Ramp signal Ramp, wherein the error signal is greater than the phase control signals when a transient jump occurs in the loadThe preset period ramp signal is used for correspondingly expanding the duty ratio of a control signal of a power tube of a circuit where the inductor currently charges a load is located; and the control signal logic circuit 323 is used for shielding the control signals of the power tubes of the circuits where the inductors of other phases are located when the load generates transient jump and if the duty ratio of one of the control signals PWM1 and PWM2 is greater than 1/2, and restoring the control signals of the phases until the control signals with the duty ratio greater than 1/2 are expanded, so that the control signals of the power tubes of the phases are prevented from being overlapped.
The duty ratios of the first control signal PWM1 and the second control signal PWM2 generated by the control signal generating circuit 322 are respectively determined by the difference between the error signal and the preset period harmonic signal Ramp; the periods and phases of the first control signal PWM1 and the second control signal PWM2 are determined by the corresponding preset first period clock signal CLK1 and second period clock signal CLK2, respectively.
In the disclosed embodiment, the period of the periodic ramp signal is the same as the period of the single-phase periodic clock signal. The Ramp signal Ramp may generate a periodic pulse signal, and for example, a two-phase series capacitor dc-dc converter may generate two-phase clock signals CLK1 and CLK2 with a phase difference of 180 ° by dividing the Ramp by two, so that the control signals of the power transistors of the circuits in which the inductors of the respective phases are located have corresponding phase differences. The generation of the ramp signal and the clock signal is only an example, and the specific implementation is not limited. Because the switching frequency is fixed, the circuit has a simple structure and is easy to design.
In the disclosed embodiment, the output voltage V is adjusted by adjusting the duty cycle of the two-phase control signal oUT Stabilized to a reference voltage V REF . The function of the two-phase control signals is not limited by the disclosure, and when the load is in a transient state, the duty ratio of the power tube control signal PWMA or PWMB is allowed to be more than 0.5 for expansion. And when the error signal is greater than the lowest potential of the preset periodic ramp signal, correspondingly expanding the duty ratio of the power tube control signal for charging the load at present along with the magnitude of the error signal. If the duty cycle of the power tube control signal currently charging the load is greater than 0.5,and the control signal logic circuit shields the control signals of the power tubes of other phases until the control signals with the duty ratio larger than 0.5 are expanded, and restores the control signals of the phases, so that the control signals of two phases of grid ends are prevented from being mutually overlapped.
Further, when the power stage circuit comprises an N-phase inductor, if the load has transient jump and the duty ratio of the current power tube control signal for charging the load is greater than 1/N, the pulse width modulation control circuit shields the control signals of the power tubes of the circuits where the inductors of other phases are located until the control signals with the duty ratio greater than 1/N are expanded, and recovers the control signals of the phases, so that the control signals of the power tubes of the phases are prevented from being overlapped.
Fig. 4 schematically shows a signal diagram of a control circuit of a multiphase series capacitor dc-dc converter provided by the embodiment of the present disclosure.
As shown in fig. 4, when the load has a transient jump, the Phase1 is used to illustrate the extension of the current inductor current loop for charging the load, which allows the duty ratio of PWMA to be greater than 0.5.
Phase1 power tube control signal PWMA allows a duty cycle extension greater than 0.5 to be achieved when a transient transition in the load occurs. As shown in FIG. 4, the amplitude of the PWM1 signal expansion depends on the error signal V when the load has a transient transition EA And according to the magnitude relation of the Ramp signal, when the duty ratio of the PWM1 is larger than 0.5, the PWM2 signal is shielded, the SBH of the power switch is closed, the SBL is switched on, and the existing two-phase control signal is recovered until the PWM1 signal is expanded.
As shown in fig. 4, when the load has transient jump, the equivalent inductor current i L (i.e. the sum of the two-phase inductor currents) is less than the load current I OUT The output filter capacitor C discharges to the load and outputs a voltage V OUT Descend through D trnew Equivalent inductor current i after T time L Equal to the load current, the output voltage stops decreasing, and then the equivalent inductor current i L And the output filter capacitor C is charged when the load current Iout is larger than the load current Iout. Equivalent inductor current i as shown in FIG. 4 L And the load current I OUT Black shadow betweenThe partial area represents the charge Q discharged by the output capacitor when the load jumps new_discharge . The time for the equivalent inductor current to reach the load current in the control method proposed by the present disclosure can be calculated by equation (6).
Figure BDA0003142312440000081
In the formula D trnew T is equivalent inductance current i after transient state L Increase to load current I OUT_H Required time, D A，trnew Duty ratio (D) of control signal PWMA of Phase1 power tube in transient state A，trnew May be greater than 0.5), I OUT_L And I OUT_H Respectively, the load current before and after the load jump.
In contrast, as shown in fig. 2, in the conventional control method of the multi-phase series capacitance type buck-type dc-dc converter, when a load jumps, a two-phase control signal V is generated M And V s The duty ratio of the inductor is alternatively expanded and cannot be larger than 0.5, so that the equivalent inductive current i L Load current I after not reaching a load jump OUt_H Time, equivalent inductor current i L And the slope of the formula (4) begins to decrease, another phase of inductive current is waited for to charge the load capacitor, the output load capacitor cannot be continuously charged, the discharge of the output capacitor to the load is intensified, the discharge electric charge quantity of the output capacitor is increased, the fluctuation range of the output voltage is increased, and the recovery time is prolonged. Equivalent inductor current i as shown in FIG. 2 L And the load current I OUT The area of the black shaded part between the two represents the charge quantity Q discharged by the output capacitor when the load jumps old_discharge . The time for the equivalent inductor current to reach the load current under this control method can be calculated by equation (7).
Figure BDA0003142312440000091
In the formula D trold T is equivalent inductive current i after transient state of traditional control method L Increase to load current I OUT_H Required time, D A，trold Phase1 control signal V in transient state S Duty cycle (D) A，trold Less than 0.5).
Represented by formula (6) and formula (7) OUT_H And I OUT_L Equality can be seen in D trnew T＜D trold T; as can be seen from the areas of the black shaded portions in fig. 2 and 4 (the charging slope and the discharging slope of the equivalent inductor current in the transient response control method proposed by the present disclosure are equal to those in the conventional control method, respectively), Q is new_discharge ＜Q old_discharge Namely: according to the transient control method, when the load jumps, the electric charge amount discharged by the output capacitor can be reduced, and meanwhile, the time for the equivalent inductive current to reach the load current after jumping can be reduced. By the formula Δ V OUT ×C＝Q discharge Obtaining: Δ V OUT_new ＜ΔV OUT_old When the control method provided by the disclosure generates load jump, the output voltage has smaller change amplitude and is more stable. To sum up: because the control signal PWMA of the Phase1 power tube in the transient response control method provided by the disclosure can realize the duty ratio expansion of more than 0.5, the continuous charging time of the equivalent inductive current for the output load is greatly expanded, and the transient response speed of the load is improved.
The control circuit can be applied to an N-phase series capacitor direct current-direct current converter, when a load jumps transiently, the conduction time of a power tube larger than T/N can be expanded, T represents the charging period of a power level circuit to the load, the continuous charging time of the equivalent inductive current for the output load in a single period is greatly expanded, and the transient response speed is improved.
Fig. 5 schematically shows a flow of a control method of a multiphase series capacitor dc-dc converter provided in an embodiment of the present disclosure.
As shown in fig. 5, the control method provided by the present disclosure includes steps S510 to S520.
And S510, respectively generating control signals of power tubes of all phases in a power stage circuit of the multi-phase series capacitor DC-DC converter so as to control the inductors of all phases to charge the load alternately in sequence.
And S520, when the load is subjected to transient jump, expanding the duty ratio of the power tube control signal which charges the load at present so as to quickly respond to the transient jump of the load.
In the embodiment of the disclosure, the error signal generating circuit 321 outputs the output voltage V OUT And a reference voltage V REF Comparing to obtain an error signal V EA (ii) a The control signal generation circuit 322 outputs the error signal V EA The size relation with the Ramp determines the expansion amplitude of the PWM1 and the PWM2; the control signal logic circuit 323 performs logic processing on the control signals PWM1 and PWM2 to avoid mutual overlapping of the Phase control signals, and further generates the control signals PWMA and PWMB of Phase1 and Phase 2. Adjusting output voltage V by adjusting the duty cycle of Phase1 and Phase2 loop power pipe control signals PWMA, PWMB OUT Stabilized to a reference voltage V REF 。
Wherein the control signal generation circuit 322 outputs the error signal V EA The magnitude relation with Ramp determines the extension amplitude of PWM1, including:
s521, comparing the difference value of the output voltage of the power stage circuit and the reference voltage to obtain an error signal;
and S522, when the error signal is greater than the lowest potential of the preset period ramp signal, correspondingly expanding the duty ratio of a control signal of a power tube of a circuit where the inductor is located, which is currently used for charging a load, along with the magnitude of the error signal.
Accordingly, the error signal V EA The expansion amplitude of the PWM2 is determined by the size relation with the Ramp, and a control signal PWM2 of Phase2 is generated; when the load jumps, when the duty ratio of the control signal PWM1 of Phase1 is greater than 0.5, the control signal PWM2 of Phase2 is masked, that is, the SBH is turned off, the SBL is turned on, and the process is ended until the PWM1 signal is expanded, and the existing two-Phase control signal is recovered.
According to an embodiment of the disclosure, the method further comprises:
s523, if the duty ratio of the control signal of the power tube of the circuit where the inductor is located, which is currently charging the load, is greater than 0.5, shielding the control signals of the power tubes of the circuits where the inductors of other phases are located;
and S524, recovering the control signals of each phase until the control signals with the duty ratio larger than 0.5 are expanded.
It should be noted that steps S520 to S524 are only an exemplary illustration of the flow of the control method for the multiphase series capacitor dc-dc converter provided in the embodiment of the present disclosure, and are not limited herein.
The control method can be applied to the N-phase series capacitor direct current-direct current converter, when the load jumps transiently, the conduction time of the power tube larger than T/N can be expanded, the continuous charging time of the output load by the equivalent inductive current in a single period is greatly expanded, and the transient response speed is improved.
It is understood that steps S510 to S520 may be combined and implemented in one module, or any one of the modules may be split into a plurality of modules. Alternatively, at least part of the functionality of one or more of these modules may be combined with at least part of the functionality of the other modules and implemented in one module. According to embodiments of the present disclosure, at least one of them may be implemented at least in part as a hardware circuit, such as a Field Programmable Gate Array (FPGA), a Programmable Logic Array (PLA), a system on a chip, a system on a substrate, a system on a package, an Application Specific Integrated Circuit (ASIC), or in hardware or firmware in any other reasonable manner of integrating or packaging a circuit, or in a suitable combination of three implementations of software, hardware, and firmware. Alternatively, at least one of steps S510 to S520 may be at least partially implemented as a computer program module, which, when executed by a computer, may perform the functions of the respective module.
Those skilled in the art will appreciate that various combinations and/or combinations of features recited in the various embodiments and/or claims of the present disclosure can be made, even if such combinations or combinations are not expressly recited in the present disclosure. In particular, various combinations and/or combinations of the features recited in the various embodiments and/or claims of the present disclosure may be made without departing from the spirit or teaching of the present disclosure. All such combinations and/or associations are within the scope of the present disclosure.
While the disclosure has been shown and described with reference to certain exemplary embodiments thereof, it will be understood by those skilled in the art that various changes in form and details may be made therein without departing from the spirit and scope of the disclosure as defined by the appended claims and their equivalents. Accordingly, the scope of the present disclosure should not be limited to the above-described embodiments, but should be defined not only by the appended claims, but also by equivalents thereof.

Claims (4)

1. A multiphase series capacitor dc-dc converter control circuit, comprising:
the power level circuit at least comprises two phases of inductors, the current of each phase of inductor has a preset phase difference, and the inductors of each phase are used for alternately charging the load by controlling the power tubes of the circuit where the inductors of each phase are located to be alternately switched on and off so as to convert the input direct-current voltage into the stable direct-current voltage required by the load;
the pulse width modulation control circuit is used for generating control signals for controlling power tube switches of circuits where the inductors of all phases are located so as to control the inductor currents of all phases to alternately charge the load at a fixed frequency in sequence, wherein when the load generates transient jump, the duty ratio of the power tube control signals of the circuits where the inductors of the load are currently charged is expanded so as to quickly respond to the transient jump of the load;
when the load has transient jump, if the duty ratio of the current power tube control signal for charging the load is larger than 1/N, the pulse width modulation control circuit shields the control signals of the power tubes of the circuits where the inductors of other phases are located until the control signals with the duty ratio larger than 1/N are expanded, and the control signals of the phases are recovered, wherein N represents the number of phases of the inductors.
2. The control circuit of claim 1, wherein the pulse width modulation control circuit comprises:
the error signal generating circuit is used for comparing the difference value of the output voltage of the power level circuit and the reference voltage to obtain an error signal;
the control signal generating circuit is used for generating control signals for controlling the power tube switches of the circuits where the inductors of all phases are located according to the error signals and a periodic ramp signal, wherein when the load has transient jump, the error signals are larger than the preset periodic ramp signal, and the duty ratio of the control signals of the power tubes of the circuits where the inductors are located and charging the load at present is correspondingly expanded; the duty ratio of each phase control signal is determined by the difference value of the error signal and the preset period ramp signal; the period and the phase of each phase control signal are respectively determined by each corresponding preset period clock signal;
and the control signal logic circuit is used for shielding the control signals of the power tubes of the circuits where the inductors of other phases are located when the load has transient jump and if the duty ratio of the current power tube control signal for charging the load is greater than 1/N, and restoring the control signals of the phases until the control signals with the duty ratio greater than 1/N are expanded, so that the control signals of the power tubes of the phases are prevented from being overlapped, and N represents the phase number of the inductors.
3. A method for controlling a multiphase series capacitor dc-dc converter, comprising:
respectively generating control signals of each phase power tube in a power stage circuit of the multi-phase series capacitor DC-DC converter so as to control each phase inductive current to alternately charge a load at a fixed frequency in sequence;
when the load has transient jump, expanding the duty ratio of the power tube control signal which charges the load at present so as to quickly respond to the transient jump of the load;
if the duty ratio of the power tube control signal for charging the load at present is larger than 1/N, the control signal logic circuit shields the control signals of the power tubes of other phases, and N represents the phase number of the inductor in the power stage circuit;
and restoring the power tube control signals of all phases until the control signal with the duty ratio larger than 1/N is expanded.
4. The control method according to claim 3, characterized by comprising:
comparing the difference value of the output voltage of the power level circuit and the reference voltage to obtain an error signal;
when the error signal is greater than a preset period ramp signal, correspondingly expanding the duty ratio of a control signal of a power tube of a circuit where the inductor currently charges the load is located; the duty ratio of each phase control signal is determined by the difference value of the error signal and the preset period harmonic signal; the period and the phase of each phase control signal are respectively determined by each corresponding preset period clock signal.
CN202110754199.7A 2021-06-30 2021-06-30 Control circuit and control method for multiphase series capacitor DC-DC converter Active CN113507207B (en)

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