CN113489296A - Active compensation control circuit and method - Google Patents
Active compensation control circuit and method Download PDFInfo
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- CN113489296A CN113489296A CN202110781245.2A CN202110781245A CN113489296A CN 113489296 A CN113489296 A CN 113489296A CN 202110781245 A CN202110781245 A CN 202110781245A CN 113489296 A CN113489296 A CN 113489296A
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- 239000003990 capacitor Substances 0.000 claims abstract description 89
- 238000006243 chemical reaction Methods 0.000 claims abstract description 42
- 238000007599 discharging Methods 0.000 claims description 21
- 230000000694 effects Effects 0.000 abstract description 2
- 230000001276 controlling effect Effects 0.000 description 12
- 238000010586 diagram Methods 0.000 description 7
- 230000000295 complement effect Effects 0.000 description 2
- 238000004146 energy storage Methods 0.000 description 2
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/34—Parallel operation in networks using both storage and other dc sources, e.g. providing buffering
- H02J7/345—Parallel operation in networks using both storage and other dc sources, e.g. providing buffering using capacitors as storage or buffering devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
Abstract
The invention provides an active compensation control circuit and a method, wherein the active compensation circuit is connected in parallel with a direct current bus between a preceding stage conversion circuit and a direct current conversion circuit and provides active compensation for a first capacitor connected in parallel on the direct current bus, the active compensation circuit comprises a charge-discharge module and a second capacitor, the control circuit controls the charge-discharge module, the charge-discharge module is connected with the first capacitor and the second capacitor, the control circuit samples a first voltage at two ends of the first capacitor, and when the first voltage is greater than a peak voltage reference value, the control circuit controls the first voltage; and when the first voltage is smaller than the valley voltage reference value, the control circuit controls the second voltage at two ends of the second capacitor. The technical scheme of the invention can effectively improve the compensation precision and effect of the active compensation circuit.
Description
Technical Field
The invention relates to an alternating current-direct current conversion circuit, in particular to an active compensation control circuit and method.
Background
Generally, an AC/DC electric energy conversion device comprises a preceding stage conversion circuit and a DC conversion circuit, wherein a capacitor needs to be connected in parallel on a DC bus between the preceding stage conversion circuit and the DC conversion circuit to store energy so as to reduce the fluctuation range of the DC bus voltage and optimize the design of the conversion device.
If the capacitance value of the capacitor is selected to be small, the voltage fluctuation of a direct current bus is large, so that the design of a later stage is difficult, the size is large, and the efficiency is low; in severe cases (for example, when full power is output), the voltage trough of the pulsating dc bus is low, even reduced to 0V, the output voltage of the dc converter circuit cannot be maintained, and therefore the capacitor is usually selected to be an electrolytic capacitor with a large capacitance value.
However, the electrolytic capacitor has a large size, which is not beneficial to realizing the small and portable design of the adapter, and in addition, the electrolytic capacitor has a short service life and a limited service life of the product.
Disclosure of Invention
The invention provides an active compensation control circuit and method, which can effectively and accurately control the precision of active compensation.
The technical scheme adopted by the invention is as follows:
an active compensation control circuit is used for controlling an active compensation circuit, the active compensation circuit is connected in parallel with a direct current bus between a preceding stage conversion circuit and the direct current conversion circuit and provides active compensation for a first capacitor connected in parallel with the direct current bus, the active compensation circuit comprises a charge-discharge module and a second capacitor, the charge-discharge module is connected in parallel between the first capacitor and the second capacitor, the control circuit controls the charge-discharge module, the control circuit comprises a mode selection module, the mode selection module samples a first voltage at two ends of the first capacitor and outputs a working mode signal, when the first voltage is greater than a peak voltage reference value, the working mode signal is a charging mode signal, and the control circuit controls a second voltage at two ends of the second capacitor according to the charging mode signal; when the first voltage is smaller than the valley voltage reference value, the working mode signal is a discharging mode signal, and the control circuit controls the first voltage according to the discharging mode signal; when the first voltage is between the peak voltage reference value and the peak voltage reference value, the working mode signal is a shutdown mode signal, and the control circuit controls the charging and discharging module to be shut down according to the shutdown mode signal.
The active compensation control circuit further comprises a discharge control loop and a current control module, wherein the discharge control loop works when the discharge mode signal is effective, the discharge control loop samples the first voltage and compares the first voltage with a first reference voltage to generate a first current reference signal, and the current control module generates a control signal of a switch in the charge and discharge module according to the first current reference signal to control the first voltage.
The active compensation control circuit further comprises a charging control loop, wherein the charging control loop works when the charging mode signal is effective, the charging control loop samples the second voltage and compares the second voltage with a second reference voltage to generate a second current reference signal, and the current control module generates a control signal of a switch in the charging and discharging module according to the second current reference signal to control the second voltage.
The active compensation control circuit further comprises a shutdown control loop, the shutdown control loop works when the shutdown control signal is effective, the shutdown control loop outputs a third current reference signal, the third current reference signal is zero, and the current control module generates a control signal for turning off a switch in the charge and discharge module according to the third current reference signal.
The active compensation control circuit further comprises a driving module, wherein the driving module is connected with the output end of the current control module, and the control signal output by the current control module is converted into a driving signal for driving the switch in the charge and discharge module.
The charge control loop includes a proportional-integral regulator.
The discharge control loop includes a proportional-integral regulator.
The first current reference value is connected with the current control module after passing through the fifth switch, the second current reference value is connected with the current control module after passing through the sixth switch, when the working mode signal is in a discharging mode, the fifth switch is closed, the sixth switch is turned off and on, when the working mode signal is in a charging mode, the fifth switch is opened, and the sixth switch is closed.
And the first current reference value or the second current reference value is output to the current control module after being subjected to amplitude limiting by the amplitude limiting processor.
The mode selection module comprises a hysteresis comparator, wherein the positive input end of the hysteresis comparator is connected with the first voltage, and the negative input end of the hysteresis comparator is respectively connected with a peak voltage reference value and a valley voltage reference value.
The output end of the hysteresis comparator is connected with the control ends of the fifth switch, the sixth switch and the seventh switch.
The shutdown control loop comprises an eighth switch, the eighth switch is normally open, the seventh switch is closed, and the output end of the third current reference signal is connected with the ground end.
The shutdown control loop further comprises a fifth resistor, a seventh capacitor and a seventh switch, wherein the fifth resistor and the seventh capacitor are connected in series between the auxiliary power supply and the ground, a voltage between the anode of the seventh capacitor and the ground provides a driving signal for the eighth switch to control the eighth switch to be disconnected, the seventh switch is connected in parallel with two ends of the seventh capacitor, and the control end of the seventh switch is connected with the output end of the mode selection module.
The driving module further comprises a converter, and the converter allocates the corresponding relation between the driving signal and the switch in the charging and discharging module according to the working mode signal.
The invention also provides a control method of the active compensation circuit, which is used for controlling the active compensation circuit, the active compensation circuit is connected in parallel with a direct current bus between a preceding stage conversion circuit and the direct current conversion circuit and provides active compensation for a first capacitor connected in parallel with the direct current bus, the active compensation circuit comprises a charge-discharge module, a second capacitor and a control circuit, the charge-discharge module is connected in parallel between the first capacitor and the second capacitor, the control circuit controls the charge-discharge module, and the control method is integrated in the control circuit and comprises the following steps:
step 2, the first voltage is larger than the peak voltage reference value, the second voltage at two ends of the second capacitor is controlled, and the preceding stage conversion circuit outputs power to the second capacitor through the charge-discharge module;
step 3, the first voltage is smaller than the valley voltage reference value, the output power of the second capacitor to the first capacitor through the charge-discharge module is controlled, and the first voltage at two ends of the first capacitor is controlled;
and 4, when the first voltage is between the peak voltage reference value and the valley voltage reference value, stopping the work of the charge-discharge module.
The peak voltage reference value and the valley voltage reference value are functions of the input voltage of the preceding stage conversion circuit.
The peak voltage reference value and the valley voltage reference value may also be fixed values, and the peak voltage reference value is greater than the valley voltage reference value.
The step 2 further includes a step 21 of controlling the second voltage, detecting the second voltage, and generating a driving signal of a switch in the charge and discharge module using a control logic of a voltage outer loop current inner loop.
The step 3 further includes a step 31 of controlling the first voltage, detecting the first voltage, and generating a driving signal of a switch in the charge and discharge module using a control logic of a voltage outer loop and a current inner loop.
The control method of the active compensation circuit provided by the invention can realize accurate active compensation and reduce voltage fluctuation on the direct current bus.
In order to make the aforementioned and other features and advantages of the invention more comprehensible, embodiments accompanied with figures are described in detail below.
Drawings
FIG. 1 is a schematic diagram of an active compensation circuit according to the present invention;
FIG. 2 is a schematic diagram of the structure of one embodiment of FIG. 1;
fig. 3 is a specific embodiment of the pre-stage conversion circuit, the dc conversion circuit and the charging/discharging module in fig. 2.
Fig. 4 is a circuit diagram of a specific embodiment of a part of the circuit of the control circuit in fig. 2.
FIG. 5 is a circuit diagram illustrating an embodiment of a mode selection module in the control circuit of FIG. 2.
Fig. 6 is a schematic waveform diagram of a part of signals in fig. 4.
Fig. 7 is a schematic waveform diagram of part of signals in fig. 3 and 4.
FIG. 8 is a flowchart of a control method of the active compensation circuit according to the present invention.
Detailed Description
In order to make the purpose and technical solutions of the embodiments of the present invention clearer, the technical solutions of the embodiments of the present invention will be clearly and completely described below with reference to the drawings of the embodiments of the present invention. It is to be understood that the embodiments described are only a few embodiments of the present invention, and not all embodiments. All other embodiments, which can be derived by a person skilled in the art from the described embodiments of the invention without any inventive step, are within the scope of protection of the invention.
The terms "first," "second," "third," "fourth," and the like (if any) in this disclosure are used for distinguishing between similar elements and not necessarily for describing a particular sequential or chronological order. It is to be understood that the terms so used are interchangeable under appropriate circumstances such that the embodiments of the subject matter described herein are, for example, capable of operation in other sequences than those illustrated or otherwise described herein. Further, wherever possible, the same reference numbers are used in the drawings and the description to refer to the same or like parts.
As shown in fig. 1, the present invention provides an active compensation circuit 13, where the active compensation circuit 13 is connected in parallel to a dc bus between a preceding stage conversion circuit 11 and a dc conversion circuit 12, and is connected in parallel to an intermediate dc bus capacitor C1, the active compensation circuit 13 provides active compensation for a capacitor C1, and a control circuit 14 controls a switching element in the active compensation circuit. The pre-conversion circuit 11 is usually a rectification circuit, and the ac voltage Vac passes through the pre-conversion circuit 11, outputs a voltage Vdc1, and is filtered by a capacitor C1 to provide an input voltage for the dc conversion circuit 12; the active compensation circuit 13 has a charging mode in which a valley voltage of the high voltage Vdc1 is pumped and a discharging mode in which C2 is charged, the fluctuation range of the voltage Vdc1 is reduced, and an input voltage with less fluctuation is supplied to the dc conversion circuit 12.
Fig. 2 shows an embodiment of fig. 1, in which the active compensation circuit 23 includes a charging/discharging module 231 and a capacitor C2, and the charging/discharging module realizes energy exchange between the capacitor C1 and the capacitor C2. The control circuit 24 includes a mode selection module 245, the mode selection module 245 outputs a mode signal mode, a value of the mode signal mode is equal to the charging mode signal mode2, the charging control loop 242 outputs a charging current reference value Iref2, the current control module 246 outputs a control signal Vc to the driving module 244 according to the reference value Iref2, and the driving module 244 generates a driving signal S1 for controlling the switches in the charging and discharging module 231; the mode selection module 245 outputs a mode signal mode, the value of the mode signal mode is equal to the discharge mode signal mode1, the discharge control loop 241 outputs a discharge current reference value Iref1, the current control module 246 outputs a control signal Vc to the driving module 244 according to the reference value Iref1, and the driving module 244 generates a driving signal S1 for controlling the switches in the charge-discharge module 231; in shutdown mode, the shutdown control loop 243 outputs a current reference value Iref3, which in a preferred embodiment is equal to zero, Iref 3. The mode selection module 245 selects an operating mode based on the voltage Vdc 1:
the voltage Vdc1 is compared with a valley voltage reference value Vvalley _ ref and a peak voltage reference value Vpeak _ ref, specifically:
(1) when Vdc1< Vvalley _ ref, the mode select module 245 outputs a discharge mode signal mode1, which is when the capacitor C2 discharges to the capacitor C1. The valley voltage reference value Vvalley _ ref may be set to a fixed value or may be set as a function of the AC voltage peak value, facilitating valley regulation according to different AC input voltages.
(2) When Vdc1> Vpeak _ ref, the mode selection module 245 outputs a charge mode signal mode2, which charges the capacitor C2 for the pre-stage conversion circuit 11. The peak voltage reference value Vpeak _ ref can be set to Vvalley _ ref +/Δ V, and can also be set to be a function of the AC alternating voltage peak value, so that the energy storage voltage can be adjusted conveniently according to different AC input voltages.
(3) When Vvalley _ ref < Vdc1< Vpeak _ ref, the mode select module 245 outputs a shutdown mode signal mode 3.
As shown in fig. 7, is a waveform diagram of the key variables in fig. 2:
at time t1, the output voltage Vrec of the preceding stage conversion circuit rises to the valley voltage reference value Vvalley _ ref, the mode selection module 245 outputs the shutdown mode signal mode3, and the charge/discharge module 231 is shutdown.
At time t2, the output voltage Vrec of the pre-stage conversion circuit rises to the peak voltage reference value Vpeak _ ref, the mode selection module 245 outputs the charge mode2 signal, and the charge/discharge module 231 charges the capacitor C2.
At time t3, the output voltage Vrec of the preceding stage conversion circuit drops to the peak voltage reference value Vpeak _ ref, the mode selection module 245 outputs the shutdown mode3 signal, and the charge/discharge module 231 is shutdown.
At time t4, the output voltage Vrec of the preceding stage conversion circuit drops to the valley voltage reference value Vvalley _ ref, the mode selection module 245 outputs the discharge mode1 signal, the capacitor C2 charges the capacitor C1 through the charge/discharge module 231, and the voltage across the high capacitor C1 is pumped.
As shown in fig. 5, an embodiment of the mode selection module 245 is a hysteresis comparator, and the input terminal of the mode selection module 245 receives the Vdc1, the valley voltage reference value valley _ ref of the Vdc1, and the peak voltage reference value Vpeak _ ref of the Vdc1, and determines the output control signal mode after hysteresis comparison, wherein the control signal mode has a value equal to the discharging mode signal mode1, the charging mode signal mode2, or the shutdown mode signal mode3, and determines the operation mode.
Fig. 3 shows a specific implementation of the pre-stage conversion circuit, the dc conversion circuit and the active compensation circuit in fig. 2, the pre-stage conversion circuit 31 is a full-bridge rectification circuit, and includes diodes D1-D4, the input end of the pre-stage conversion circuit 31 is connected in parallel with the ac power source Vac, and the output end is connected in parallel with the capacitor C1. In this embodiment, the dc converter circuit 32 is a flyback converter circuit, and includes a main switching tube Q1, a transformer T1, a capacitor C0, and a switch Q2, and the flyback converter circuit may be a quasi-resonant flyback converter circuit or an active-clamp flyback converter circuit, or may be a flyback converter circuit of other structures. The input end of the dc conversion circuit 32 is connected in parallel with the capacitor C1, and the output end of the dc conversion circuit 32 is connected in parallel with the load. The active compensation circuit 33 is connected in parallel with the dc bus, specifically, in parallel with the intermediate dc bus capacitor C1, and the active compensation circuit 33 provides active compensation for the capacitor C1.
The active compensation circuit 33 in the embodiment shown in fig. 3 includes a charge and discharge circuit 331, and the charge and discharge circuit 331 is a bidirectional BUCK circuit including an inductor L1, a switch Q3, and a switch Q4. And is described with reference to fig. 6.
(1) When Vdc1< Vvalley _ ref, a discharge mode is entered, which is when the capacitor C2 discharges to the capacitor C1. The charge and discharge circuit 331 operates in a buck mode. The Q3 high-frequency switch, Q4 synchronous complementary work or only body diode work, the charge and discharge circuit 331 forms buck step-down circuit. Referring to the waveform of Vdc1 in fig. 6, a high voltage Vdc1 is pumped up to a specified maintenance constant voltage output, and the power output is maintained by the active compensation circuit 33.
(2) When Vdc1> Vpeak _ ref, enter the charging mode, which charges the capacitor C2 for the pre-stage conversion circuit 31. The charge and discharge circuit 331 operates in a boost mode.
(3) When Vvalley _ ref < Vdc1< Vpeak _ ref, the charge and discharge circuit 331 operates in the shutdown mode. Referring to the waveform of Vdc2 in fig. 7, switch Q3 and switch Q4 are turned off, if Vdc1< Vdc2, t3-t4 time period, C2 ends energy storage and maintains voltage, if Vdc1> Vdc2, t1-t2 time period, capacitor C1 charges C2 through the body diode of Q3.
The valley voltage reference Vvalley _ ref is set low and in discharge mode, Q3 is operating at a sustained high frequency. The valley voltage reference Vvalley _ ref, set higher, as the voltage Vdc1 rises and the voltage Vdc2 falls, the switch Q3 enters a through state and Q4 remains off. Therefore, the switching loss of the power tube can be reduced, and the circuit efficiency is improved.
Fig. 4 shows an embodiment of the control circuit 24 of fig. 2. the control circuit 44 includes a discharge control loop 441, a charge control loop 442, a shutdown control loop 443, a current control module 246, and a driver module 444.
The discharge control loop 441 samples the voltage Vdc1, and calculates the first current reference signal Iref1 through the first adjusting unit 4411, the first reference signal Vdc1_ ref, and the first compensating unit 4412. Specifically, the first adjusting unit 4411 is a proportional regulator, and the compensating unit 4412 is a proportional integral regulator, and includes an operational amplifier U1, a resistor R1, a capacitor C3, and a capacitor C4. When the mode signal mode is equal to the discharging mode signal mode1, the current reference value Iref of the current control module 446 is equal to the first current reference signal Iref 1. More specifically, the discharge control loop 441 further includes a switch Q5, and the switch Q5 is connected in series between the output terminal of the first compensation unit 4412 and the current control module 446. When the mode signal mode equals the charge mode signal mode2, the switch Q5 is closed.
The charging control loop 442 samples the voltage Vdc2, and calculates a second error signal Vc2 after the voltage Vdc2 is adjusted by the second adjusting unit 4421 and the second reference signal Vdc2_ ref is adjusted by the second compensating unit 4422. Specifically, the second adjusting unit 4421 is a proportional regulator, and the compensating unit 4422 is a proportional integral regulator, and includes an operational amplifier U2, a resistor R2, a capacitor C5, and a capacitor C6. When the mode signal mode is equal to the charging mode signal mode2, the current reference value Iref of the current control module 446 is equal to the second current reference signal Iref 2. More specifically, the discharge control loop 441 further includes a switch Q6, and the switch Q6 is connected in series between the output terminal of the second compensation unit 4422 and the current control module 446. When the mode signal mode equals the charge mode signal mode1, the switch Q6 is closed.
The shutdown control loop 443, when the shutdown mode signal mode3 is asserted, sets the current reference value Iref3 to zero, which includes a switch Q7, a resistor R5, a capacitor C7, and a switch Q8 in the embodiment of the present invention. Switch Q7 is closed, switch Q8 is closed, and Iref3 is zero when the shutdown mode signal mode3 is active. The resistor R5 and the capacitor C7 are connected in series between the positive pole and the negative pole of the auxiliary power supply to provide soft start for the active compensation circuit 23.
The present invention further includes a limiter LIM1, and the first current reference signal Iref1 and the second current reference signal Iref2 are provided to the current control module 446 after being limited.
The current control module 446 generates a control signal Vc according to the current IL1 (shown in fig. 3) and the current reference value Iref, and the control signal Vc generates a driving signal S1 for controlling the switching device in the charge-discharge module 231 through the driving module 444. In an embodiment of the invention, the current control module 446 includes an operational amplifier U3, the operational amplifier U3 generates the peak current control signal Vc, and the driving module 444 includes an RS flip-flop generating the PWM signal. Taking the fixed frequency case as an example, when a clock signal clock is detected, and the capacitor C2 discharges to the capacitor C1, the current IL1 rises, and when the current IL1 sampling signal is superposed with the slope compensation signal slope and reaches Iref, the RS flip-flop is set low, so that the RS flip-flop outputs a PWM signal with a certain duty ratio. The PWM signal generates a pair of complementary PWM signals S1 containing dead zone through a dead zone circuit U5,
And then the final driving signal SQ3 and the final lower tube driving signal SQ4 are obtained through the conversion circuit U6.
The converter U6 will distribute S1,
The corresponding relation with Q3 and Q4 specifically includes:
(1) a discharging mode: q3 corresponds to
Q4 corresponds to S1;
(2) and (3) charging mode:q3 for S1 and Q4 for
Referring back to FIG. 6, after IL1 reaches the peak, the Q3 driving signal SQ3 corresponds to the PWM signal generated
Switch Q3 is closed and switch Q4 drives signal SQ4Corresponding to S1, the lower pipe is opened; current IL1 freewheels through switch Q4 and current IL1 drops. When the next clock signal is detected, the circuit enters a new duty cycle. The transistor Q8, the resistor R5, and the capacitor C7 form a soft start circuit, which may be in other circuit modes.
Fig. 8 shows a flow chart of a control method of an active compensation circuit according to the present invention, which is integrated in the control circuit 14 and can be implemented in an analog or digital manner, for controlling the active compensation circuit shown in fig. 1.
in step 806, when the voltage Vdc1 is between the peak voltage reference value and the valley voltage reference value, the control unit controls the charging and discharging module 131 to stop regulating.
Step 803 further includes detecting voltage Vdc2, and generating driving signals for the switches in charge/discharge module 131 using the control logic of the voltage outer loop current inner loop.
Step 805 above further includes detecting voltage Vdc1, and using the control logic of the voltage outer loop current inner loop to generate the driving signals for the switches in charge and discharge module 131.
The control scheme of the invention can effectively control the precision of active compensation and achieve good control effect.
Although the present invention has been described with reference to the above embodiments, it should be understood that various changes and modifications can be made therein by those skilled in the art without departing from the spirit and scope of the invention.
Claims (19)
1. An active compensation control circuit is used for controlling an active compensation circuit, the active compensation circuit is connected in parallel with a direct current bus between a preceding stage conversion circuit and a direct current conversion circuit and provides active compensation for a first capacitor connected in parallel on the direct current bus, it is characterized in that the active compensation circuit comprises a charge-discharge module and a second capacitor, the charge-discharge module is connected in parallel between the first capacitor and the second capacitor, the control circuit controls the charge and discharge module, the control circuit includes a mode selection module that samples a first voltage across the first capacitor, and outputs a working mode signal, wherein the working mode signal is a charging mode signal when the first voltage is greater than the peak voltage reference value, the control circuit controls a second voltage at two ends of the second capacitor according to the charging mode signal; when the first voltage is smaller than the valley voltage reference value, the working mode signal is a discharging mode signal, and the control circuit controls the first voltage according to the discharging mode signal; when the first voltage is between the peak voltage reference value and the peak voltage reference value, the working mode signal is a shutdown mode signal, and the control circuit controls the charging and discharging module to be shut down according to the shutdown mode signal.
2. The active compensation control circuit of claim 1, further comprising a discharge control loop and a current control module, wherein the discharge control loop operates when the discharge mode signal is active, the discharge control loop samples the first voltage and compares the first voltage with a first reference voltage to generate a first current reference signal, and the current control module generates a control signal for a switch in the charge and discharge module based on the first current reference signal.
3. The active compensation control circuit of claim 2, further comprising a charge control loop, wherein the charge control loop operates when the charge mode signal is active, the charge control loop samples the second voltage and compares the second voltage with a second reference voltage to generate a second current reference signal, and the current control module generates a control signal for a switch in the charge/discharge module according to the second current reference signal to control the second voltage.
4. The active compensation control circuit of claim 3, further comprising a shutdown control loop, wherein the shutdown control loop operates when the shutdown control signal is active, the shutdown control loop outputs a third current reference signal, the third current reference signal is zero, and the current control module generates the control signal for turning off the switch in the charge and discharge module according to the third current reference signal.
5. The active compensation control circuit of claim 4, further comprising a driving module, wherein the driving module is connected to an output terminal of the current control module, and converts a control signal output by the current control module into a driving signal for driving a switch in the charge/discharge module.
6. The active compensation control circuit of claim 2, wherein the charge control loop comprises a proportional-integral regulator.
7. The active compensation control circuit of claim 3, wherein the discharge control loop comprises a proportional-integral regulator.
8. The active compensation control circuit of claim 5, wherein the first current reference value is connected to the current control module through a fifth switch, the second current reference value is connected to the current control module through a sixth switch, the fifth switch is turned on and the sixth switch is turned off when the operation mode signal is in the discharging mode, and the fifth switch is turned off and the sixth switch is turned on when the operation mode signal is in the charging mode.
9. The active compensation control circuit of claim 8, wherein the first current reference value or the second current reference value is output to the current control module after being clipped by the clipping processor.
10. The active compensation control circuit of claim 1, wherein the mode selection module comprises a hysteresis comparator, the positive input terminal of the hysteresis comparator is connected to the first voltage, and the negative input terminal of the hysteresis comparator is connected to the peak voltage reference and the valley voltage reference, respectively.
11. The active compensation control circuit of claim 10, wherein an output of the hysteresis comparator is coupled to control terminals of the fifth, sixth and seventh switches.
12. The active compensation control circuit of claim 4, wherein the shutdown control loop comprises an eighth switch that is normally open, and wherein the seventh switch is closed to connect the output of the third current reference signal to ground.
13. The active compensation control circuit of claim 12, wherein the shutdown control loop further comprises a fifth resistor, a seventh capacitor, and a seventh switch, the fifth resistor and the seventh capacitor are connected in series between the auxiliary power source and the ground, a voltage between the positive terminal of the seventh capacitor and the ground provides a driving signal for the eighth switch to control the eighth switch to be turned off, the seventh switch is connected in parallel with the seventh capacitor, and a control terminal of the seventh switch is connected with the output terminal of the mode selection module.
14. The active compensation control circuit of claim 5, wherein the driving module further comprises a converter, and the converter adjusts the corresponding relationship between the driving signal and the switch of the charge/discharge module according to the operation mode signal.
15. A control method of an active compensation circuit is used for controlling the active compensation circuit, the active compensation circuit is connected in parallel with a direct current bus between a preceding stage conversion circuit and the direct current conversion circuit and provides active compensation for a first capacitor connected in parallel on the direct current bus, the active compensation circuit comprises a charge-discharge module, a second capacitor and a control circuit, the charge-discharge module is connected in parallel between the first capacitor and the second capacitor, the control circuit controls the charge-discharge module, and the control method is integrated in the control circuit and comprises the following steps:
step 1, detecting a first voltage at two ends of a first capacitor;
step 2, the first voltage is larger than the peak voltage reference value, the second voltage at two ends of the second capacitor is controlled, and the preceding stage conversion circuit outputs power to the second capacitor through the charge-discharge module;
step 3, the first voltage is smaller than the valley voltage reference value, the output power of the second capacitor to the first capacitor through the charge-discharge module is controlled, and the first voltage at two ends of the first capacitor is controlled;
and 4, when the first voltage is between the peak voltage reference value and the valley voltage reference value, stopping the work of the charge-discharge module.
16. The active compensation circuit control method of claim 15, wherein the peak voltage reference and the valley voltage reference are functions of an input voltage of a preceding stage.
17. The active compensation circuit control method of claim 15, wherein the peak voltage reference value and the valley voltage reference value are fixed values, and the peak voltage reference value is greater than the valley voltage reference value.
18. The active compensation circuit control method of claim 15, wherein the step 2 further comprises the step 21 of controlling the second voltage, detecting the second voltage, and generating the driving signal of the switch in the charge/discharge module using the control logic of the voltage outer loop current inner loop.
19. The active compensation circuit control method of claim 15, wherein the step 3 further comprises the step 31 of controlling the first voltage, detecting the first voltage, and generating the driving signal of the switch in the charge/discharge module using the control logic of the voltage outer loop current inner loop.
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