CN113224536A - Broadband dual-polarized dielectric patch antenna based on metal column - Google Patents

Broadband dual-polarized dielectric patch antenna based on metal column Download PDF

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Publication number
CN113224536A
CN113224536A CN202110574838.1A CN202110574838A CN113224536A CN 113224536 A CN113224536 A CN 113224536A CN 202110574838 A CN202110574838 A CN 202110574838A CN 113224536 A CN113224536 A CN 113224536A
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China
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dielectric
dielectric plate
antenna
equal
patch
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张立
曹志勋
翁子彬
鲁昊
孙季秋
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Xidian University
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Xidian University
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0414—Substantially flat resonant element parallel to ground plane, e.g. patch antenna in a stacked or folded configuration
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q25/00—Antennas or antenna systems providing at least two radiating patterns
    • H01Q25/04—Multimode antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/045—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means

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Abstract

The invention discloses a broadband dual-polarized antenna of a dielectric patch resonator based on a metal cylinder, which mainly solves the problem that the working frequency band of the existing low-profile dual-polarized dielectric resonator antenna is narrow. The dielectric patch comprises a dielectric patch (1), a first dielectric plate (2), a second dielectric plate (5) and a third dielectric plate (7). A first feeder line (4) is printed on the upper surface of the second dielectric plate (5); the upper surface and the lower surface of the third dielectric plate are respectively printed with a metal floor (6) and a second feeder line (8); a cross coupling gap (9) is etched on the metal floor, and a vertical strip-shaped gap and two feeder lines (4, 8) form a gap coupling structure; through holes (10) and through holes (11) are respectively formed in the first dielectric plate and the second dielectric plate along the diagonal lines of the first dielectric plate and the second dielectric plate, and the middle parts of the lower surfaces of the dielectric patches are connected with the middle part of the metal floor through metal cylinders (3). The invention has wide working frequency band and low section and can be applied to a base station communication system.

Description

Broadband dual-polarized dielectric patch antenna based on metal column
Technical Field
The invention belongs to the technical field of antennas, and particularly relates to a broadband dual-polarized dielectric patch antenna which can be used for a base station communication system.
Background
Microstrip patch antennas and dielectric resonator antennas have been extensively studied by researchers as two very important types of antennas in modern wireless communications. The microstrip patch antenna has the advantages of high gain, light weight, small volume, low profile and easy processing, so that the microstrip patch antenna has very wide application in wireless communication, and various technologies have been developed to overcome the defect of narrow bandwidth of the microstrip patch antenna. However, with the development of modern wireless communication technology, the disadvantage of high conductor loss of the microstrip patch antenna at high frequency becomes more and more remarkable. Thus, the dielectric resonator antenna has been widely studied due to its advantages of high radiation efficiency, low conductor loss, multi-mode, easy excitation, flexible design, and the like.
The dual-polarized antenna has the advantages of improving communication capacity, reducing multipath effect and the like, and particularly can greatly save the number of antennas in the aspect of base station application. In recent years, many dual-polarized dielectric resonator antennas have been proposed, one of which is to implement dual polarization by using two mutually perpendicular feed structures for a cylindrical dielectric resonator. Another is to realize dual polarization by using a dielectric resonator of a special shape having a vertical structure, such as a clover type and a cross type. However, the antenna of both structures has a problem of high profile. In view of the disadvantages of the dielectric resonator antenna, a dielectric patch antenna has been proposed in recent years, in which the electric field distribution of the dielectric patch antenna is concentrated inside the dielectric resonator, and the electric field distribution is more concentrated between the bottom of the dielectric patch and the metal floor. The mechanism of operation is similar to that of a microstrip patch antenna, which results in a dielectric patch antenna having a lower profile than a dielectric resonator antenna. On the other hand, the dielectric patch antenna keeps the characteristics of low conductor loss, high radiation efficiency and multiple modes of the dielectric resonator antenna. Therefore, the dielectric patch antenna has wide application prospect in a millimeter wave band with narrow installation space and increasingly prominent conductor loss problem.
Chinese patent No. CN 110676589B discloses a differential dual-polarized dielectric patch antenna, which adopts a three-layer structure of a dielectric patch, a first dielectric plate and a second dielectric plate, and a floor and a differential feeder are respectively located at the top and bottom of the second dielectric plate. High-order mode TM excited by introducing four grounding columns between bottom periphery of dielectric patch and top of second dielectric plate132Modes and enables TM121The mode shifts to high frequencies. By merging TMs121Mode and TM132Mode, a gain of up to 9dBi is achieved. But due to the two modes of operation TM of the antenna121And TM132The impedance bandwidth is only 4.27%, the working performance is poor, the requirement of the broadband cannot be met, and the application range is limited.
Disclosure of Invention
The invention aims to overcome the defects of the existing dual-polarized dielectric patch antenna and provides a broadband dual-polarized dielectric patch antenna so as to improve the impedance bandwidth, improve the working performance of the antenna and expand the application range of the antenna.
In order to achieve the purpose, the broadband dual-polarized dielectric patch antenna based on the metal cylinder comprises a dielectric patch, a first dielectric plate, the metal cylinder, a second dielectric plate and a metal floor, and is characterized in that:
a first feeder line is printed on the upper surface of the second dielectric plate, and a third dielectric plate is tightly attached to the lower part of the second dielectric plate;
the metal floor is printed on the upper surface of the third dielectric plate, and a second feeder line is printed on the lower surface of the third dielectric plate; a cross coupling gap formed by two mutually vertical strip-shaped gaps is etched on the metal floor, and the vertical strip-shaped gaps and a first feeder line and a second feeder line which are respectively positioned on the upper side and the lower side of the metal floor form a gap coupling structure so as to improve impedance bandwidth;
the first feeder line and the second feeder line are respectively composed of T-shaped power dividers, so that the shielding of a coupling gap parallel to the tail end of the feeder line is avoided through a tail end branch structure of the first feeder line and the second feeder line, and the isolation degree is improved.
Furthermore, through holes with the same radius and the same axis are symmetrically arranged on the first dielectric plate and the second dielectric plate along the diagonal lines of the first dielectric plate and the second dielectric plate respectively, and the metal cylinders connect the lower surfaces of the dielectric patches with the metal floor through the through holes.
Furthermore, the branch structures at the tail ends of the first feed line and the second feed line are respectively symmetrical to the center line of the strip-shaped gap of the first feed line and the second feed line.
Furthermore, the dielectric patch is of a square structure and is positioned in the center of the upper surface of the first dielectric plate, and two adjacent edges of the dielectric patch are respectively placed along two polarization directions.
Compared with the prior art, the invention has the following advantages:
1) according to the invention, the first feeder line is printed on the upper surface of the second dielectric plate, the third dielectric plate is tightly attached to the lower part of the second dielectric plate, the metal floor is printed on the upper surface of the third dielectric plate, and the second feeder line is printed on the lower surface of the third dielectric plate, so that enough space is provided for the design of the first feeder line and the second feeder line, the use of an additional feed structure is avoided, and meanwhile, the coupling between the first feeder line and the second feeder line is effectively isolated.
2) The first feeder line and the second feeder line are formed by the T-shaped power divider, and the tail end branch structure of the first feeder line and the second feeder line avoids shielding a coupling gap parallel to the tail end of the feeder lines, so that the isolation degree of the antenna is improved.
3) The invention can excite transverse magnetic mode TM with 1 upper half period number on x and z axis and 0 upper half period number on y axis because of etching a cross coupling gap composed of two mutually perpendicular strip gaps on the metal floor to make the strip gap in the perpendicular direction and the first and second feed lines respectively positioned on the upper and lower sides of the metal floor form a gap coupling structure101And transverse magnetic mode TM with 1 half period number on x and z axes and 2 half period number on y axis121(ii) a Meanwhile, the metal cylinder 3 is connected between the middle part of the lower surface of the dielectric patch and the middle part of the metal floor 6, so that TM with longer frequency distance can be obtained101And TM121The mode is respectively translated to high frequency and low frequency, so that the impedance bandwidth is improved; this is achieved byExternal cause TM101And TM121The modes can be correspondingly combined in an orthogonal mode, so that the dual-polarization characteristic is realized.
Drawings
FIG. 1 is an exploded view of an embodiment of the present invention;
FIG. 2 is a side view of an embodiment of the present invention;
FIG. 3 is a top view of an embodiment of the present invention;
FIG. 4 is a schematic structural diagram of the first feed line of FIG. 1;
FIG. 5 is a schematic structural diagram of a second feed line of FIG. 1;
FIG. 6 is a graph of reflection coefficient and gain when an embodiment of the present invention is excited only by Port 1;
FIG. 7 is a graph of reflection coefficient and gain for an embodiment of the present invention excited only by port 2;
FIG. 8 is a graph of the isolation between Port 1 and Port 2 of an embodiment of the present invention;
FIG. 9 is an antenna radiation pattern at different frequencies when an embodiment of the present invention is excited only by port 1;
FIG. 10 is an antenna radiation pattern at different frequencies when an embodiment of the present invention is excited only by port 2;
Detailed Description
The embodiments and effects of the present invention will be further described with reference to the accompanying drawings.
Referring to fig. 1, 2 and 3, the broadband dual-polarized dielectric patch antenna of this embodiment is sequentially stacked from top to bottom with a dielectric patch 1, a first dielectric plate 2, a second dielectric plate 5 and a third dielectric plate 7. The dielectric patch 1 is of a square structure and is positioned in the center of the upper surface of the first dielectric plate 2, and two adjacent edges of the dielectric patch are respectively placed along two polarization directions. The second dielectric board 5 is a single-sided printed board, the upper surface of which is printed with the first feeder line 4, and the third dielectric board 7 is a double-sided printed board, the upper and lower surfaces of which are printed with the metal floor 6 and the second feeder line 8, respectively. The metal floor 6 is etched with a cross-shaped coupling slot 9 consisting of two mutually perpendicular strip-shaped slots. Four through holes with the same radius are symmetrically arranged on the first dielectric plate 2 and the second dielectric plate 5 along the diagonal lines of the first dielectric plate and the second dielectric plate respectively and are marked as a through hole 10 and a through hole 11 respectively, the four through holes on the first dielectric plate 2 and the four through holes on the second dielectric plate 5 are coaxial in pairs, and metal cylinders 3 with the same radius as the through holes penetrate through the through holes and are used for connecting the middle part of the lower surface of the dielectric patch 1 with the middle part of the metal floor 6.
The dielectric patch 1 has a dielectric constant epsilonrThe value of epsilon is more than or equal to 10rLess than or equal to 90, side length of ldThe value of which is less than or equal to l and is 12mmdLess than or equal to 36mm and thickness hdThe value of h is not less than 0.8mmdCeramic material with a diameter less than or equal to 2 mm. This example uses, but is not limited to, a dielectric constant of 45, a loss tangent of 0.001, and a side length of ld24mm, thickness hd1.4mm ceramic patch.
The first dielectric plate 2, the second dielectric plate 5 and the third dielectric plate 7 have dielectric constants epsilon1The value of epsilon is more than or equal to 2.21Less than or equal to 4, side length lgThe value of l is not less than 30mmgA dielectric plate with a thickness less than or equal to 80 mm. Wherein, the thickness h of the first dielectric plate 21The value of h is not less than 0.2mm1Not more than 6mm, and the thickness h of the second dielectric plate 5 and the third dielectric plate 72And h3Equal, i.e. 0.2mm ≤ h2＝h3Less than or equal to 4 mm. In this embodiment, but not limited to, F4B, a dielectric plate with a dielectric constant of 3.5 and a loss tangent of 0.007, and the side lengths of the first dielectric plate 2, the second dielectric plate 5 and the third dielectric plate 7 are all lg55mm in thickness, h1＝1.0mm、h2＝h3＝0.8mm。
The width w of the cross-shaped gap 9sEqual and 0.2mm ≤ wsNot more than 1.8mm, and the lengths in the x and y directions are respectively ls1And ls2The value of l is not less than 8mms1≤20mm，6mm≤ls2Less than or equal to 18mm, with this embodiment using, but not limited to, ws0.8mm, length ls115.4mm and ls2＝10.6mm。
The radius r of the through hole 10 is equal to that of the through hole 11, r is more than or equal to 0.2mm and less than or equal to 0.5mm, and the distance d between two adjacent through holes on the same dielectric platepD is not less than 3mmpNot more than 12mm, and is not limited to 0.35mm in r and dp＝6.3mm。
The distance between the metal cylinders 3 is equal to the distance between two adjacent through holes on the same dielectric plate, the radius is equal to the radius of the through hole 10 and the radius of the through hole 11, and the height is the sum of the heights of the first dielectric plate 2 and the second dielectric plate 5. The metal cylinder 3 is connected with the middle part of the lower surface of the dielectric patch and the middle part of the metal floor 6, so that the number of the upper half cycles of the x axis and the z axis is 1, and the number of the upper half cycles of the y axis is 0101The electric field of the mode is concentrated in the middle of the antenna, which is equivalent to reducing the side length l of the dielectric patchdThereby promoting TM101Of (c) is detected. Simultaneously, the number of the first half cycles on the x axis and the z axis is 1, and the number of the first half cycles on the y axis is 2121The electric field distribution of the mode also becomes equal to TM101The modes are similar, thereby reducing TM121The frequency of the mode.
Referring to fig. 4 and 5, the first feeder line 4 and the second feeder line 8 are each formed of a T-type power divider and are located on both sides of the metal floor 6. The two branches at the lower end of the strip-shaped coupling structure and the strip-shaped gap in the vertical direction form a gap coupling structure together, the branch structures at the lower end are respectively symmetrical to the central line of the strip-shaped gap of the strip-shaped coupling structure, and the two branch structures are positioned at two sides of the strip-shaped coupling gap in the parallel direction and do not shield the strip-shaped coupling gap in the parallel direction.
In the first feeder line 4, the transmission line width of the first section is w1Length is s4The value ranges are respectively 0.8mm and less than or equal to w1≤2.6mm，2mm≤s4Less than or equal to 20 mm; the widths of two branch lines in the second section of transmission line are w2At a spacing of s5The length in the y-axis direction is s3The value ranges are respectively not less than 0.2mm and not more than w2≤1.6mm，2mm≤s5≤18mm，1mm≤s3Less than or equal to 9 mm; the two branch lines in the third section of transmission line are as wide as the first section of transmission line, and the length of the third section of transmission line is s2The value range is s is more than or equal to 1.8mm2Less than or equal to 12 mm; the widths of two branch lines in the fourth section of transmission line are all w4At a spacing of s6All lengths being s1The value ranges are respectively not less than 0.2mm and not more than w4≤1.6mm，0.5mm≤s6≤4mm，4mm≤s1Less than or equal to 20 mm. This embodiment uses but is not limited to w1＝1.8mm，s4＝10mm，w2＝0.9mm，s5＝9.1mm，s3＝4.5mm，s2＝5.9mm，w4＝0.8mm，s6＝2.0mm，s1＝11.1mm。
The second feeder line 8 has the 1 st transmission line with the same width and length as the first transmission line in the first feeder line 44The value range is 2mm < l4Less than or equal to 20 mm; two branch lines in the 2 nd section transmission line are as wide as the second section transmission line in the first feeder line 4, and the distance between the two branch lines is l5The length in the y-axis direction is l3The value ranges are respectively 6mm < l5≤24mm，1mm≤l3Less than or equal to 9 mm; two branch lines in the 3 rd section transmission line are as wide as the first section transmission line in the first feeder line 4, and the length of the two branch lines is l2The value range is; the widths of two branch lines in the fourth section of transmission line are all w3At a pitch of l6All lengths are l1The value ranges are respectively 0.8mm and less than or equal to w3≤2.2mm，0.5mm≤l6Not more than 4mm and not more than 4mm1Less than or equal to 20 mm. This embodiment uses but is not limited to4＝10mm，l5＝14.3mm，l3＝5.9mm，l2＝4.6mm，w3＝1.5mm，l6＝2.5mm，l1＝11.2mm。
The effect of the invention can be further explained by combining the simulation result:
simulation conditions
Simulation software: using HFSS — 19.0 software, the feed of the first feed line 4 was set to port 2 and the feed of the second feed line 8 was set to port 1.
Second, simulation content
Simulation 1, reflection coefficient S when the antenna of this embodiment is excited only by port 1 under the above conditions11The parameters and gain parameters were calculated by simulation, and the results are shown in fig. 6. From FIG. 6, see S11The standard of less than or equal to-10 dB, the impedance bandwidth of the antenna provided by the embodiment of the invention when only excited by the port 1 is 5.10 GHz-5.93 GHz, the relative bandwidth is 15.05%, and the maximum gain in the band is 9.05 dBi.
Simulation 2, under the above conditionsFor the present embodiment, the antenna is excited only by the port 211The parameters and gain parameters were calculated by simulation, and the results are shown in fig. 7. From FIG. 7, see S11The standard of less than or equal to-10 dB, the impedance bandwidth of the antenna provided by the embodiment of the invention when only excited by the port 2 is 5.05 GHz-5.83 GHz, the relative bandwidth is 14.34%, and the maximum gain in the band is 8.65 dBi.
Simulation 3, in the above conditions, simulation calculation was performed on the isolation between port 1 and port 2 of the antenna of this embodiment, and the result is shown in fig. 8. As can be seen from fig. 8, the minimum isolation between port 1 and port 2 of the antenna of the embodiment of the present invention is 41dB in band.
Simulation 4, under the above conditions, a far-field radiation pattern at frequencies of 5.25GHz and 5.75GHz when the antenna of the present embodiment is excited only by the port 1 is subjected to simulation calculation, and the result is shown in fig. 9, where: fig. 9(a) is the far-field radiation pattern of the example antenna at a frequency of 5.25GHz, and fig. 9(b) is the far-field radiation pattern of the example antenna at a frequency of 5.75 GHz. It can be seen from fig. 9 that the cross-polarization of the E-plane and H-plane antennas is below-30 dB when excited by port 1 only at frequencies of 5.25GHz and 5.75 GHz.
Simulation 5, under the above conditions, a far-field radiation pattern at frequencies of 5.25GHz and 5.75GHz when the antenna of the present embodiment is excited only by port 2 is subjected to simulation calculation, and the result is shown in fig. 10, where: fig. 10(a) is a far-field radiation pattern of the embodiment antenna at a frequency of 5.25GHz, and fig. 10(b) is a far-field radiation pattern of the embodiment antenna at a frequency of 5.75 GHz. It can be seen from fig. 10 that the E-plane and H-plane antennas cross-polarize less than-15 dB when excited only by port 2 at frequencies of 5.25GHz and 5.75 GHz.
The simulation results show that the antenna has wider impedance bandwidth, relatively higher in-band gain and high isolation.
The above description is only an example of the present invention and does not constitute any limitation to the present invention, and it is obvious to those skilled in the art that various modifications and changes in form and detail may be made without departing from the principle and structure of the present invention after understanding the present invention, but those modifications and changes based on the idea of the present invention are still within the scope of the claims of the present invention.

Claims (8)

1. The utility model provides a broadband dual polarization dielectric patch antenna based on metal cylinder, includes dielectric patch (1), first dielectric plate (2), metal cylinder (3), second dielectric plate (5) and metal floor (6), its characterized in that:
a first feeder line (4) is printed on the upper surface of the second dielectric plate (5), and a third dielectric plate (7) is tightly attached to the lower part of the second dielectric plate (5);
the metal floor (6) is printed on the upper surface of a third dielectric board (7), a second feed line (8) is printed on the lower surface of the third dielectric board (7), a cross-shaped coupling gap (9) formed by two mutually vertical strip-shaped gaps is etched on the metal floor (6), and the vertical strip-shaped gaps and a first feed line (4) and a second feed line (8) which are respectively positioned on the upper side and the lower side of the metal floor (6) form a gap coupling structure to improve impedance bandwidth;
the first feeder line (4) and the second feeder line (8) are respectively composed of T-shaped power dividers, so that the shielding of a coupling gap parallel to the tail end of the feeder line is avoided through a tail end branch structure of the first feeder line and the second feeder line, and the isolation degree of the antenna is improved;
the metal cylinder (3) is connected between the middle of the lower surface of the medium patch (1) and the middle of the metal floor (6).
2. The antenna of claim 1, wherein: the first dielectric plate (2) and the second dielectric plate (5) are symmetrically provided with through holes (10) and through holes (11) which are the same in radius and coaxial along the diagonal lines of the first dielectric plate and the second dielectric plate respectively, and the middle of the lower surface of the dielectric patch (1) is connected with the middle of the metal floor (6) through the through holes (10) and the through holes (11) by the metal cylinder (3).
3. The antenna of claim 1, wherein: the branch structures at the tail ends of the first feed line (4) and the second feed line (8) are respectively symmetrical to the center line of the strip-shaped gap of the first feed line and the second feed line.
4. The antenna of claim 1, wherein: the dielectric patch (1) is of a square structure and is positioned in the center of the upper surface of the first dielectric plate (2), and two adjacent edges of the dielectric patch are respectively placed along two polarization directions.
5. The antenna of claim 1, wherein: the side lengths of the first dielectric plate (2), the second dielectric plate (5) and the third dielectric plate (7) are equal.
6. The antenna of claim 1, wherein: the thickness h1 of the first dielectric slab (2) is not less than 0.2mm and not more than h1Less than or equal to 6 mm; thickness h of the second dielectric plate (5) and the third dielectric plate (7)2And h3Equal, i.e. 0.2mm ≤ h2＝h3≤4mm。
7. The antenna of claim 1, wherein: the metal cylinder (3) is connected with the middle part of the lower surface of the medium patch and the middle part of the metal floor (6), the radius of the metal cylinder is equal to the radius r of the through hole, and r is more than or equal to 0.2mm and less than or equal to 0.5 mm; the distance between the metal cylinders 3 and the distance d between two adjacent through holes on the same dielectric platepEqual, i.e. d is not less than 3mmp≤12mm。
8. The antenna of claim 1, wherein: the width w of the cross-shaped gap (9)sEqual, x and y axial lengths are ls1And ls2The value range is not less than 0.2mm and not more than ws≤1.8mm，8mm≤ls1≤20mm，6mm≤ls2≤18mm。
CN202110574838.1A 2021-05-26 2021-05-26 Broadband dual-polarized dielectric patch antenna based on metal column Pending CN113224536A (en)

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Application publication date: 20210806