CN113132028B - IQ correction method for originating terminal - Google Patents

IQ correction method for originating terminal Download PDF

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CN113132028B
CN113132028B CN202110447884.5A CN202110447884A CN113132028B CN 113132028 B CN113132028 B CN 113132028B CN 202110447884 A CN202110447884 A CN 202110447884A CN 113132028 B CN113132028 B CN 113132028B
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CN113132028A (en
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马雅男
邹建
李振川
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Chengdu Jovian Technology Exploitation Co ltd
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/10—Monitoring; Testing of transmitters
    • H04B17/11—Monitoring; Testing of transmitters for calibration
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits

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Abstract

The invention discloses an IQ correction method for an originating terminal, which comprises the following steps: s1, the transmitting end respectively sends a plurality of groups of signals TX, and the plurality of groups of signals TX enter a receiving channel for processing after self-multiplication to respectively obtain a plurality of groups of signals RX; s2, after cross-correlation is carried out between multiple groups of signals RX and multiple groups of sinusoidal signals generated at the receiving end, a signal corresponding to the maximum value of a cross-correlation curve is taken for delay phase estimation and the like; the invention can correct IQ imbalance of the signal at the transmitting end, simultaneously avoids the influence of IQ imbalance at the receiving end on the system, improves the signal-to-noise ratio of the signal at the transmitting end, has high realizability, can effectively reduce the influence of mirror image components, improves the performance of the system, and has strong practical value and the like.

Description

IQ correction method for originating terminal
Technical Field
The present invention relates to the field of communications, and more particularly, to an originating IQ correction method.
Background
With the development of wireless communication, higher and higher requirements are put on miniaturization, easy integration, and the like of devices [1 ]. The development of industry is severely restricted by the traditional super-extrapolation structure transceiver at present, and the novel zero intermediate frequency transceiver is gradually paid attention to by people to become a hotspot of research in the years with the advantages of simple structure, easy integration, low power consumption and small volume [ 2-4 ]. However, in the practical application process, due to the limitation of device processes, the devices such as filters, amplifiers, mixers and the like on the in-phase branch and the quadrature branch cannot be completely consistent, and the two outputs of the local oscillator signals cannot be completely orthogonal, so that the output of the I-path response signal and the Q-path response signal is unbalanced, which means that the signal spectrum has image components, and the image signals reach a certain power, which causes serious distortion of the main signal, further reduces the dynamic range of the system, and deteriorates the overall performance of the system [5 ]. Therefore, how to eliminate the IQ imbalance phenomenon is a hot problem in current research, and has certain practical significance.
Currently, there are two types of analog domain and digital domain for IQ imbalance correction. The analog domain improves the consistency of the devices by optimizing the circuit structure and changing the layout mode of the devices, thereby reducing the influence of IQ imbalance [6], but the damage caused by IQ imbalance still cannot be eliminated by utilizing the mode. Subsequently, document [7] reports a compensation mode of a digital domain, and a mode of inserting a training sequence into a signal is utilized to estimate IQ amplitude and phase imbalance parameters for compensation. In recent years, people introduce concepts such as a channel estimation algorithm, a sparse matrix algorithm, a simulated annealing algorithm and the like based on a least square method into an IQ correction method to obtain favorable performance [ 8-10 ], but due to the complex structure and high implementation difficulty, the IQ correction method cannot be used in practice for commercial use at present, so that the search for a simple and easy-to-implement algorithm is an urgent need at present.
The classic structure of a zero-if transmitter is shown in fig. 1, a generated baseband signal is split into an I path and a Q path, which enter an upper path and a lower path respectively, an upper path signal is converted into an analog signal by a DAC and then multiplied by cos ω t, and a lower path signal is multiplied by-sin ω t carrier wave after passing through a DAC module, where ω ═ 2 π f, f represents a carrier frequency, and through this mixing process, the transmitter up-converts the baseband signal with a center frequency of zero to a center frequency point of a radio frequency signal. Under an ideal model, the amplitude-frequency and phase-frequency characteristics of the I path and the Q path should be completely consistent, the local oscillation amplitudes of the Q path and the I path are the same, and the phase difference is 90 degrees. However, the above conditions are very difficult to satisfy for process reasons, and therefore, an IQ imbalance phenomenon exists, and a model of this case is shown in fig. 2.
In the figure:
Figure GDA0003635319780000021
wherein x isI(t) and xQ(t) represents the I and Q path frequency conversion output, I and Q represent the I and Q path input signal, IDCAnd QDCCharacterizing the DC component, ω, of the paths I and QLO＝2πfLO，fLORepresenting the carrier frequency, g represents the amplitude deviation of the I and Q responses,
Figure GDA0003635319780000022
the phase deviation of the I-path response and the Q-path response is reflected. Combining the above formulas to obtain an output result as follows:
Figure GDA0003635319780000023
therefore, according to the above formula, the obtained equivalent model of the transmitting IQ imbalance is shown in fig. 3.
For a transmitting-end system, IQ imbalance is unavoidable, and causes the phenomenon are various, including IQ imbalance caused by process problems of a plurality of devices such as a modulator, a local oscillator, a filter, a DAC and the like. The most remarkable characteristic of this phenomenon is that image frequency components are generated for the original signal, thereby affecting the signal-to-noise ratio of the originating signal. Therefore, how to reduce the influence of IQ imbalance and improve the system performance of the transmitter is a current research focus and has important practical significance.
The existing references:
[1] the development and application of data communication microsatellite constellation systems [ J ] spacecraft engineering, 2011, 2: 66.
[2] chiffon zero intermediate frequency transmitter design and implementation [ J ] electronics, 2014, 27 (3): 73.
[3]SLUK A,WALSH D.Transcutaneous electrical nerve stimulation:basic science mechanisms and clinical effectiveness[J].J Pain,2003,4(3)：109.
[4]PECKHAM P H,KNUTSON J S.Functional electrical stimulation for neuromuscular applications[J].Annu Revi Biomed Engineer,2005,7(7)：327.
[5]EVERETT E,SAHAI A,SABHARWAL A,et al.Passiveself-interference suppression for full-duplex infrastructure nodes[J].IEEE Transactions on Wireless Communications,2014,13(2)：680.
[6] cao peng, feiyanchun, analysis and optimization design of leakage between sideband of direct quadrature up-conversion and local oscillator [ J ] military science, 2004, 25 (6): 712.
[7]GU C F,LAW C L,WU W.Time domain IQ imbalance compensation for wideband wireless systems[J].IEEE Communications Letters,2010,14(6):539.
[8]WANG J,YU H,WU Y,et al.Pilot optimization and power allocation for OFDM-based full-duplex relay networks with IQ-imbalances[J].IEEE Access,2017,5:24344.
[9]SHU F,ZHAO J H,YOU X H,et al.An efficient sparse channel estimator combining time-domain LS and iterative shrinkage for OFDM systems with IQ-imbalances[J].Science China Information Sciences,2012,55(11):2604.
[10] huangjiajun, teng lai, zhangchaojie, wang chunhui, brave of heavenly, I/Q imbalance correction based on simulated annealing algorithm [ J ] zhejiang university proceedings, 2018, 52 (11): 2218.
disclosure of Invention
The invention aims to overcome the defects of the prior art, and provides the transmitting-end IQ correction method, which can correct the IQ imbalance of a transmitting-end signal, avoid the influence of the receiving-end IQ imbalance on a system, improve the signal-to-noise ratio of the transmitting-end signal, has high realizability, can effectively reduce the influence of a mirror image component, improve the performance of the system, and has high practical value and the like.
The purpose of the invention is realized by the following scheme:
an originating IQ correction method, comprising the steps of:
s1, the transmitting end respectively sends a plurality of groups of signals TX, and the plurality of groups of signals TX enter a receiving channel for processing after self-multiplication to respectively obtain a plurality of groups of signals RX;
s2, cross-correlating the multiple sets of signals RX with the multiple sets of sinusoidal signals generated at the receiving end, and then performing delay phase estimation by taking the signal corresponding to the maximum value of the cross-correlation curve.
Further, in step S2, the method further includes taking a signal corresponding to the minimum value of the cross-correlation curve to perform I-path and Q-path DC error estimation, gain imbalance parameter estimation, and phase imbalance parameter estimation.
Further, in step S1, the originating end sends three sets of signals TX1, TX2, TX3, respectively, which are respectively expressed as:
TX1：
Figure GDA0003635319780000041
TX2：
Figure GDA0003635319780000042
TX3：
Figure GDA0003635319780000043
wherein t represents time, I (t) represents a sending signal of an originating I path, Q (t) represents a sending signal of an originating Q path, and omega0Representing the angular frequency of the transmitted signal.
Further, in step S2, the sets of sinusoidal signals generated at the receiving end include four sets of sinusoidal signals, which are denoted as Rx _1(i), Rx _2(i), Rx _3(i), and Rx _4(i), respectively, and each set of sinusoidal signals includes N signals with the same frequency and different initial phases, that is:
Figure GDA0003635319780000044
Figure GDA0003635319780000051
Figure GDA0003635319780000052
Figure GDA0003635319780000053
where N represents a defined positive integer and i represents a selected integer value within [0, N-1 ].
Further, in step S2, after the three groups of signals TX1, TX2, and TX3 are self-multiplied and enter the receiving channel for processing, three groups of signals RX1, RX2, and RX3 are obtained, and then the three groups of signals are cross-correlated with the four groups of sinusoidal signals RX _1(i), RX _2(i), RX _3(i), and RX _4(i) generated at the receiving end, and then the maximum value is obtained, so as to obtain N1, N2, N3, and N4, respectively, that is:
N1＝max{corr(Rx1,Rx_1(i))|i＝0,1,2...N-1}
N2＝max{corr(Rx2,Rx_2(i))|i＝0,1,2...N-1}
N3＝max{corr(Rx3,Rx_3(i))|i＝0,1,2...N-1}
N4＝max{corr(Rx3,Rx_4(i))|i＝0,1,2...N-1}
the three sets of signals R1, R2, R3 corresponding to the maximum value are:
Figure GDA0003635319780000054
Figure GDA0003635319780000055
Figure GDA0003635319780000056
where corr is the identifier of the cross-correlation.
Further, in step S2, the range of the I-path DC offset [ -g _ I [ ]max，+g_Imax]Divide it into NI+1, the originating transmission signal TX is expressed as:
Figure GDA0003635319780000061
TX1：
Figure GDA0003635319780000062
wherein i ═ 0,1, … NI]Received NI+1 groups of signals, each of which is cross-correlated with R1, the correlation value is the smallest corresponding deltaI＝EI(k0) Estimate of the I-way DC error:
Figure GDA0003635319780000063
Figure GDA0003635319780000064
wherein, EI(i) Indicating the value of DC offset of the originating I-path signal during measurement, NIIndicating the set equipartition value, I (I) indicating the I signal output of the originating terminal, Q (I) indicating the Q signal output of the originating terminal, k0Representing the value of i, delta, corresponding to the minimum value found after cross-correlationITo obtain an I-way DC error estimate.
Further, in step S2, the Q-way DC offset is set to range [ -g _ Q [ ]max，+g_Qmax]Divide it into NQ+1, the originating transmission signal TX is expressed as:
Figure GDA0003635319780000065
TX2：
Figure GDA0003635319780000066
wherein i ═ 0,1, … NQ]Received NI+1 groups of signals, each correlated with R2 with the smallest corresponding deltaQ＝EQ(k1) For the Q-way DC error estimate:
Figure GDA0003635319780000067
Figure GDA0003635319780000068
wherein E isQ(i) Representing the DC compensation value, N, of the Q-path signal at the measurement timeQDenotes the set equipartition value, k1 denotes the value of i, δ, corresponding to the minimum value found after cross-correlationQTo obtain a Q-path DC error estimate.
Further, let the range of gain imbalance parameter [ -g ]max，+gmax]Divide it into Ng+1 part, then sendThe transmit signal TX is represented as:
Figure GDA0003635319780000071
TX2：
Figure GDA0003635319780000072
wherein i ═ 1, … Ng+1]Received Ng+1 sets of signals, each with R3Making cross correlation, averaging the minimum correlation values to obtain corresponding gt＝Eg(k2) For gain imbalance parameter estimation:
Figure GDA0003635319780000073
Figure GDA0003635319780000074
wherein, Eg(i) Represents the gain imbalance estimate, N, used in the testgRepresenting the set equivalence value, k2 representing the minimum value i found after cross-correlation, and then averaging; gtTo obtain an estimate of the gain imbalance parameter.
Further, let us set the parameter range of the phase imbalance
Figure GDA0003635319780000075
Divide it into
Figure GDA0003635319780000076
And, the originating transmission signal TX is represented as:
Figure GDA0003635319780000077
TX2：
Figure GDA0003635319780000078
wherein
Figure GDA0003635319780000079
Received (a)
Figure GDA00036353197800000710
Group signals, respectively with R3Making cross-correlation, averaging the minimum correlation values
Figure GDA0003635319780000081
For phase imbalance parameter estimation:
Figure GDA0003635319780000082
Figure GDA0003635319780000083
wherein the content of the first and second substances,
Figure GDA0003635319780000084
representing the I, Q two-way phase imbalance estimate used for the test,
Figure GDA0003635319780000085
indicating the set equipartition value, k3Expressing the minimum value i found after cross-correlation, and then averaging;
Figure GDA0003635319780000086
to obtain an estimated value of the phase imbalance parameter.
Further, in step S1, the self-multiplied signals TX enter the receiving channel for processing, including filtering and amplifying.
The beneficial effects of the invention are:
the method is simple, does not need to add additional devices or equipment, can be completed in the system initialization process only by the method, and has high realizability;
the method can effectively reduce the influence of the image component and improve the performance of the system;
the method of the invention can avoid the influence of IQ imbalance of the receiver, thereby having strong practical value.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the embodiments or the description of the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to the drawings without creative efforts.
FIG. 1 is a block diagram of a classical transmitter;
FIG. 2 is a schematic diagram of the transmit-side IQ imbalance;
FIG. 3 is a diagram of an equivalent model of an originating IQ imbalance;
fig. 4 is a block diagram of an originating IQ correction scheme;
FIG. 5 is a diagram of an originating cosine signal spectrum;
FIG. 6 is a frequency spectrum diagram of the transmit-end cosine signal after up-conversion;
FIG. 7 is a graph of the spectrum of a self-multiplied originating signal;
FIG. 8 is a graph of the spectrum after receive filtering;
FIG. 9 is a cross-correlation plot of a received signal with a receive cos signal;
FIG. 10 is a graph of the spectrum of an originating sinusoidal signal;
fig. 11 is a frequency spectrum diagram of the raised frequency of the sending-end cosine signal;
FIG. 12 is a graph of the spectrum of a self-multiplied originating signal;
FIG. 13 is a graph of the spectrum after receive filtering;
FIG. 14 is a plot of the cross correlation of the received signal with the receive sin signal;
fig. 15 is a graph of the spectrum of an originating single-tone signal;
fig. 16 is a graph of the frequency spectrum of an up-converted originating single-tone signal;
fig. 17 is a graph of the spectrum of the self-multiplied originating tone signal;
FIG. 18 is a graph of the spectrum after receive filtering;
FIG. 19 is a graph of cross-correlation of a received signal with a receive 2cos signal;
fig. 20 is a graph of the cross correlation of the received signal with the receive 2sin signal;
FIG. 21 is a diagram of an originating cosine signal spectrum;
fig. 22 is a graph of the self-multiplied spectrum of the originating signal;
FIG. 23 is a graph of the spectrum of a self-multiplied originating signal;
fig. 24 is a graph of the receive-end filtered spectrum;
fig. 25 is a graph of cross-correlation of 20 sets of received signals with a receive cos signal;
FIG. 26 is a diagram of an originating cosine signal spectrum;
FIG. 27 is a frequency spectrum diagram of an originating sinusoidal signal after up-conversion;
fig. 28 is a graph of the self-multiplied spectrum of the originating signal;
fig. 29 is a graph of the spectrum after receive filtering;
fig. 30 is a cross-correlation plot of 20 sets of received signals with a receive sin signal;
fig. 31 is a graph of the spectrum of an originating single-tone signal;
fig. 32 is a graph of the frequency spectrum of an up-converted originating single-tone signal;
fig. 33 is a graph of the self-multiplied spectrum of the originating signal;
fig. 34 is a graph of the spectrum after receive filtering;
fig. 35 is a graph of cross-correlation of 20 received signal sets with a receive 2cos signal;
fig. 36 is a graph of the spectrum of an originating single-tone signal;
fig. 37 is a graph of the frequency spectrum of an up-converted originating single-tone signal;
fig. 38 is a graph of the self-multiplied spectrum of an originating signal;
FIG. 39 is a graph of the spectrum after receive filtering;
fig. 40 is a graph of cross-correlation of 20 received signal sets with a receive 2cos signal.
Detailed Description
All features disclosed in all embodiments of the present specification, or all methods or process steps implicitly disclosed, may be combined and/or expanded, or substituted, in any way, except for mutually exclusive features and/or steps.
In order to make the thought and the technical scheme improvement thought of the invention more understandable for those skilled in the art, the principle of the invention is explained in detail as follows:
first, according to fig. 3, the TX signal is output as follows through the IQ imbalance procedure of the transmitter:
Figure GDA0003635319780000111
the TX end does not send a signal directly, but performs self-multiplication to obtain:
Figure GDA0003635319780000112
the signal after self multiplication is sent out through the antenna, the RX end receives the signal and then directly receives the signal through the PD after filtering and amplification, and the effects of down-conversion, filtering and the like of the RX end are avoided, so that the influence of two paths of PD errors, local oscillator leakage and filter amplitude-frequency response difference of the RX end can be removed, the received signal cannot be influenced, and the signal received by the receiving end deteriorates the influence of all IQ imbalance from the sending end. The invention finds that when the receiving end RX receives a signal consistent with the transmitted signal during B2B transmission, according to equation (3-2):
Figure GDA0003635319780000113
wherein omega0Substituting a formula into a frequency point defined in a transmission bandwidth range to obtain:
Figure GDA0003635319780000114
from the above formula, wherein
Figure GDA0003635319780000115
The information on the frequency point is
Figure GDA0003635319780000116
Where g represents the amplitude deviation of the I and Q way responses,
Figure GDA0003635319780000121
reflects the phase deviation of the I path and the Q pathDCAnd QDCAnd characterizing the direct current components of the I path and the Q path. Then, based on the above analysis, the present invention finds that when the IQ-two paths are fully balanced,
Figure GDA0003635319780000122
the bins should not carry information and therefore their objective function should be zero. Due to the fact that
Figure GDA0003635319780000123
The number of imbalance parameters involved is three, and it is not easy to find the best value of self-consistency, so here the invention only finds the best δITo counteract IDCThe influence of (c). By setting different delta at the originating endISending the values into the transmitter structure shown in fig. 4, performing fourier transform on the signals at the receiving end, and recording the signals in the frequency spectrum
Figure GDA0003635319780000124
The magnitude of the frequency bins. After polling, find the minimum of the amplitude, which corresponds to deltaIIs marked as IDCThe estimated parameters of (2).
The invention then sends another set of data:
Figure GDA0003635319780000125
substituting into the formula, we get:
Figure GDA0003635319780000126
from the above formula, wherein
Figure GDA0003635319780000127
The information on the frequency point is
Figure GDA0003635319780000128
Then, based on analysis, the present invention finds that when the IQ-two paths are fully balanced,
Figure GDA0003635319780000129
the bins should not carry information and therefore their objective function should also be zero. Due to the fact that
Figure GDA00036353197800001210
The number of imbalance parameters involved is three, and it is not easy to find the best value of self-consistency, so here the invention only finds the best δQTo cancel out QDCThe influence of (c). By setting delta differently at the originQSending it to the transmitter structure shown in fig. 4, the receiving end performs fourier transform on the signal, and records it in the frequency spectrum
Figure GDA00036353197800001211
The magnitude of the frequency bins. After polling, find the minimum of the amplitude, which corresponds to deltaQIs recorded as QDCThe estimated parameters of (2).
The invention then sends a signal:
Figure GDA00036353197800001212
substituting into the formula, we get:
Figure GDA0003635319780000131
from the above formula, wherein
Figure GDA0003635319780000132
The information on the frequency point is
Figure GDA0003635319780000133
Then, based on analysis, the present invention finds that when the IQ-two paths are fully balanced,
Figure GDA0003635319780000134
the bins should not carry information and therefore their objective function should also be zero. Therefore, the invention herein seeks the best gtAnd
Figure GDA0003635319780000135
to counteract g and
Figure GDA0003635319780000136
the influence of (c). By setting different g at the originating endtAnd
Figure GDA0003635319780000137
sending it to the transmitter structure shown in fig. 4, the receiving end performs fourier transform on the signal, and records it in the frequency spectrum
Figure GDA0003635319780000138
The magnitude of the frequency bins. Finding the minimum of amplitude after polling, which corresponds to gtThe estimated parameters noted as g are then used,
Figure GDA0003635319780000139
is marked as
Figure GDA00036353197800001310
The estimated parameters of (2).
Based on the above principle analysis, the specific embodiment of the present invention comprises the following steps:
according to the description of the originating IQ correction method, verification is performed by matlab simulation, wherein the main parameters are shown in table 1 below, and the simulation process of the system includes delay error search, I-path DC offset estimation, Q-path DC offset estimation, gain imbalance parameter estimation, and phase imbalance parameter estimation.
TABLE 1 reference table for setting up originating straightening parameters
Figure GDA00036353197800001311
Figure GDA0003635319780000141
Figure GDA0003635319780000151
The simulation verification is carried out by utilizing the parameters, and the method comprises the following steps:
1. generating a signal:
Figure GDA0003635319780000152
the frequency spectrum is shown in fig. 5, and the frequencies corresponding to the peaks in the graph are ± 0.1MHz, respectively, and are consistent with the single-tone signal frequency set in table 1.
2. The signal enters an originating radio frequency model with IQ imbalance parameters, the output spectrum is shown in FIG. 6, the + -0.4 MHz signal represents the influence caused by the DC offset of the I path and the Q path, and the + -0.3 MHz and + -0.5 MHz signals represent the signal after the cosine signal is up-converted.
3. The signal after radio frequency output is self-multiplied, and the function is expressed as:
Figure GDA0003635319780000153
the output spectrum is shown in fig. 7, and it can be seen from fig. 7 that the signal not only includes a zero-frequency signal, but also includes a plus/minus one-frequency multiplication signal ± 0.1MHz and a plus/minus two-frequency multiplication signal ± 0.2 MHz.
4. The output enters the receiving end for filtering, the frequency spectrum of the filtered signal is shown in fig. 8, only the signal in the bandwidth of the receiver is reserved in fig. 8, and other periodic signals are filtered.
5. The received signal and the signal of the receiving end with different phases are cross-correlated, and the signal of the receiving end is:
Figure GDA0003635319780000161
where N denotes 2 pi divided into N parts, i ═ 0,1,2.. N-1, 2 pi (i-1)/N represents each phase value. Here set to 64 equally divided phases. The correlation curve of the received signal with the cos signal is shown in fig. 9.
From the above, it is found that the maximum value is at the position of 19, the phase error corresponding to the delay of the filter, etc. is 101.25 °, so the present invention sets the first curve generated by the receiving end as:
Figure GDA0003635319780000162
6. the originating end generates a signal:
Figure GDA0003635319780000163
the frequency spectrum is shown in fig. 10, in which the frequencies corresponding to the peaks are ± 0.1MHz, respectively, and are consistent with the single-tone signal frequencies set in table 1.
7. The signal enters into the originating rf model with IQ imbalance parameters, the output spectrum is as shown in fig. 11, the ± 0.4MHz signal represents the influence caused by the DC offset of the I path and the Q path, and the ± 0.3MHz and ± 0.5MHz signals represent the up-converted signal of the cosine signal.
8. The signal after radio frequency output is self-multiplied, and the function of the signal is expressed as:
Figure GDA0003635319780000164
Figure GDA0003635319780000171
the output spectrum is shown in fig. 12, and it can be seen from fig. 12 that the signal not only includes a zero-frequency signal, but also includes a plus/minus one-frequency multiplication signal ± 0.1MHz and a plus/minus two-frequency multiplication signal ± 0.2 MHz.
9. The output enters the receiving end for filtering, the frequency spectrum of the filtered signal is as shown in fig. 13, only the signal in the bandwidth of the receiver is reserved in fig. 13, and other periodic signals are filtered.
10. The received signal and the signal of different phases of the receiving end are cross-correlated, and the signal of the receiving end is:
Figure GDA0003635319780000172
where N denotes 2 pi divided into N parts, i ═ 0,1,2.. N-1, 2 pi (i-1)/N represents each phase value. Here set to 64 equally divided phases. The curve after the received signal is most correlated with the above signal is shown in fig. 14. The invention finds that the maximum value is at the position of 19, the phase error corresponding to the delay of a filter and the like is 101.25 degrees, therefore, the invention sets the first curve generated by the receiving end as:
Figure GDA0003635319780000173
11. the originating end generates a signal:
Figure GDA0003635319780000174
the frequency spectrum is shown in fig. 15, and the frequencies corresponding to the peaks in fig. 15 are 0.1MHz, respectively, and are consistent with the single-tone signal frequencies set in table 1.
12. The signal enters an originating radio frequency model with IQ imbalance parameters, and the output spectrum is as follows: in the figure, the +/-0.4 MHz signal represents the influence caused by the DC offset of the I path and the Q path, and the +/-0.3 MHz signal and the +/-0.5 MHz signal represent the up-converted signal of the sine-cosine signal.
13. The signal after radio frequency output is self-multiplied, and the function is expressed as:
Figure GDA0003635319780000181
Figure GDA0003635319780000182
the output spectrum is shown in fig. 17, and it can be seen from fig. 17 that the signal not only includes a zero-frequency signal, but also includes a plus/minus one-frequency multiplication signal ± 0.1MHz and a plus/minus two-frequency multiplication signal ± 0.2 MHz.
14. The output enters the receiving end for filtering, the frequency spectrum of the filtered signal is shown in fig. 18, in which only the signal in the bandwidth of the receiver is retained, and other periodic signals are filtered out.
15. The received signal and the signal of the receiving end with different phases are cross-correlated, and the signal of the receiving end is:
Figure GDA0003635319780000183
Figure GDA0003635319780000184
where N denotes 2 pi divided into N parts, i ═ 0,1,2.. N-1, 2 pi (i-1)/N represents each phase value. Here set to 64 equally divided phases. The curves after the received signal is most correlated with the above signal are shown in fig. 19 and 20. The invention finds that the maximum value of the two curves is at the position of 19, and the phase error corresponding to the delay of a filter and the like is 101.25 degrees, so the invention sets the third curve generated by the receiving end as:
Figure GDA0003635319780000185
16. after finding the accurate phase delay, the sending end performs I-path DC correction to generate a signal:
Figure GDA0003635319780000191
TX1：
Figure GDA0003635319780000192
the frequency spectrum is shown in fig. 21, the frequencies corresponding to the peaks in the graph are ± 0.1MHz, respectively, and are consistent with the single-tone signal frequency set in table 1, and the zero-frequency signal represents the initially transmitted DC correction signal.
17. The signal enters an originating radio frequency model with IQ imbalance parameters, and the output spectrum is as follows:
in the figure, a +/-0.4 MHz signal represents the influence caused by the DC offset of the I path and the Q path, and +/-0.3 MHz and +/-0.5 MHz signals represent signals after cosine signal up-conversion.
18. The signals output by the radio frequency are self-multiplied, the output frequency spectrum is shown in fig. 23, and it can be seen from fig. 23 that the signals not only include zero-frequency signals, but also include plus/minus one-frequency-multiplied signals ± 0.1MHz and plus/minus two-frequency-multiplied signals ± 0.2 MHz.
19. The output enters the receiving end for filtering, the frequency spectrum of the filtered signal is as shown in fig. 24, only the signal in the bandwidth of the receiver is reserved in fig. 24, and other periodic signals are filtered.
20. The received signal and a first signal stored by a receiving end are cross-correlated and then data is stored, wherein the receiving end signal is as follows:
Figure GDA0003635319780000193
subsequently, 20 different groups of I-path DC test data are sent one by one, and are cross-correlated with equations (4-16), respectively, and the resulting curve is shown in fig. 25. The invention finds that the offset of the I-path DC offset corresponding to the lowest point position is-0.04, and can completely compensate the initial error value of the I-path DC of the table 1 by 0.04.
21. Then, the transmitting end carries out Q-path DC rectification and generates a signal:
Figure GDA0003635319780000201
TX2：
Figure GDA0003635319780000202
the frequency spectrum is shown in fig. 27, the frequencies corresponding to the peak values in fig. 27 are ± 0.1MHz, respectively, and are consistent with the single-tone signal frequency set in table 1, and the zero-frequency signal represents the initially transmitted I-path and Q-path DC correction signals.
22. The signal enters an originating radio frequency model with IQ imbalance parameters, and the output spectrum is as follows: in the figure, a +/-0.4 MHz signal represents the influence caused by the DC offset of the I path and the Q path, and +/-0.3 MHz and +/-0.5 MHz signals represent signals after cosine signal up-conversion.
23. The signals output by the radio frequency are self-multiplied, the output frequency spectrum is shown in fig. 28, and it can be seen from fig. 28 that the signals not only include zero-frequency signals, but also include plus/minus one-frequency-multiplied signals ± 0.1MHz and plus/minus two-frequency-multiplied signals ± 0.2 MHz.
24. The output enters the receiving end for filtering, the frequency spectrum of the filtered signal is shown in fig. 29, only the signal in the bandwidth of the receiver is reserved in fig. 29, and other periodic signals are filtered.
25. The received signal and the first signal stored in the receiving end are cross-correlated and then data is stored, and the receiving end signal is:
Figure GDA0003635319780000203
then 20 different groups of Q-path DC test data are sent one by one, and are cross-correlated with equations (4-19), respectively, and the resulting curve is shown in fig. 30. The invention finds that the deviation of the DC offset of the Q path corresponding to the lowest point position is-0.05, and can completely compensate the initial error value of the DC of the Q path of 0.05 in the table 1, so the compensation method is correct.
26. Subsequently, the transmitting end carries out gain imbalance parameter estimation to generate a signal:
Figure GDA0003635319780000211
TX2：
Figure GDA0003635319780000212
the frequency spectrum is shown in fig. 31, the frequencies corresponding to the peaks in the diagram are ± 0.1MHz, respectively, and are consistent with the single-tone signal frequency set in table 1, and the zero-frequency signal represents the initially transmitted I-path and Q-path DC correction signals. Since the amplitudes of the cos and sin signals are different, the amplitudes of the two signal bins, which are symmetric about the zero frequency, are different.
27. The signal enters an originating radio frequency model with IQ imbalance parameters, and the output spectrum is as follows:
in the figure, the +/-0.4 MHz signal represents the influence caused by the DC offset of the I path and the Q path, and the existence of a correct estimation value is already counteracted, so that no signal exists in the frequency point. The + -0.3 MHz and + -0.5 MHz signals represent the up-converted cosine signal.
28. The signal after radio frequency output is self-multiplied, and the function of the signal is expressed as:
Figure GDA0003635319780000213
the output spectrum is shown in fig. 33, and it can be seen that the signal not only includes zero-frequency signal, but also includes plus-minus double-frequency signal plus-minus 0.2MHz, because of IDCAnd QDCAll are zero after correct compensation, so the position of plus-minus one frequency doubling signal plus or minus 0.1MHz has no signal according to the above formula and picture.
29. The output enters the receiving end for filtering, the spectrum of the filtered signal is as shown in fig. 34, only the signal in the bandwidth of the receiver is retained in fig. 34, and other periodic signals are filtered out.
30. The received signal and a third signal stored by a receiving end are cross-correlated and then data is stored, wherein the receiving end signal is as follows:
Figure GDA0003635319780000221
then 20 sets of different gain test data are sent one by one and cross-correlated with equations (4-26), respectively, and the resulting curve is shown in fig. 35. The gain imbalance corresponding to the lowest point position is found to be 1.05, and is completely the same as the gain imbalance parameters set in the table 1, so that the estimation algorithm is correct.
31. Then, the originating terminal performs phase imbalance parameter estimation to generate a signal:
Figure GDA0003635319780000222
TX2：
Figure GDA0003635319780000223
the frequency spectrum is shown in fig. 36, the frequencies corresponding to the peaks in fig. 36 are ± 0.1MHz, respectively, and are consistent with the single-tone signal frequency set in table 1, and the zero-frequency signal represents the initially transmitted I-path DC correction signal and Q-path DC correction signal. Because the amplitudes of the cos and sin signals are different, the amplitudes of the two signal frequency points which are symmetrical about the zero frequency are different.
32. The signal enters an originating radio frequency model with IQ imbalance parameters, and the output spectrum is as follows:
in the figure, the +/-0.4 MHz signal represents the influence caused by the DC offset of the I path and the Q path, and the frequency point has no signal because the existence of a correct estimation value is already counteracted. The + -0.3 MHz and + -0.5 MHz signals represent the up-converted cosine signal.
33. The signal after radio frequency output is self-multiplied, and the function of the signal is expressed as:
Figure GDA0003635319780000231
the output spectrum is shown in fig. 38, and it can be seen that the signal not only includes zero-frequency signal, but also includes plus-minus double-frequency signal plus-minus 0.2MHz, because of IDCAnd QDCAll are zero after correct compensation, so that no signal at plus-minus-one frequency multiplication signal plus-minus 0.1MHz can be demonstrated according to the formula and the picture。
34. The output enters the receiving end for filtering, the frequency spectrum of the filtered signal is shown in fig. 39, only the signal in the bandwidth of the receiver is reserved in fig. 39, and other periodic signals are filtered.
35. And the received signal and a third signal stored by a receiving end are subjected to cross correlation and then data are stored, wherein the receiving end signal is as follows:
Figure GDA0003635319780000232
the subsequent 20 sets of different gain test data were sent one by one and cross-correlated with equations (4-27), respectively, to obtain the curve shown in fig. 40. The invention finds that the phase imbalance corresponding to the lowest point position is 5 degrees, which is completely the same as the gain imbalance parameter set in the table 1, so the estimation algorithm is correct.
The invention can be used in any system generating IQ imbalance, and is not limited to a broadband system, and a narrow-band system is still applicable.
Other embodiments than the above examples may be devised by those skilled in the art based on the foregoing disclosure, or by adapting and using knowledge or techniques of the relevant art, and features of various embodiments may be interchanged or substituted and such modifications and variations that may be made by those skilled in the art without departing from the spirit and scope of the present invention are intended to be within the scope of the following claims.
The functionality of the present invention, if implemented in the form of software functional units and sold or used as a stand-alone product, may be stored in a computer readable storage medium. Based on such understanding, the technical solution of the present invention or a part thereof which substantially contributes to the prior art may be embodied in the form of a software product, which is stored in a storage medium, and performs all or part of the steps of the method according to the embodiments of the present invention in a computer device (which may be a personal computer, a server, or a network device, etc.) and corresponding software. And the aforementioned storage medium includes: various media capable of storing program codes, such as a usb disk, a removable hard disk, or an optical disk, exist in a read-only Memory (RAM), a Random Access Memory (RAM), and the like, for performing a test or actual data in a program implementation.

Claims (6)

1. An outbound IQ correction method comprising the steps of:
s1, the transmitting end respectively sends a plurality of groups of signals TX, and the plurality of groups of signals TX enter a receiving channel for processing after self-multiplication to respectively obtain a plurality of groups of signals RX;
in step S1, the originating end sends three sets of signals TX1, TX2, TX3, respectively, which are respectively expressed as:
TX1：
Figure FDA0003635319770000011
TX2：
Figure FDA0003635319770000012
TX3：
Figure FDA0003635319770000013
wherein t represents time, I (t) represents I-path sending signal of the sending end, Q (t) represents Q-path sending signal of the sending end, omega0Representing the angular frequency of the transmitted signal;
s2, after cross-correlation is carried out between multiple groups of signals RX and multiple groups of sinusoidal signals generated at the receiving end, the signal corresponding to the maximum value of the cross-correlation curve is taken for delay phase estimation; in step S2, the sets of sinusoidal signals generated at the receiving end include four sets of sinusoidal signals, which are denoted as Rx _1(i), Rx _2(i), Rx _3(i), and Rx _4(i), respectively, and each set of sinusoidal signals includes N signals with the same frequency and different initial phases, that is:
Figure FDA0003635319770000014
Figure FDA0003635319770000015
Figure FDA0003635319770000016
Figure FDA0003635319770000021
wherein, N represents a defined positive integer, i represents an integer value selected in [0, N-1 ]; in step S2, the three sets of signals TX1, TX2, and TX3 are multiplied by themselves and then enter the receiving channel for processing, so as to obtain three sets of signals RX1, RX2, and RX3, and then cross-correlated with the four sets of sinusoidal signals RX _1(i), RX _2(i), RX _3(i), and RX _4(i) generated by the receiving end to obtain the maximum values, so as to obtain N1, N2, N3, and N4, respectively, that is:
N1＝max{corr(Rx1,Rx_1(i))|i＝0,1,2...N-1}
N2＝max{corr(Rx2,Rx_2(i))|i＝0,1,2...N-1}
N3＝max{corr(Rx3,Rx_3(i))|i＝0,1,2...N-1}
N4＝max{corr(Rx3,Rx_4(i))|i＝0,1,2...N-1}
the three sets of signals R1, R2, R3 corresponding to the maximum value are:
Figure FDA0003635319770000022
Figure FDA0003635319770000023
Figure FDA0003635319770000024
wherein corr is the identifier of the cross-correlation;
and taking three groups of signals R1, R2 and R3 corresponding to the maximum value to carry out I-path and Q-path DC error estimation, gain imbalance parameter estimation and phase imbalance parameter estimation.
2. The transmitting IQ correction method according to claim 1, wherein in step S2, set the range of I-way DC offset [ -g _ I [ ]max，+g_Imax]Divide it into NI+1, the originating transmission signal TX is expressed as:
Figure FDA0003635319770000031
TX1：
Figure FDA0003635319770000032
wherein i ═ 0,1, … NI]Received NI+1 groups of signals, each correlated with R1 with the smallest corresponding deltaI＝EI(k0) Estimate of the I-way DC error:
Figure FDA0003635319770000033
Figure FDA0003635319770000034
wherein E isI(i) Indicating the value of DC offset of the originating I-path signal during measurement, NIIndicating the set equipartition value, I (I) indicating the I signal output of the originating terminal, Q (I) indicating the Q signal output of the originating terminal, k0Representing the value of i, delta, corresponding to the minimum value found after cross-correlationITo obtain an I-way DC error estimate.
3. The IQ correction method for an outbound mail message according to claim 1,in step S2, the Q-way DC offset is set to range [ -g _ Q ]max，+g_Qmax]Divide it into NQ+1, the originating transmission signal TX is expressed as:
Figure FDA0003635319770000035
TX2：
Figure FDA0003635319770000036
wherein i ═ 0,1, … NQ]Received NI+1 groups of signals, each of which is cross-correlated with R2, the correlation value is the smallest corresponding deltaQ＝EQ(k1) For the Q-way DC error estimate:
Figure FDA0003635319770000037
Figure FDA0003635319770000038
delta corresponding to the smallest correlation valueI＝EI(k0) Estimate of the I-way DC error:
Figure FDA0003635319770000041
Figure FDA0003635319770000042
wherein E isQ(i) Representing the DC offset value, N, of the originating Q-path signal during measurementQDenotes the set equipartition value, k1 denotes the value of i, δ, corresponding to the minimum value found after cross-correlationQTo obtain a Q-path DC error estimate.
4. The IQ correction method according to claim 1, wherein the gain imbalance parameter is set in the range [ -g ]max，+gmax]Divide it into Ng+1, the transmission signal TX is expressed as:
Figure FDA0003635319770000043
TX2：
Figure FDA0003635319770000044
wherein i ═ 1, … Ng+1]Received Ng+1 sets of signals, respectively with R3Making cross correlation, averaging the minimum correlation values, and obtaining the corresponding gt＝Eg(k2) For gain imbalance parameter estimation:
Figure FDA0003635319770000045
Figure FDA0003635319770000046
wherein, deltaI＝EI(k0) Estimate of the I-way DC error:
Figure FDA0003635319770000047
Figure FDA0003635319770000048
δQ＝EQ(k1) For the Q-way DC error estimate:
Figure FDA0003635319770000049
Figure FDA0003635319770000051
Eg(i) represents the gain imbalance estimate, N, used in the testgRepresenting the set equipartition value, k2 representing the minimum value i value found after cross-correlation, and then averaging; g is a radical of formulatTo obtain an estimate of the gain imbalance parameter.
5. The transmit-end IQ correction method according to claim 1, wherein setting the parameter range of phase imbalance
Figure FDA0003635319770000052
Divide it into
Figure FDA0003635319770000053
And, the originating transmission signal TX is represented as:
Figure FDA0003635319770000054
TX2：
Figure FDA0003635319770000055
wherein
Figure FDA0003635319770000056
Received (a)
Figure FDA0003635319770000057
Group signals, respectively with R3Making cross-correlation, corresponding to the minimum value after averaging
Figure FDA0003635319770000058
For phase imbalance parameter estimation:
Figure FDA0003635319770000059
Figure FDA00036353197700000510
wherein, deltaI＝EI(k0) Estimate of the I-way DC error:
Figure FDA00036353197700000511
Figure FDA00036353197700000512
δQ＝EQ(k1) Estimate of the Q-way DC error:
Figure FDA00036353197700000513
Figure FDA0003635319770000061
gt＝Eg(k2) As an estimate of gain imbalance:
Figure FDA0003635319770000066
Figure FDA0003635319770000062
Figure FDA0003635319770000063
representing the I, Q two-way phase imbalance estimate used for the test,
Figure FDA0003635319770000064
indicating the set equipartition value, k3Representing the minimum value i found after cross-correlation, and then averaging;
Figure FDA0003635319770000065
to obtain the estimated value of the phase imbalance parameter.
6. The IQ correction method according to any of claims 1-5, wherein in step S1, the self-multiplied signals TX are processed in the receiving channel, including filtering and amplification.
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