CN113131804B - Three-switch converter topology and control strategy for switched reluctance motor - Google Patents
Three-switch converter topology and control strategy for switched reluctance motor Download PDFInfo
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- CN113131804B CN113131804B CN202110427923.5A CN202110427923A CN113131804B CN 113131804 B CN113131804 B CN 113131804B CN 202110427923 A CN202110427923 A CN 202110427923A CN 113131804 B CN113131804 B CN 113131804B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/10—Arrangements for controlling torque ripple, e.g. providing reduced torque ripple
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/14—Electronic commutators
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/28—Arrangements for controlling current
Abstract
The invention relates to the technical field of motors, and provides a topology and a control strategy of a three-switch converter for a switched reluctance motor. The proposed three-switch converter topology can realize bipolar operation of current, and has 8 operation modes such as a forward excitation mode, a forward upper tube zero-voltage follow current mode, a forward lower tube zero-voltage follow current mode, a forward negative voltage follow current mode, a reverse excitation mode, a reverse upper tube zero-voltage follow current mode, a reverse lower tube zero-voltage follow current mode and a reverse negative voltage follow current mode. Meanwhile, the magnetic circuit balance control method can eliminate the phenomenon of asymmetric magnetic circuits of the switched reluctance motor with even phases, realize the balance control of the magnetic circuits and improve the operation efficiency of the system. Compared with a conventional asymmetric half-bridge power converter for driving the switched reluctance motor, the power converter can reduce the using number of power semiconductor devices, does not need to increase passive devices such as inductors, capacitors and the like, and has good engineering application value.
Description
Technical Field
The invention relates to the technical field of motors, in particular to a three-switch converter topology and a control strategy for a switched reluctance motor.
Background
The switched reluctance motor has the advantages of simple structure, low manufacturing cost, strong fault-tolerant capability and the like, and becomes an important choice for driving motors of new energy vehicles, wind power generation, the coal mine field and intelligent manufacturing equipment. However, due to the rare earth-free characteristic and the double-salient structure, the switched reluctance motor also has the disadvantages of low power density, large torque ripple, low efficiency and the like, and the reliability problem caused by the disadvantages is a main obstacle for preventing the large-scale application and development of the switched reluctance motor system. In order to overcome the above disadvantages, a new power converter topology with low cost and high reliability needs to be explored. The existing low-cost converter topologies mainly comprise a Miller converter, an m-switch converter, a C-dump converter, an R-dump converter and the like, but the topologies often bring about the reduction of control performance and fault-tolerant capability. For example, m-switch converters can reduce the number of power devices used, but the fault tolerance is significantly reduced compared to asymmetric half-bridge power converters. Meanwhile, the fault-tolerant power converter for the conventional switched reluctance motor usually needs to be added with power semiconductor devices, and particularly, each pole of the topology of the distributed fault-tolerant power converter needs two controllable switching tubes and two diodes, so that the system cost is greatly increased. Meanwhile, the existing power converter topology cannot solve the problem of unbalanced magnetic circuits of even-phase switched reluctance motors. Therefore, in order to improve the operation performance of the system, a high-performance power converter topology with low cost and high reliability needs to be researched urgently.
Disclosure of Invention
The present invention is directed to solving, at least in part, one of the technical problems in the related art.
Therefore, one objective of the present invention is to provide a topology and a control strategy of a three-switch converter for a switched reluctance motor, so as to reduce the number of components and system cost, improve fault tolerance, remote efficiency and power density, and achieve balanced operation of a magnetic circuit.
To achieve the above objective, an embodiment of the present invention provides a topology and a control strategy of a three-switch converter for a switched reluctance motor. Each bridge arm of the proposed three-switch converter is composed of three controllable switch tubes with built-in diodes, and each phase winding is respectively connected to the upper and lower nodes of the adjacent bridge arm, so that any phase of switched reluctance motor can be driven.
Description of the working principle: the proposed three-switch converter topology can realize bipolar operation of current, and has 8 operation modes such as a forward excitation mode, a forward upper tube zero-voltage follow current mode, a forward lower tube zero-voltage follow current mode, a forward negative voltage follow current mode, a reverse excitation mode, a reverse upper tube zero-voltage follow current mode, a reverse lower tube zero-voltage follow current mode and a reverse negative voltage follow current mode. The three switching tubes of one bridge arm are named as an upper tube, a middle tube and a lower tube according to positions, a parasitic diode of the upper tube is named as an upper diode, a parasitic diode of the middle tube is named as a middle diode, and a parasitic diode of the lower tube is named as a lower diode. The current bridge arm is the kth bridge arm, the next bridge arm is the (k + 1) th bridge arm, and the previous bridge arm is the (k-1) th bridge arm. If two ends of a phase winding are respectively connected with the upper node of the kth bridge arm and the lower node of the (k + 1) th bridge arm, the upper tube of the kth bridge arm and the lower tube of the (k + 1) th bridge arm need to be switched on in a forward excitation mode. For example, when the phase a is excited in the forward direction, the upper tube S1 of the 1 st arm and the lower tube S6 of the 2 nd arm need to be turned on, and the phase a winding is excited by the power supply. Under the reverse excitation mode, the middle tube and the lower tube of the kth bridge arm and the upper tube and the middle tube of the (k + 1) th bridge arm need to be opened. For example, when a is excited in the opposite direction, it is necessary to open the intermediate tube S2, the lower tube S3, the upper tube S4, and the intermediate tube S5 of the 1 st arm. When zero-voltage freewheeling is performed on the forward upper tube, the upper tube of the kth bridge arm needs to be turned on, and the parasitic diode of the upper tube of the (k + 1) th bridge arm and the parasitic diode of the middle tube are turned on simultaneously. For example, when the a-phase forward-direction tube has zero freewheeling, the tube S1 of the 1 st arm needs to be turned on, and the parasitic diode D4 of the tube S4 of the 2 nd arm and the parasitic diode D5 of the intermediate tube S5 need to be turned on at the same time. When zero-voltage freewheeling is performed on the reverse upper tube, the parasitic diode of the upper tube of the kth bridge arm needs to be turned on, and the upper tube of the kth +1 bridge arm and the middle tube need to be turned on simultaneously. For example, when the a-phase reverse-transistor zero-voltage freewheeling occurs, the parasitic diode D1 of the transistor S1 of the 1 st arm needs to be turned on, and the transistor S4 and the intermediate transistor S5 of the 2 nd arm need to be turned on at the same time. When the forward lower tube continues current at zero voltage, a parasitic diode of a kth bridge arm intermediate tube and a parasitic diode of a lower tube need to be switched on, and a kth +1 th bridge arm lower tube is switched on simultaneously. For example, when the a-phase forward down tube freewheels at zero voltage, it is necessary to turn on the parasitic diode D2 of the 1 st arm intermediate tube S2 and the parasitic diode D3 of the down tube S3, and turn on the 2 nd arm down tube S6 at the same time. When the backward lower tube is subjected to zero-voltage freewheeling, the middle tube and the lower tube of the kth bridge arm need to be conducted, and the parasitic diode of the kth +1 lower tube of the bridge arm needs to be simultaneously turned on. For example, when the a-phase reverse down tube freewheels at zero voltage, the intermediate tube S2 and the down tube S3 of the 1 st bridge arm need to be turned on, and the parasitic diode D6 of the 2 nd bridge arm down tube S6 needs to be turned on at the same time. When the forward negative voltage continues current, the parasitic diode of the middle tube and the parasitic diode of the lower tube of the kth bridge arm need to be conducted, and the parasitic diode of the upper tube and the parasitic diode of the middle tube of the kth +1 bridge arm need to be conducted at the same time. For example, when the a-phase forward negative voltage freewheel, it is necessary to conduct the parasitic diode D2 of the middle tube S2 and the parasitic diode D3 of the lower tube S3 in the 1 st arm, and to conduct the parasitic diode D4 of the tube S4 and the parasitic diode D5 of the middle tube S5 in the 2 nd arm. When the reverse negative voltage continues current, the parasitic diode on the upper tube of the kth bridge arm needs to be turned on, and the parasitic diode on the lower tube of the (k + 1) th bridge arm needs to be turned on at the same time. For example, when the a-phase reverse lower tube freewheels at zero voltage, the parasitic diode D1 of the upper tube S1 of the 1 st arm needs to be turned on, and the parasitic diode D6 of the lower tube S6 of the 2 nd arm needs to be turned on at the same time.
Through the effective combination of 8 operation modes, the ordered bipolar operation of current can be realized, so that the phenomenon of asymmetric magnetic circuits of the switched reluctance motor with even phases can be eliminated, the balance control of the magnetic circuits is realized, and the torque pulsation of the system is reduced. Meanwhile, the magnetic circuit balance control method can reduce the phase current frequency, thereby reducing the iron loss and improving the system operation efficiency. Taking a four-phase switched reluctance motor as an example, if unipolar currents are sequentially introduced into the phase a, the phase B, the phase C and the phase D, two situations nnnsssss or nsnsnssnsn are distributed in the stator pole magnetic field at this time. For the first case 3 long and 1 short magnetic circuit occur per week, and for the second case 1 long and 3 short magnetic circuit occur per week. By adopting the proposed three-switch converter, bipolar currents are sequentially introduced into the A phase, the B phase, the C phase and the D phase, the sequence of the introduced currents is A +, B +, C + D + A-B-C-D-, and the magnetic field distribution of the stator poles is NSNSNSNSNS which is short magnetic circuit operation, so that the magnetic field is symmetrically distributed, and the method is called as a magnetic circuit balance control method.
The converter can provide multiple excitation modes and two-phase series-connected and conducted channels, so that partial excitation of a fault phase can be ensured after an open-circuit fault of a system occurs, and the fault-tolerant capability and reliability of the system are improved; after the short-circuit fault of the switching tube occurs, the short-circuit fault can be converted into the open-circuit fault manually; for example, after the phase a lower tube S3 has an open-circuit fault, S2, S4, S5, S11 and S12 may be turned on to conduct the phase D and the phase a in series; and after the phase A tube S1 has short-circuit fault, S1 can be manually cut off to convert the short-circuit fault into an open-circuit fault.
The beneficial effects of the invention are as follows: compared with a conventional asymmetric half-bridge power converter for driving a switched reluctance motor, the power converter can reduce the using number of power semiconductor devices, and does not need to increase passive devices such as inductors, capacitors and the like, so that the system cost and size can be reduced, the power density, the efficiency and the fault-tolerant capability are improved, and the torque ripple is reduced.
Drawings
Fig. 1 is a topology structural diagram of a three-switch converter according to embodiment 1 of the present invention.
Fig. 2 is a schematic diagram of a forward excitation mode current path in embodiment 1 of the present invention.
Fig. 3 is a schematic diagram of a reverse excitation mode current path in embodiment 1 of the present invention.
Fig. 4 is a schematic diagram of a current path in a zero-voltage freewheeling mode on a forward direction in embodiment 1 of the present invention.
Fig. 5 is a schematic diagram of a current path in a reverse high-tube zero-voltage freewheeling mode according to embodiment 1 of the present invention.
Fig. 6 is a schematic diagram of a current path in a zero-voltage freewheeling mode of a forward low tube in embodiment 1 of the present invention.
Fig. 7 is a schematic diagram of a current path in reverse low-tube zero-voltage freewheel mode according to embodiment 1 of the present invention.
Fig. 8 is a schematic diagram of a current path in the positive negative voltage freewheel mode according to embodiment 1 of the present invention.
Fig. 9 is a schematic diagram of a reverse negative voltage freewheel mode current path according to embodiment 1 of the present invention.
Fig. 10 is a schematic diagram of a fault-tolerant operating current path according to embodiment 1 of the present invention.
Detailed Description
Reference will now be made in detail to embodiments of the present invention, examples of which are illustrated in the accompanying drawings, wherein like reference numerals refer to the same or similar elements or elements having the same or similar functions throughout. The embodiments described below with reference to the accompanying drawings are illustrative and intended to explain the present invention and should not be construed as limiting the present invention.
The following describes a switched reluctance motor three-switch converter topology and a magnetic circuit balancing method according to an embodiment of the present invention with reference to the accompanying drawings.
Fig. 1 is a topological structure diagram of a three-switch converter for a four-phase switched reluctance motor according to an embodiment of the present invention. As shown in fig. 1, the three-switch converter topology for the four-phase switched reluctance motor according to the embodiment of the present invention is characterized in that each bridge arm is composed of three controllable switching tubes with built-in diodes, and each phase winding is connected to the upper and lower nodes of the adjacent bridge arm. The phase-A winding La is connected to an upper node of the first bridge arm and a lower node of the second bridge arm, the phase-B winding Lb is connected to an upper node of the second bridge arm and a lower node of the third bridge arm, the phase-C winding Lc is connected to an upper node of the third bridge arm and a lower node of the fourth bridge arm, and the phase-D winding Ld is connected to an upper node of the fourth bridge arm and a lower node of the first bridge arm. The proposed three-switch converter topology can realize the bipolar operation of current, and has 8 operation modes such as a forward excitation mode, a forward upper tube zero voltage follow current mode, a forward lower tube zero voltage follow current mode, a forward negative voltage follow current mode, a reverse excitation mode, a reverse upper tube zero voltage follow current mode, a reverse lower tube zero voltage follow current mode, a reverse negative voltage follow current mode and the like. The three switching tubes of one bridge arm are named as an upper tube, a middle tube and a lower tube according to positions, a parasitic diode of the upper tube is named as an upper diode, a parasitic diode of the middle tube is named as a middle diode, and a parasitic diode of the lower tube is named as a lower diode. The current bridge arm is the kth bridge arm, the next bridge arm is the kth +1 bridge arm, and the previous bridge arm is the kth-1 bridge arm. If two ends of a phase winding are respectively connected with the upper node of the kth bridge arm and the lower node of the (k + 1) th bridge arm, the upper tube of the kth bridge arm and the lower tube of the (k + 1) th bridge arm need to be switched on in the forward excitation mode. For example, when the phase a is excited in the forward direction, the upper tube S1 of the 1 st arm and the lower tube S6 of the 2 nd arm need to be turned on, and the phase a winding is excited in the forward direction by the power supply, as shown in fig. 2. Under the reverse excitation mode, the middle tube and the lower tube of the kth bridge arm and the upper tube and the middle tube of the (k + 1) th bridge arm need to be opened. For example, when a is excited in the opposite direction, it is necessary to open the intermediate tube S2, the lower tube S3, the upper tube S4 and the intermediate tube S5 of the 1 st arm, as shown in fig. 3. When the forward upper tube continues current at zero voltage, the upper tube of the kth bridge arm needs to be switched on, and the parasitic diode of the upper tube of the (k + 1) th bridge arm and the parasitic diode of the middle tube are switched on simultaneously. For example, when the a-phase forward top tube has a zero-voltage freewheel, the top tube S1 of the 1 st leg needs to be turned on, and the parasitic diode D4 of the top tube S4 of the 2 nd leg and the parasitic diode D5 of the intermediate tube S5 need to be turned on, as shown in fig. 4. When zero-voltage freewheeling is performed on the reverse upper tube, the parasitic diode of the upper tube of the kth bridge arm needs to be turned on, and the upper tube of the kth +1 bridge arm and the middle tube need to be turned on simultaneously. For example, when the a-phase reverse-transistor zero-voltage freewheeling occurs, the parasitic diode D1 of the transistor S1 of the 1 st leg needs to be turned on, and the transistor S4 and the intermediate transistor S5 of the 2 nd leg need to be turned on at the same time, as shown in fig. 5. When the forward lower tube continues current at zero voltage, a parasitic diode of a middle tube of the kth bridge arm and a parasitic diode of the lower tube need to be switched on, and the lower tube of the (k + 1) th bridge arm is switched on simultaneously. For example, when the a-phase forward down tube freewheels at zero voltage, it is necessary to conduct the parasitic diode D2 of the 1 st arm intermediate tube S2 and the parasitic diode D3 of the down tube S3, and to conduct the 2 nd arm down tube S6, as shown in fig. 6. When the backward lower tube continues current at zero voltage, the middle tube and the lower tube of the kth bridge arm need to be conducted, and the parasitic diode of the kth +1 th bridge arm lower tube needs to be simultaneously turned on. For example, when the a-phase reverse low tube freewheeling at zero voltage, the intermediate tube S2 and the low tube S3 of the 1 st arm need to be turned on, and the parasitic diode D6 of the low tube S6 of the 2 nd arm needs to be turned on at the same time, as shown in fig. 7. When the forward negative voltage continues current, the parasitic diode of the middle tube and the parasitic diode of the lower tube of the kth bridge arm need to be conducted, and the parasitic diode of the upper tube and the parasitic diode of the middle tube of the kth +1 bridge arm need to be conducted at the same time. For example, when the a-phase forward negative voltage freewheel, it is necessary to turn on the parasitic diode D2 of the middle tube S2 and the parasitic diode D3 of the lower tube S3 in the 1 st arm, and turn on the parasitic diode D4 of the upper tube S4 and the parasitic diode D5 of the middle tube S5 in the 2 nd arm, as shown in fig. 8. When the reverse negative voltage continues current, the parasitic diode on the upper tube of the kth bridge arm needs to be conducted, and the parasitic diode on the lower tube of the (k + 1) th bridge arm needs to be simultaneously conducted. For example, when the reverse a-phase tube freewheels at zero voltage, the parasitic diode D1 of the top tube S1 of the 1 st arm needs to be turned on, and the parasitic diode D6 of the bottom tube S6 of the 2 nd arm needs to be turned on, as shown in fig. 9.
Through the effective combination of 8 operation modes, the ordered bipolar operation of current can be realized, so that the phenomenon of asymmetric magnetic circuits of the switched reluctance motor with even phases can be eliminated, the balance control of the magnetic circuits is realized, and the torque pulsation of the system is reduced. Meanwhile, the provided magnetic circuit balance control method can reduce the phase current frequency, thereby reducing the iron loss and improving the system operation efficiency. Taking a four-phase switched reluctance motor as an example, if unipolar currents are sequentially introduced into the phase a, the phase B, the phase C and the phase D, two situations nnnsssss or nsnsnssnsn are distributed in the stator pole magnetic field at this time. 3 long and 1 short magnetic circuits will occur one cycle for the first case and 1 long and 3 short magnetic circuits will occur one cycle for the second case. By adopting the proposed three-switch converter, bipolar currents are sequentially introduced into the A phase, the B phase, the C phase and the D phase, the sequence of the introduced currents is A +, B +, C + D + A-B-C-D-, and the magnetic field distribution of the stator poles is NSNSNSNSNS which is short magnetic circuit operation, so that the magnetic field is symmetrically distributed, and the method is called as a magnetic circuit balance control method.
The converter can provide multiple excitation modes and two-phase series-connected and conducted channels, so that partial excitation of a fault phase can be ensured after an open-circuit fault of a system occurs, and the fault-tolerant capability and reliability of the system are improved; after the short-circuit fault of the switching tube occurs, the short-circuit fault can be converted into the open-circuit fault manually; for example, after the phase a tube S1 has an open-circuit fault, S10 and S6 may be turned on to conduct the phase D and the phase a in series; and after the phase A tube S1 has short-circuit fault, S1 can be manually cut off to convert the short-circuit fault into an open-circuit fault.
The converter can provide multiple excitation modes and two-phase series-connected and conducted channels, so that partial excitation of a fault phase can be ensured after an open-circuit fault of a system occurs, and the fault-tolerant capability and reliability of the system are improved; after the short-circuit fault of the switching tube occurs, the short-circuit fault can be converted into the open-circuit fault manually; for example, after the open-circuit fault occurs in the a-phase tube S3, S2, S4, S5, S11 and S12 may be turned on to conduct the D-phase and the a-phase in series, as shown in fig. 10; and after the phase A pipe S1 has a short-circuit fault, S1 can be manually cut off to convert the short-circuit fault into an open-circuit fault.
Although embodiments of the present invention have been shown and described above, it is understood that the above embodiments are exemplary and should not be construed as limiting the present invention, and that variations, modifications, substitutions and alterations can be made to the above embodiments by those of ordinary skill in the art within the scope of the present invention.
Claims (2)
1. A control method of a three-switch converter topological circuit for a switched reluctance motor is characterized by comprising the following steps: each bridge arm of the topological circuit is formed by sequentially connecting three controllable switching tubes S1, S2 and S3 with built-in diodes in series, each phase winding is connected to the upper node and the lower node of the adjacent bridge arm respectively, the upper node is the intersection point of S1 and S2, and the lower node is the intersection point of S2 and S3; the control method comprises the following steps: the topology circuit can provide a plurality of excitation modes and a two-phase series-connection conduction channel, and can enable a fault phase to be in series-connection conduction with another phase winding after a certain phase switching tube has an open-circuit fault, so that partial excitation of the fault phase is ensured; after a switch tube of a certain phase has a short-circuit fault, the fault switch tube is manually cut off, and the short-circuit fault is converted into an open-circuit fault.
2. A control method according to claim 1, characterized in that: the device has 8 operation modes, namely a forward excitation mode, a forward upper tube zero voltage follow current mode, a forward lower tube zero voltage follow current mode, a forward negative voltage follow current mode, a reverse excitation mode, a reverse upper tube zero voltage follow current mode, a reverse lower tube zero voltage follow current mode and a reverse negative voltage follow current mode; through the effective combination of 8 operation modes, the ordered bipolar operation of current can be realized, so that the phenomenon of asymmetric magnetic circuits of the switched reluctance motor with even phases can be eliminated, and the balance control of the magnetic circuits is realized.
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| CN1848665A (en) * | 2006-04-06 | 2006-10-18 | 南京航空航天大学 | Three-switch type power converter |
| CN105305859A (en) * | 2015-10-19 | 2016-02-03 | 南京信息工程大学 | Power converter for switched reluctance motor of battery-supercapacitor electric vehicle |
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| CN1848665A (en) * | 2006-04-06 | 2006-10-18 | 南京航空航天大学 | Three-switch type power converter |
| CN105305859A (en) * | 2015-10-19 | 2016-02-03 | 南京信息工程大学 | Power converter for switched reluctance motor of battery-supercapacitor electric vehicle |
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