CN113075622B - Transmitting beam forming method for multi-user communication in radar communication integration - Google Patents

Transmitting beam forming method for multi-user communication in radar communication integration Download PDF

Info

Publication number
CN113075622B
CN113075622B CN202110341320.3A CN202110341320A CN113075622B CN 113075622 B CN113075622 B CN 113075622B CN 202110341320 A CN202110341320 A CN 202110341320A CN 113075622 B CN113075622 B CN 113075622B
Authority
CN
China
Prior art keywords
communication
array
radar
user
beam pattern
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN202110341320.3A
Other languages
Chinese (zh)
Other versions
CN113075622A (en
Inventor
姚雪
聂祥飞
曹湘
刘毓
陈怀柔
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Chongqing Three Gorges University
Original Assignee
Chongqing Three Gorges University
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Chongqing Three Gorges University filed Critical Chongqing Three Gorges University
Priority to CN202110341320.3A priority Critical patent/CN113075622B/en
Publication of CN113075622A publication Critical patent/CN113075622A/en
Application granted granted Critical
Publication of CN113075622B publication Critical patent/CN113075622B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Classifications

    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/28—Details of pulse systems
    • G01S7/282—Transmitters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
    • Y02D30/00—Reducing energy consumption in communication networks
    • Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Remote Sensing (AREA)
  • Radar Systems Or Details Thereof (AREA)

Abstract

The invention discloses a transmitting beam forming method of multi-user communication in radar communication integration, which comprises the following steps: a radar communication integrated signal model suitable for a multi-user communication scene is established; determining a mean square error of the designed transmission beam pattern and an ideal transmission beam pattern as an optimized objective function; determining constraint conditions taking the magnitude of side lobe levels of multiple communication user directions as an optimization problem; using weight vectors u k In the direction of the space angle theta and the weight vectorThe principle that the space power distribution in the-theta direction is the same is that the size optimization constraint of side lobe level of the symmetric direction of the multi-communication user with respect to the array normal is increased, and an optimization problem is established; the communication performance takes the bit error rate as an evaluation standard, the radar performance takes the target arrival angle estimation mean square error as an evaluation standard, and a function is solved. The invention can reduce the number of phased array transmitting beam forming weight vectors to be solved, thereby reducing the times of solving the optimization problem and achieving the purpose of reducing the operand.

Description

Transmitting beam forming method for multi-user communication in radar communication integration
Technical Field
The invention belongs to the field of radar communication integration, and particularly relates to a transmitting beam forming method for multi-user communication in radar communication integration.
Background
The beams referred to in the spatial energy distribution (spatial beam pattern) of the array antenna include mechanically scanned beams and electrically scanned beams. Wherein the mechanically scanned beam changes the pointing direction of the beam by movement of the mechanical device, and for phased arrays, the electrically scanned beam forming relies on transmit beam forming weight vector design. Electronically scanned beamforming is a spatial filtering method that uses a set of sensors to control the energy radiated into various directions in space, specifically by designing the weighting coefficients (weight vectors) of the array antennas to obtain the desired spatial beam pattern. In radar detection, the main lobe of the spatial beam pattern is mainly used, and the side lobe of the spatial beam pattern is not used.
In order to realize the radar communication integrated function, under the condition of guaranteeing the radar main function (namely guaranteeing the main lobe of the space beam pattern to be unchanged), a method for transmitting a side lobe communication symbol is provided, and the method adjusts the side lobe level (the energy in the side lobe direction) of a communication user to transmit the communication symbol under the condition that the control weight vector guarantees the main lobe of the space beam pattern to be unchanged. In addition, on the premise of utilizing a plurality of orthogonal waveforms, the method is similar to the method, and the main lobe of the space beam pattern is ensured to be unchanged through controlling the weight vector, and the level of the side lobe level (the energy in the side lobe direction) pointing to a communication user is adjusted to transmit the communication bit. Both the above two methods can realize multi-user communication after improvement, however, because the acquisition of each weight vector needs to solve the corresponding optimization problem once and the number of the needed weight vectors is very large, the radar communication integrated emission beam forming based on the above method can bring about the problem of huge calculation amount requirement.
Disclosure of Invention
In order to solve the problems, the invention provides a transmitting beam forming method for multi-user communication in radar communication integration.
The invention relates to a transmitting beam forming method of multi-user communication in radar communication integration, which comprises the following steps:
step 1: and a radar communication integrated signal model suitable for a multi-user communication scene is established.
Step 2: an objective function optimized with respect to the mean square error of the designed transmit beam pattern and the ideal transmit beam pattern is determined.
Step 3: and determining constraint conditions taking the magnitude of side lobe levels of multiple communication user directions as an optimization problem.
Step 4: using weight vectors u k In the direction of the space angle theta and the weight vectorAnd in the principle that the space power distribution in the-theta direction is the same, the optimization constraint of the magnitude of sidelobe level of the multi-communication user in the direction of array normal symmetry (namely the virtual multi-communication user direction) is increased, and the optimization problem is established.
Step 5: the communication performance takes Bit Error Rate (BER) as an evaluation standard, radar performance takes a target arrival angle (DOA, direction Of Arrival) estimation mean square Error (RMSE, root-mean Square Error) as an evaluation standard, and a function is solved.
Further, the application scenario of the signal model in step 1 is: the radar communication integrated transmitting array, the radar receiving array, the communication receiving arrays and the rotary table; the transmitting array and the radar receiving array are positioned on the rotary table, and the rotary table can mechanically rotate the transmitting array and the radar receiving array, so that the main lobe direction of the space directional diagram is controlled; the transmitting array is M t The array element linear array, the radar receiving array is M r A linear array of array elements.
The transmit antenna input baseband signal S is represented as:
wherein ,uk K=1, 2, …, K is M t X 1 transmit beam weight vector;k orthogonal waveforms, P is the number of fast time sampling points for each pulse repetition time; lambda (lambda) k K=1, …, K is the energy distribution factor under certain conditions of total energy emitted, (·) * Representing the complex conjugate.
The radar receiving baseband signal is provided with Q far-field targets positioned in the main lobe of the space beam pattern, wherein the radar receiving baseband signal is as follows:
wherein ,βq The radar cross-sectional area fluctuation parameter is the radar cross-sectional area fluctuation parameter of the target and obeys the Swerling II type; alpha (theta) q) and b(θq ) Steering vectors for transmit and receive arrays, respectively; x is X 1 Indicating clutter coming in from the sidelobe region; z is Z 1 Is zero mean variance ofAdditive white gaussian noise of (2); />Is M r ×M r Is a unit array of (a) units.
N communication receiving arrays are arranged at any position of a sidelobe area, and all orthogonal waveforms used in transmission are known; the nth communication receiving array is M n A linear array of array elements; the received baseband signal may be expressed as:
Y n ＝a n c n (φ n )α T (θ n )S+n n
wherein ,an Is the channel influencing factor, phi, of the transmitting array and the nth communication receiver n Is the angle at which the signal arrives at the nth communication receiver c n (φ n ) Is the steering vector of the nth communication receiving array, n n Is M n Zero mean, variance of x PAdditive white gaussian noise of (c).
Further, in the step 2, the expression of the optimization objective function is:
wherein ,representing an ideal spatial beam pattern, (·) H Represents conjugate transpose, u k Represents the weight vector, θ represents the main lobe region.
Further, in the step 3, the side lobe level constraint expression is:
where ε is the upper limit of the sidelobe region level,representing the sidelobe region.
The sidelobe level constraint expression pointing to the direction of the multi-communication user is as follows:
wherein a= [ α (θ) 1 ),α(θ 2 ),…,α(θ N )]Representing transmit array steering vectors directed to N communication receivers;side lobe levels representing the directions of N communication receivers, eta being a very small positive number.
Further, the sidelobe level constraint expression added in the step 4, which points to the virtual multi-communication user direction, is as follows:
wherein, A' = [ alpha (-theta) 1 ),α(-θ 2 ),…,α(-θ N )]Representing transmit array steering vectors directed to N virtual communication receivers;side lobe levels representing the directions of N virtual communication receivers, eta being a very small positive number.
The final optimization problem is:
the beneficial technical effects of the invention are as follows:
the beam in the transmit beamforming method of the present invention is a beam that combines mechanical scanning and electrical scanning. Wherein mechanical scanning is used to change the main lobe direction of the beam, and electronically scanned transmit beamforming relies on phased array transmit beamforming weight vector design. Phased array-based transmitting beam forming weight vector u k Beamforming weight vector in the direction of spatial angle θThe method establishes a new optimization model for realizing phased array transmitting beam forming weight vector design by adding additional side lobe constraint conditions on the principle that the space power distribution in the-theta direction is the same, and the model can reduce the number of phased array transmitting beam forming weight vectors to be solved, thereby reducing the frequency of solving the optimization problem and achieving the purpose of reducing the operand. The communication performance of the method is measured by Bit Error Rate (BER), and the simulation result shows that the communication performance of the transmission beam forming method with low operand proposed herein is nearly consistent with that of the transmission beam forming method in the prior art. Because the main lobe is essentially unchanged in the spatial pattern, radar performance is essentially unchanged during transmission of the communication information.
Drawings
FIG. 1 is a radar communication integrated multi-user communication scenario;
fig. 2 is a prior art transmit beam pattern (bit transmission);
fig. 3 is a prior art transmit beam pattern (symbol transmission, where communication user 1 transmits information 00);
fig. 4 is a prior art transmit beam pattern (symbol transmission, wherein communication user 1 transmits information 01);
fig. 5 is a prior art transmit beam pattern (symbol transmission, in which communication user 1 transmits information 10);
fig. 6 is a prior art transmit beam pattern (symbol transmission, in which communication user 1 transmits information 11);
fig. 7 is a diagram showing a new technique of transmit beam pattern (bit transmission);
fig. 8 is a diagram showing a new technology transmission beam pattern (symbol transmission, in which communication user 1 transmits information 00);
fig. 9 is a diagram showing a new technology transmission beam pattern (symbol transmission, in which communication user 1 transmits information 01);
fig. 10 is a diagram of a transmission beam pattern (symbol transmission in which the communication user 1 transmits information 10) in which a new technique is proposed;
fig. 11 is a diagram showing a new technology transmission beam pattern (symbol transmission in which the communication user 1 transmits information 11);
fig. 12 is a graph showing the variation of the information average Bit Error Rate (BER) with the Signal-to-noise Ratio (SNR);
fig. 13 is a graph of the variation of the target spatial angle of arrival (DOA) estimate (RMSE) with signal-to-noise ratio (SNR).
Detailed Description
The invention will be described in further detail with reference to the accompanying drawings and the detailed description.
The invention relates to a transmitting beam forming method of multi-user communication in radar communication integration, which comprises the following steps:
1. and a radar communication integrated signal model suitable for a multi-user communication scene is established.
As shown in fig. 1, the application scenario of the signal model is: the radar communication integrated transmitting array, the radar receiving array, the communication receiving arrays and the rotary table; the transmitting array and the radar receiving array are positioned on the rotary table, and the rotary table can mechanically rotate the transmitting array and the radar receiving array, so that the main lobe direction of the space directional diagram is controlled; the transmitting array is M t The array element linear array, the radar receiving array is M r A linear array of array elements. Without loss of generality, it is assumed that the integrated transmit array and radar receive array are very closely spaced, and that the far-field target reaches the same spatial angle of both arrays. The main function of the system is the radar detection function, so that the radar function is not affected when multi-user communication is required. By designing the transmitted waveThe beam forming weight vector method keeps the main lobe area of the transmitting space beam pattern unchanged for radar detection, and changes the side lobe level in the direction of the communication receiver to transmit communication information.
It should be noted that, based on the cognitive radar system, it is assumed that the spatial direction angle of the communication receiver located at the side lobe is known when the weight vector is designed.
The transmit antenna input baseband signal S is represented as:
wherein ,uk K=1, 2, …, K is M t X 1 transmit beam weight vector;k orthogonal waveforms, P is the number of fast time sampling points for each pulse repetition time; lambda (lambda) k K=1, …, K is the energy distribution factor under certain conditions of total energy emitted, (·) * Representing the complex conjugate.
The radar receiving baseband signal is provided with Q far-field targets positioned in the main lobe of the space beam pattern, wherein the radar receiving baseband signal is as follows:
wherein ,βq The radar cross-sectional area fluctuation parameter is the radar cross-sectional area fluctuation parameter of the target and obeys the Swerling II type; alpha (theta) q) and b(θq ) Steering vectors for transmit and receive arrays, respectively; x is X 1 Indicating clutter coming in from the sidelobe region; z is Z 1 Is zero mean variance ofAdditive white gaussian noise of (2); />Is M r ×M r Is a unit array of (a) units.
N communication receiving arrays are arranged at any position of a sidelobe area, and all orthogonal waveforms used in transmission are known; the nth communication receiving array is M n A linear array of array elements; the received baseband signal may be expressed as:
Y n ＝a n c n (φ n )α T (θ n )S+n n
wherein ,an Is the channel influencing factor, phi, of the transmitting array and the nth communication receiver n Is the angle at which the signal arrives at the nth communication receiver c n (φ n ) Is the steering vector of the nth communication receiving array, n n Is M n Zero mean, variance of x PAdditive white gaussian noise of (c).
2. An objective function optimized with respect to the mean square error of the designed transmit beam pattern and the ideal transmit beam pattern is determined. The optimization objective function expression is:
wherein ,representing an ideal spatial beam pattern, (·) H Represents conjugate transpose, u k Represents the weight vector, θ represents the main lobe region.
3. Constraint conditions with side lobe level size as an optimization problem are determined. The sidelobe level constraint expression is:
where ε is the upper limit of the sidelobe region level,representing side lobe regions;
the sidelobe level constraint expression pointing to the direction of the multi-communication user is as follows:
wherein a= [ α (θ) 1 ),α(θ 2 ),…,α(θ N )]Representing transmit array steering vectors directed to N communication receivers;side lobe levels representing the directions of N communication receivers, eta being a very small positive number.
Epsilon is the upper limit of the side lobe area level, and the value is not easy to be set too high so as not to influence the radar detection performance. Delta k The side lobe level of N communication receiver directions is shown, the value is set to have a certain gap when different communication symbols or communication bits are transmitted, and the correct demodulation of the transmitted communication information is ensured.
4. Using weight vectors u k In the direction of the space angle theta and the weight vectorAnd the principle that the spatial power distribution in the-theta direction is the same is that the size optimization constraint of the side lobe level of the virtual multi-communication user direction is increased, and the optimization problem is established.
The added sidelobe level constraint expression pointing to the virtual multi-communication user direction is as follows:
wherein, A' = [ alpha (-theta) 1 ),α(-θ 2 ),…,α(-θ N )]Representing transmit array steering vectors directed to N virtual communication receivers;side lobe level representing N virtual communication receiver directions, eta is a very small positive number;
the parameter η represents the fluctuation range of the sidelobe level values of the N communication receiver directions or the N virtual communication receiver directions, and can be set manually by a technician according to application requirements. In practical settings, consider the following two points:
(1) When the communication demodulation effect is expected to be good, the larger the sidelobe level difference representing different communication symbols or different communication bits is, the better;
(2) The greater the dynamic range of the sidelobe levels of the N communication receiver directions or the N virtual communication receiver directions, the better as the desired spatial beam pattern is closer to the ideal pattern.
When solving the optimization problem, the variable u k And (3) withIndependent of each other. Thus, can be achieved by alternate iteration u k And->Thereby minimizing the objective function. Specifically, assume u k (q-1) And->Respectively represent u k And->Solution at the q-1 th iteration. Fix u k (q-1) The minimum objective function can be calculated as +.>Namely:
the optimal solution of the above problem is
FixingMinimizing the convex optimization problem below can yield u k (q) 。
The above steps are then repeated until convergence. If the iteration number exceeds the preset maximum iteration number K max Or the mean square error of the designed antenna beam pattern and the ideal beam pattern is less than epsilon 0 The iteration stops. To ensure algorithm convergence, a maximum number of iterations K is typically set max Is a larger positive integer epsilon 0 Is a very small positive number.
Specific examples:
parameter setting: the radar communication integrated transmitting array is the array element number M t =10, the array element spacing is a uniform linear array of half wavelength, the main lobe area of the space beam pattern is θ= [ -10 °,10 °]Normal detection of radar requires that the sidelobe level is at least 20dB below the main lobe (i.e. epsilon=0.1), and 1 communication symbol is transmitted per radar pulse repetition period, the communication symbol comprising L B =2 bits of information. With 2 communication users located at θ 1 = -50 ° and θ 2 = 30 ° direction.
Embodiment one:
if the method of sidelobe communication bit transmission is adopted in the prior art, J is solved in the example bit ＝2 2 =4 times optimization problem P 2 4 different weight vectors are obtained. Wherein problem constraint parameters are optimizedOr (b)η＝0。/>Indicating that the transmission bit is 1,is 10 -4 Indicating that the transmission bit is 0. Then the communication parameters delta of 2 users are realized k There will be 4 different possibilities, representing the transmission of 0 and 0, 0 and 1, 1 and 0 and 1, respectively, to 2 communication directions. For convenience of explanation, the existing weight vector design technique is simply referred to as EX-WVD. Fig. 2 is a prior art transmit beam pattern (bit transmission). As shown in fig. 2, the main lobe of all the transmit spatial beam patterns remains substantially unchanged, meaning that the detection function of the radar can be well ensured. The sidelobe levels pointing to the 2 communication directions vary from one transmission information bit to another.
If the prior art adopts a sidelobe communication symbol transmission method, J is solved in the example sym ＝(2 2 ) 2 =16 optimization problem P 2 16 different weight vectors are obtained. Wherein problem constraint parameters are optimizedCan be from Is selected from the group consisting of a plurality of combinations of the above. Wherein-> Representing transmission traffic symbols 00, 01, 10, 11, respectively. Then the communication parameters delta of 2 users are realized k There will be 16 different possibilities, representing transmission of symbols 00 and 00, 00 and 01, 00 and 10, 00 and 11, 01 and 00, 01 and 01, and 2 communication directions, respectively01. 01 and 10, 01 and 11, 10 and 00, 10 and 01, 10 and 10, 10 and 11, 11 and 00, 11 and 01, 11 and 10, 11 and 11. For convenience of explanation, the existing weight vector design technique is simply referred to as EX-WVD. Fig. 3-6 illustrate prior art transmit beam patterns (symbol transmissions). The main lobe of all the transmitting space beam patterns is basically unchanged, which means that the detection function of the radar can be well ensured. The sidelobe levels pointing in the 2 communication directions vary from one transmission information symbol to another.
Embodiment two:
if the method of sidelobe communication bit transmission in the technology proposed herein is adopted, the solution is adopted in the exampleSub-optimization problem P 2 2 different weight vectors are obtained, the other 2 weight vectors being the complex conjugate of the solved weight vector. The maximum iteration number of the iteration solution optimization problem is K max =200, or the mean square error is less than ε 0 ＝10 -6 The iteration is stopped. Specifically, if a parameter is used->Andthen under the parameter setting, the solved weight vector controls the space beam direction to be positioned at theta 1 、θ 2 The transmission information bits to the communication receiver are 1 and 1, respectively. The complex conjugate of this weight vector will control the spatial beam pattern to lie at θ 1 、θ 2 The transmission information bits are 0 and 0, respectively, to the communication receiver. If parameters are adoptedThen under the parameter setting, the solved weight vector controls the space beam direction to be positioned at theta 1 、θ 2 The transmission information bits to the communication receiver are 1 and 0, respectively. The complex conjugate of this weight vector will control the spatial beam pattern to lie at θ 1 、θ 2 The transmission information bits are 0 and 1, respectively, to the communication receiver. For convenience of explanation, the existing weight vector design technique is abbreviated as CE-WVD. Fig. 7 is a transmit beam pattern (bit transmission) of the presently proposed technology. As shown in fig. 7, the main lobe of all the transmit spatial beam patterns remains substantially unchanged, meaning that the detection function of the radar can be well guaranteed. The sidelobe levels pointing to the 2 communication directions vary from one transmission information bit to another. The solid line represents the spatial beam pattern of the solution optimization resulting in weight vector control, and the dashed line represents the spatial beam pattern of the complex conjugate weight vector control. It can be seen that the solid and dashed patterns are symmetrical about the normal of the array antenna.
The method for sidelobe communication symbol transmission in the technology proposed herein is adopted, and is solved in the exampleSub-optimization problem P 2 8 different weight vectors are obtained, the other 8 weight vectors being the complex conjugate of the solved weight vector. Let-> Representing transmission information symbols 00, 01, 10, 11, respectively. The optimization parameter settings should follow the following rules: when the information symbol 00 (delta) 1 ) When transmitted to a communication receiver located at θ, the information symbol 11 (Δ 4 ) Is transmitted to a virtual communication receiver located at-theta. When information symbol 01 (delta) 2 ) When transmitted to a communication receiver located at θ, the information symbol 10 (Δ 3 ) Is transmitted to a virtual communication receiver located at-theta. For example, the parameters are Then under the parameter setting, the solved weight vector controls the space beam direction pattern to be orientedAt theta 1 、θ 2 The transmission information symbols to the communication receiver are 00 and 10, respectively. The complex conjugate of this weight vector will control the spatial beam pattern to lie at θ 1 、θ 2 The transmission information bits to the communication receiver are 11 and 01, respectively.
It can be observed that the spatial beam patterns shown in fig. 8 and 11 are symmetric about the normal, the solid line represents the spatial beam pattern of which the solution optimization yields the weight vector control, and the broken line represents the spatial beam pattern of which the complex conjugate weight vector control. The spatial beam patterns shown in fig. 9 and 10 are also symmetrical about the normal. Likewise, the solid line represents the spatial beam pattern of which the solution optimization yields the weight vector control, and the dotted line represents the spatial beam pattern of which the complex conjugate weight vector control. The main lobe of all the transmitting space beam patterns is basically unchanged, which means that the detection function of the radar can be well ensured. The sidelobe levels pointing in the 2 communication directions vary from one transmission information symbol to another.
The proposed technique and prior art herein result in a transmit beam pattern, and the computer CPU run time (InterCore i5-6200U@2.3GHz and RAM 8GHz) for solving for the ownership vector when using sidelobe communication symbol transmission and sidelobe communication bit transmission, respectively, is shown in Table 1.
Table 1 comparative time
By the method CPU runtime
EX-WVD (bit Transmission) 507s
EX-WVD (symbol transmission) 2167s
CE-WVD (bit transmission) 260s
CE-WVD (symbol transmission) 1102s
Embodiment III:
2 independent contains 10 6 The sequence of uncoded communication symbols, each containing 2 bits of information, is transmitted to 2 communication receivers, respectively. The 2 communication receiving arrays are assumed to be uniform linear arrays with the number of array elements being 10 and the array element spacing being half wavelength. The variation of Bit Error Rate (BER) with signal-to-noise ratio (SNR) is shown in fig. 12 by using the transmission beam patterns of the present technology and the prior art, and using the sidelobe communication symbol transmission and the sidelobe communication bit transmission, respectively. Obviously, the performance of the proposed transmit beamforming method is similar to existing transmit beamforming methods. But the method proposed herein is less computationally intensive than the existing methods.
Embodiment four:
assume that 2 far field targets are located at spatial angles of 3 ° and 5 °, respectively. The target reflection coefficient is assumed to be constant at each radar pulse repetition period, but to be variable between pulses, subject to a normal distribution. The number of array elements of the radar receiving array is 50, and the number of pulses in one coherent processing interval is 100. Using the techniques presented herein and prior art transmit beam patterns, angle of arrival (DOA) estimation was performed using the MUSIC (Multiple Signal Classification) algorithm. 1000 independent experiments were performed to determine the average of the minimum mean square error (RMSE). Fig. 13 shows the variation of minimum mean square error (RMSE) with signal-to-noise ratio (SNR). Obviously, the performance of the proposed transmit beamforming method is similar to existing transmit beamforming methods.
The invention provides a transmitting beam forming method for multi-user communication in radar communication integration. In which the machine scansFor changing the main lobe direction of the beam, electronically scanned transmit beamforming relies on phased array transmit beamforming weight vector design. If different information transmission (multi-user communication) of N communication directions is to be realized, a method of sidelobe communication symbol transmission is adopted, if the prior art is adopted, the method needs to solveSub-optimization problem P 2 Obtain->A different weight vector (assuming that the radar transmits 1 communication symbol, which is L, at a pulse repetition interval B Bit information), if the technique proposed herein is used, only the +.>Sub-optimization problem P 1 Obtain->A different weight vector. Method for transmitting communication bits by using side lobe, if the prior art is adopted, J is needed to be solved bit ＝(2) N Sub-optimization problem P 2 Obtaining J bit ＝(2) N A different weight vector, if the technology proposed herein is adopted, only the +.>Sub-optimization problem P 1 Obtain->A different weight vector. Thereby saving the calculation amount. Optimization problem of the prior art P 2 The following are provided:

Claims (1)

1. the transmitting beam forming method for multi-user communication in radar communication integration is characterized by comprising the following steps:
step 1: establishing a radar communication integrated signal model suitable for a multi-user communication scene;
the application scene of the signal model is as follows: the radar communication integrated transmitting array, the radar receiving array, the communication receiving arrays and the rotary table; the transmitting array and the radar receiving array are positioned on the rotary table, and the rotary table can mechanically rotate the transmitting array and the radar receiving array, so that the main lobe direction of the space directional diagram is controlled; the transmitting array is M t The array element linear array, the radar receiving array is M r A linear array of array elements;
the transmit antenna input baseband signal S is represented as:
wherein ,uk K=1, 2, …, K is M t X 1 transmit beam weight vector;k orthogonal waveforms, P is the number of fast time sampling points for each pulse repetition time; lambda (lambda) k K=1, …, K is the energy distribution factor under certain conditions of total energy emitted, (·) * Representing complex conjugation;
the radar receiving baseband signal is provided with Q far-field targets positioned in the main lobe of the space beam pattern, wherein the radar receiving baseband signal is as follows:
wherein ,βq The radar cross-sectional area fluctuation parameter is the radar cross-sectional area fluctuation parameter of the target and obeys the Swerling II type; alpha (theta) q) and b(θq ) Respectively, hairTransmitting and receiving array steering vectors; x is X 1 Indicating clutter coming in from the sidelobe region; z is Z 1 Is zero mean variance ofAdditive white gaussian noise of (2); />Is M r ×M r A unit array of (a);
n communication receiving arrays are arranged at any position of a sidelobe area, and all orthogonal waveforms used in transmission are known; the nth communication receiving array is M n A linear array of array elements; the received baseband signal is expressed as:
Y n ＝a n c n (φ n )α T (θ n )S+n n
wherein ,an Is the channel influencing factor, phi, of the transmitting array and the nth communication receiver n Is the angle at which the signal arrives at the nth communication receiver c n (φ n ) Is the steering vector of the nth communication receiving array, n n Is M n Zero mean, variance of x PAdditive white gaussian noise of (2);
step 2: determining a mean square error of the designed transmission beam pattern and an ideal transmission beam pattern as an optimized objective function; the optimization objective function expression is:
wherein ,representing an ideal spatial beam pattern, (·) H Represents conjugate transpose, u k The weight vector is represented by a vector of weights,θ represents the main lobe region;
step 3: determining constraint conditions taking the magnitude of side lobe levels of multiple communication user directions as an optimization problem;
the sidelobe level constraint expression is:
where ε is the upper limit of the sidelobe region level,representing side lobe regions;
the sidelobe level constraint expression pointing to the direction of the multi-communication user is as follows:
wherein a= [ α (θ) 1 ),α(θ 2 ),…,α(θ N )]Representing transmit array steering vectors directed to N communication receivers;side lobe level representing N communication receiver directions, eta is a very small positive number;
step 4: using weight vectors u k In the direction of the space angle theta and the weight vectorThe principle that the spatial power distribution in the-theta direction is the same is that the optimization constraint of the magnitude of the side lobe level of the direction of the multi-communication user with respect to the array normal symmetrical direction, namely the virtual multi-communication user is increased, and the optimization problem is established;
the added sidelobe level constraint expression pointing to the virtual multi-communication user direction is as follows:
wherein, A' = [ alpha (-theta) 1 ),α(-θ 2 ),…,α(-θ N )]Representing transmit array steering vectors directed to N virtual communication receivers;side lobe level representing N virtual communication receiver directions, eta is a very small positive number;
the final optimization problem is:
step 5: the communication performance takes the bit error rate as an evaluation standard, the radar performance takes the target arrival angle estimation mean square error as an evaluation standard, and a function is solved.
CN202110341320.3A 2021-03-30 2021-03-30 Transmitting beam forming method for multi-user communication in radar communication integration Active CN113075622B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202110341320.3A CN113075622B (en) 2021-03-30 2021-03-30 Transmitting beam forming method for multi-user communication in radar communication integration

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202110341320.3A CN113075622B (en) 2021-03-30 2021-03-30 Transmitting beam forming method for multi-user communication in radar communication integration

Publications (2)

Publication Number Publication Date
CN113075622A CN113075622A (en) 2021-07-06
CN113075622B true CN113075622B (en) 2023-08-15

Family

ID=76611650

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202110341320.3A Active CN113075622B (en) 2021-03-30 2021-03-30 Transmitting beam forming method for multi-user communication in radar communication integration

Country Status (1)

Country Link
CN (1) CN113075622B (en)

Families Citing this family (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113612708B (en) * 2021-08-09 2022-06-07 电子科技大学 Multi-user communication radar integrated system based on time division multiple access
CN113466796B (en) * 2021-08-16 2023-05-26 电子科技大学 Radar communication integrated method based on coherent phase modulation broadcast mode
CN114675238B (en) * 2022-02-24 2023-11-03 中国人民解放军国防科技大学 Radar communication integrated waveform direct optimization method and system
CN114928389B (en) * 2022-05-09 2023-04-07 浙江大学 Communication perception integrated waveform design method and device, computer equipment and storage medium
CN116633742B (en) * 2023-07-25 2023-09-19 天津师范大学 Dual-function radar communication design method based on direction modulation
CN117665709A (en) * 2023-12-07 2024-03-08 天津师范大学 Distributed antenna array dual-function radar communication design method based on direction modulation

Citations (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101950014A (en) * 2010-09-02 2011-01-19 西安电子科技大学 MIMO (Multiple Input Multiple Output) radar wave shape online designing method
CN104392034A (en) * 2014-11-17 2015-03-04 南京信息工程大学 L1/2-norm-based sparse linear array optimization method
CN104618006A (en) * 2015-03-03 2015-05-13 重庆大学 Distributed multi-user downstream MIMO robust beam forming method
CN105281817A (en) * 2015-10-08 2016-01-27 东南大学 Robust wave beam molding method based on distributed bidirectional relay system
CN106646387A (en) * 2016-12-16 2017-05-10 西安电子科技大学 MIMO radar method capable of resisting active interference based on emission wave beam domain
CN106772260A (en) * 2017-03-31 2017-05-31 西安电子科技大学 Radar array and difference beam directional diagram optimization method based on convex optimized algorithm
CN108667493A (en) * 2018-03-14 2018-10-16 西安电子科技大学 A kind of beam form-endowing method towards under NLOS scenes in extensive MIMO
CN108919199A (en) * 2018-07-12 2018-11-30 南京航空航天大学 Side lobe suppression method, the array Sparse methods of multi-beam imaging sonar thinned array
EP3690483A1 (en) * 2019-02-04 2020-08-05 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. A method for synthesis of antenna array layouts or selection of waveform in a set of mutually incoherent apertures for radar and radio-frequency applications
CN111651719A (en) * 2020-06-04 2020-09-11 湖北工业大学 Robust adaptive beam forming method based on contraction estimation covariance matrix reconstruction

Patent Citations (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101950014A (en) * 2010-09-02 2011-01-19 西安电子科技大学 MIMO (Multiple Input Multiple Output) radar wave shape online designing method
CN104392034A (en) * 2014-11-17 2015-03-04 南京信息工程大学 L1/2-norm-based sparse linear array optimization method
CN104618006A (en) * 2015-03-03 2015-05-13 重庆大学 Distributed multi-user downstream MIMO robust beam forming method
CN105281817A (en) * 2015-10-08 2016-01-27 东南大学 Robust wave beam molding method based on distributed bidirectional relay system
CN106646387A (en) * 2016-12-16 2017-05-10 西安电子科技大学 MIMO radar method capable of resisting active interference based on emission wave beam domain
CN106772260A (en) * 2017-03-31 2017-05-31 西安电子科技大学 Radar array and difference beam directional diagram optimization method based on convex optimized algorithm
CN108667493A (en) * 2018-03-14 2018-10-16 西安电子科技大学 A kind of beam form-endowing method towards under NLOS scenes in extensive MIMO
CN108919199A (en) * 2018-07-12 2018-11-30 南京航空航天大学 Side lobe suppression method, the array Sparse methods of multi-beam imaging sonar thinned array
EP3690483A1 (en) * 2019-02-04 2020-08-05 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. A method for synthesis of antenna array layouts or selection of waveform in a set of mutually incoherent apertures for radar and radio-frequency applications
CN111651719A (en) * 2020-06-04 2020-09-11 湖北工业大学 Robust adaptive beam forming method based on contraction estimation covariance matrix reconstruction

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
"导向矢量和协方差矩阵联合迭代估计的稳健波束形成算法";杨志伟;《电子与信息学报》;第40卷(第12期);2874-2880 *

Also Published As

Publication number Publication date
CN113075622A (en) 2021-07-06

Similar Documents

Publication Publication Date Title
CN113075622B (en) Transmitting beam forming method for multi-user communication in radar communication integration
Zarifi et al. Collaborative null-steering beamforming for uniformly distributed wireless sensor networks
CN109921837B (en) Steady wave beam forming method based on multicast frequency control array direction modulation
EP3091681A1 (en) Beamforming-based communication method and apparatus
CN107181519B (en) Null steering expansion 3D-MIMO beam forming method based on moving target DOA
WO2022170783A1 (en) Beam control method and system for array antenna based on frequency diversity, and controller
CN102830387A (en) Data preprocessing based covariance matrix orthogonalization wave-beam forming method
CN107979404B (en) Adaptive beam forming method based on virtual array null broadening
CN113325385B (en) Anti-interference method for phased array-MIMO radar mode transmit-receive beam forming
CN109861933A (en) A kind of millimeter wave mimo channel estimation method based on MUSIC algorithm and precoding
WO2013178166A1 (en) Communication device, method and apparatus for forming beam
CN107342836B (en) Weighting sparse constraint robust ada- ptive beamformer method and device under impulsive noise
Khan et al. Antenna beam-forming for a 60 Ghz transceiver system
Ozkaptan et al. Optimal precoder design for MIMO-OFDM-based joint automotive radar-communication networks
Xiong et al. Sparse reconstruction-based beampattern synthesis for multi-carrier frequency diverse array antenna
CN113050079A (en) Joint generation method for radar transmitting waveform and receiving filter weight vector
CN107918112A (en) Combined transceiving Beamforming Method based on the collaboration of active passive radar
CN116614161A (en) Radar communication integrated beam forming method based on linear constraint power distribution
CN114499615B (en) Near-far field unified transmitting beam forming method in terahertz communication system
CN114726464B (en) Method for generating uplink and downlink asymmetric channel model parameters
CN109617258A (en) Using the RF energy collection system and method for blind adaptive beamforming algorithm
CN113466796B (en) Radar communication integrated method based on coherent phase modulation broadcast mode
CN111082843B (en) Method for realizing single carrier equalization aiming at intelligent multi-antenna beam forming
CN115396265A (en) Angle domain channel estimation method based on symmetric non-uniform array matrix reconstruction
Ali et al. 2D-AOA estimation and tilt angle adaptation for 3D beamforming interference reduction in massive MIMO

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant