CN113067165B - Broadband miniaturized Fabry-Perot resonant cavity antenna - Google Patents

Broadband miniaturized Fabry-Perot resonant cavity antenna Download PDF

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CN113067165B
CN113067165B CN202110296540.9A CN202110296540A CN113067165B CN 113067165 B CN113067165 B CN 113067165B CN 202110296540 A CN202110296540 A CN 202110296540A CN 113067165 B CN113067165 B CN 113067165B
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layer
dielectric substrate
antenna
reflecting surface
reflecting
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CN113067165A (en
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翁子彬
关云杰
李雨桐
吕乐玮
焦永昌
张立
赵钢
田季丰
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Xidian University
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Xidian University
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/14—Reflecting surfaces; Equivalent structures
    • H01Q15/145—Reflecting surfaces; Equivalent structures comprising a plurality of reflecting particles, e.g. radar chaff
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/10—Resonant slot antennas
    • H01Q13/18—Resonant slot antennas the slot being backed by, or formed in boundary wall of, a resonant cavity ; Open cavity antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H01Q19/18—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces having two or more spaced reflecting surfaces
    • H01Q19/185—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces having two or more spaced reflecting surfaces wherein the surfaces are plane

Abstract

The invention discloses a broadband high-gain Fabry-Perot resonant cavity antenna based on a regular hexagon unit, which comprises three layers of medium substrates (2, 4 and 7) at the upper layer, the middle layer and the lower layer, and the medium substrates are fixed into a whole through a low-dielectric-constant nylon frame (9). The upper layer medium substrate and the lower layer medium substrate are respectively an upper reflecting surface (1) and a lower reflecting surface (3) which form a partial reflecting surface structure; the lower surface of the middle layer dielectric substrate is a parasitic patch (5), and the parasitic patch form a radiator; the upper surface of the bottom layer medium substrate is a metal floor (6), the lower surface of the bottom layer medium substrate is a graded microstrip feeder (8), the metal floor, the graded microstrip feeder and the graded microstrip feeder form a feed source, the upper reflecting surface and the lower reflecting surface of the part (1, 3) both adopt regular hexagonal units which are periodically arranged, and the units are arranged along the perpendicular bisector direction of three adjacent sides of a regular hexagon; two rectangular gaps for widening impedance bandwidth are carved on the metal floor. The invention widens the bandwidth of the antenna, improves the gain and can be used for satellite communication and radar systems.

Description

Broadband miniaturized Fabry-Perot resonant cavity antenna
Technical Field
The invention belongs to the technical field of antennas, and further relates to a Fabry-Perot resonant cavity antenna which can be used for satellite communication and radar systems.
Background
With the rapid development of modern and next-generation communication, electronic countermeasure and other technologies, the role of the antenna becomes more and more important. In the fields of on-board antennas, remote transmission, base station antennas, and the like, people often need an antenna with a particularly strong ability to receive and transmit radio signals in a particular direction, and thus the demand for a high-gain directional antenna is increasing. Meanwhile, miniaturization and light weight are inevitable trends in modern technology development, and antennas are no exception. Although conventional high-gain antennas, such as microstrip array antennas, lens antennas, waveguide horn antennas, and reflective array antennas, can provide the desired high gain, their use is limited due to their large size, complex design and processing, and high manufacturing cost. The Fabry-Perot resonant cavity antenna is one of high-gain antennas, has obvious advantages in the aspects of miniaturization, high efficiency, assembly flexibility and the like, and is widely concerned in the field of domestic and foreign antennas. However, because the fabry-perot resonator antenna belongs to a cavity antenna, and the 3dB gain bandwidth of the fabry-perot resonator antenna is still very narrow, how to widen the 3dB gain bandwidth of the fabry-perot resonator antenna and make the antenna more miniaturized becomes a research direction in the field of the fabry-perot resonator antenna.
Normally, a fabry-perot resonator antenna is composed of a feed source, a metal floor and a partially reflecting surface. A resonant cavity is formed between the partial reflection surface and the metal floor, electromagnetic waves radiated from the feed source can be reflected in the resonant cavity, and the electromagnetic waves reflected for multiple times are superposed on the outer surface of the partial reflection surface in the same phase, so that the gain of the feed source antenna is improved. However, since the fabry-perot resonator antenna is one of cavity antennas, the 3dB gain bandwidth is small and the size is generally large, so that it is a challenge for designers to widen the gain bandwidth while miniaturizing the antenna.
In response to the above problems, researchers do not proposeFew solutions are available. For example, K.Konstantinis, A.P.Fereidis, and P.S.Hall, in IEEE transactions Propaga, vol.63, No.1, pp.423-427, Jan.2015 journal, a Broadband High-Gain Fabry-Perot resonator antenna operating in the 13-14.6GHz band is proposed. The feed source adopts a slot antenna, and the total number of partial reflecting surfaces is three. The two sides of the dielectric substrate with the partial reflecting surface are respectively printed with a square patch and an etched square ring so as to generate a phase gradient with a positive slope and improve the gain bandwidth of the antenna. However, the fabry-perot resonator antenna using the multi-layered partially reflective surface has a small bandwidth and a large size. Experiments show that only 14% of the antenna can reach 3dB gain bandwidth in the working frequency range, and the aperture surface of the antenna is as high as 16 lambda0 2. The gain bandwidth of the antenna is widened at the cost of increasing the caliber size of the antenna, so that the power loss of the antenna is increased, and the practicability of the antenna is reduced.
Disclosure of Invention
The invention aims to provide a broadband miniaturized Fabry-Perot resonant cavity antenna aiming at the defects of the prior art so as to improve the gain bandwidth of the Fabry-Perot resonant cavity antenna and reduce the caliber surface size of the antenna.
In order to achieve the purpose, the technical scheme of the invention is as follows:
a broadband miniaturization Fabry-Perot resonant cavity antenna comprises a first layer of dielectric substrate 2, a second layer of dielectric substrate 5, a third layer of dielectric substrate 7, a fourth layer of dielectric substrate 10 and a support 12, wherein the four substrates are fixed into a whole through the support 12 from top to bottom; the first layer of dielectric substrate 2 and the upper reflecting surface 1 and the lower reflecting surface 3 thereof form a first layer of reflecting structure; the second layer of dielectric substrate 5 and the upper reflecting surface 4 and the lower reflecting surface 6 thereof form a second layer of reflecting structure; the lower surface of the third layer of dielectric substrate 7 is provided with a parasitic patch 8, and the parasitic patch form a radiator structure; the upper surface of the fourth layer of dielectric substrate 10 is a metal floor 9, the lower surface is a graded microstrip feeder line 11, and the three form a feed source structure, which is characterized in that:
the upper reflecting surface 1 and the lower reflecting surface 3 of the first layer of reflecting structure and the upper reflecting surface 4 and the lower reflecting surface 6 of the second layer of reflecting structure all adopt regular hexagonal units which are periodically arranged, and the units are arranged along the direction of the perpendicular bisector of three adjacent sides of the regular hexagon;
the support 12 adopts a nylon frame with a low dielectric constant to form a narrow air band gap between the first dielectric substrate 2 and the second dielectric substrate 5, a Fabry-Perot resonant cavity is formed between the lower reflecting surface 6 of the second dielectric substrate and the metal floor 9, and an air band gap is formed between the parasitic patch 8 and the metal floor 9 to inhibit the excitation of the antenna surface wave;
the metal floor 9 has two parallel rectangular slots 91 and 92 etched therein to widen the impedance bandwidth of the antenna.
Preferably, the regular hexagonal units of the upper reflecting surface 1 of the first layer of reflecting structure and the upper reflecting surface 4 of the second layer of reflecting structure are regular hexagonal patch structures;
preferably, the regular hexagonal units of the reflective surface 3 under the first layer of reflective structure are regular hexagonal ring structures;
preferably, the regular hexagonal unit of the reflective surface 6 under the second layer of reflective structure is a combined structure of a regular hexagonal ring and three-leg branches, wherein the three branches are spaced by 60 ° two by two, and mainly function to prolong the path of current, further reduce the size of the unit, and create conditions for miniaturization of the antenna.
Compared with the prior art, the invention has the following advantages:
firstly, in the same type of multilayer broadband Fabry-Perot resonant cavity antenna, the periodically arranged regular hexagon units are firstly adopted, the units are arranged along the perpendicular bisector direction of three adjacent sides of the regular hexagon, and compared with the traditional square units and circular units, the arrangement direction is increased, namely the arrangement among the units is more compact, the coupling is stronger, so that the antenna can be more miniaturized and obtain wider gain bandwidth;
secondly, the parasitic patch and the feeder line are prevented from contacting each other due to the adoption of a feeding mode of coupling the double patches by the double slits, and compared with the traditional slit feeding mode, the parasitic patch and the feeder line have the air band gap, so that surface wave excitation can be well inhibited, the impedance bandwidth of the antenna is favorably improved, and the radiation pattern of the antenna is improved;
thirdly, compared with the same type of multilayer broadband Fabry-Perot resonant cavity antenna, the multi-layer broadband Fabry-Perot resonant cavity antenna not only has wider gain bandwidth, but also has lower profile, so that the multi-layer broadband Fabry-Perot resonant cavity antenna can work in a lower frequency range and has better practicability;
drawings
FIG. 1 is a schematic overall structure diagram of an embodiment of the present invention;
FIG. 2 is a schematic of the layered structure of FIG. 1;
FIG. 3 is a schematic view of the low-k nylon frame of FIG. 1;
FIG. 4 is a schematic structural diagram of a reflective surface 1 on the first dielectric substrate in FIG. 2;
FIG. 5 is a schematic structural diagram of the lower reflective surface 3 of the first dielectric substrate in FIG. 2;
FIG. 6 is a schematic structural diagram of the reflective surface 4 on the second dielectric substrate in FIG. 2;
FIG. 7 is a schematic structural diagram of the lower reflective surface 6 of the second dielectric substrate in FIG. 2;
FIG. 8 is a schematic diagram of the parasitic patch structure of FIG. 2;
FIG. 9 is a schematic structural view of the metal floor and the gap on the metal floor in FIG. 2;
FIG. 10 is a schematic diagram of the microstrip feed line structure of FIG. 2;
FIG. 11 is a schematic view of the height between dielectric substrates in an embodiment of the present invention;
FIG. 12 is a graph of return loss characteristics in an embodiment of the present invention;
FIG. 13 is a graph of gain curves in an embodiment of the present invention;
fig. 14 is a radiation pattern in plane E and plane H in an embodiment of the present invention.
Detailed Description
The following describes in detail specific embodiments and effects of the present invention with reference to the drawings.
Referring to fig. 1, 2 and 3, the broadband miniaturized fabry-perot resonator antenna of the present embodiment includes, from top to bottom, a first dielectric substrate 2, a second dielectric substrate 5, a third dielectric substrate 7, a fourth dielectric substrate 10 and a low-dielectric-constant nylon frame 12, and the four dielectric substrates are fixed together by the low-dielectric-constant nylon frame 12. The upper surface and the lower surface of the first layer of dielectric substrate 2 are respectively a first upper reflecting surface 1 and a first lower reflecting surface 3; the upper surface and the lower surface of the second layer of dielectric substrate 5 are respectively a second upper reflecting surface 4 and a second lower reflecting surface 6; a parasitic patch 8 is arranged below the third layer of dielectric substrate 7; the upper surface and the lower surface of the fourth layer of dielectric substrate 10 are respectively a metal floor 9 and a microstrip feeder line 11.
The low-k nylon frame 12 comprises a square outer frame 121, a square inner frame 122, a support post 123, a support post 124, a support post 125, a support post 126, a support post 127, a support post 128 and a support post 129, wherein the first support post 123 is provided with two slots 1231 and 1232, and the second support post 124 is provided with two slots 1241 and 1242; the square outer frame 121 is divided into an upper layer 1211, a middle layer 1212 and a lower layer 1213, and is fixed by four support columns; the square inner frame 122 is fixed in the middle of the lower frame 1213 of the outer frame by means of the support bracket 127, the support bracket 128 and the support bracket 129.
The first layer of dielectric substrate 2, the upper reflecting surface 1 and the lower reflecting surface 3 form a first layer of reflecting structure, and the reflecting structure is fixed in an upper layer frame 1211 of an external frame in an embedding manner and is used for improving the gain of the Fabry-Perot resonant cavity antenna.
The second dielectric substrate 5, the upper reflective surface 4 and the lower reflective surface 6 thereof form a second layer reflective structure, and the reflective structure is fixed in the middle layer frame 1212 of the outer frame through the insertion notch 1231 and the notch 1241, so as to widen the gain bandwidth of the fabry-perot resonator antenna.
The third dielectric substrate 7 and the parasitic patch 8 on the lower surface thereof form a radiator structure, and the radiator structure is fixed in the square inner frame 122 in an embedded manner and is used for providing broadband and stable-gain electromagnetic radiation for the fabry-perot resonator antenna.
The fourth layer dielectric substrate 10, the metal floor 9 on the upper surface of the fourth layer dielectric substrate and the microstrip feeder 11 on the lower surface of the fourth layer dielectric substrate form a feed source structure, and the feed source structure is inserted into the lower layer 1213 of the outer frame through the notch 1232 and the notch 1242 on the supporting column and used for inhibiting surface wave excitation of the feed source antenna.
The first layer of dielectric substrate 2, the second layer of dielectric substrate 5 and the fourth layer of dielectric substrate 10 are all square dielectric substrates, the side lengths and the dielectric constants of the three are completely the same, the side length L is 60mm-80mm, and the dielectric constant epsilon is1Is 2.2; thickness H of first layer dielectric substrate 2 and second layer dielectric substrate 51Is 0.8mm-1.2mm, and the thickness H of the fourth layer dielectric substrate 102Is 1mm-1.5 mm; side length L of third layer dielectric substrate8Is 15mm-20mm, and has a thickness H30.8mm-1.2mm, a dielectric constant ε2Is 3.5; the side length L of the metal floor 6 is 60mm-80 mm. The example is not limited to L being 60mm, L8Is 18mm, H1Is 1mm and H3Is 0.8 mm.
Referring to fig. 4, the first upper reflective surface 1 is formed by periodic arrangement of regular hexagonal patches, the arrangement direction is perpendicular to the perpendicular bisector direction of three adjacent sides of a regular hexagon, and six identical patches surround any one of the regular hexagonal patches, so as to greatly enhance the coupling between the regular hexagonal patches, thereby enabling the regular hexagonal cells to obtain a positive phase gradient in a wide operating frequency range, the arrangement period P is 7mm to 9mm, the side length L1 of each regular hexagonal patch is 5mm to 7mm, in this example, but not limited thereto, P is 8mm, and L1 is 6 mm.
Referring to fig. 5, the first lower reflective surface 3 is formed by periodic arrangement of regular hexagonal ring-shaped cells, the arrangement direction is perpendicular to the midperpendicular direction of three adjacent sides of the regular hexagon, and the arrangement direction is used for enhancing the coupling between the regular hexagon cells by complementing the regular hexagon patches to improve the reflective performance of the first layer reflective structure, and the outer diameter side length of the regular hexagon ring is L36mm-8mm, and the length L of the inner diameter side of the regular hexagon ring2Is 4mm-6mm, and the example is not limited to L25mm, L3 7 mm.
Referring to fig. 6, the second upper reflective surface 4 is formed by periodic arrangement of regular hexagonal patches in the perpendicular direction of three adjacent sides of the regular hexagon, and the patch size is 1.2-1.5 times that of the first upper reflective surface 1, so as to greatly enhance the coupling between the regular hexagonal patches, thereby enabling the regular hexagonal cells to obtain a positive phase gradient in a wide operating frequency range, the arrangement period P thereof is 7mm-9mm, and the side length L of each regular hexagonal patch4Is 5mm to 7mm, and in this example, but not limited thereto, P is 8mm and L is4Is 6 mm.
Referring to fig. 7, the second lower reflecting surface 6 is formed by periodically arranging regular hexagonal cells, each of the regular hexagonal cells is formed by combining a regular hexagonal aperture and three-leg branches in the aperture, the arrangement direction is perpendicular to the perpendicular bisector direction of three adjacent sides of the regular hexagon, the regular hexagonal aperture is used for enhancing the coupling between the regular hexagonal cells and improving the reflection performance of the partial reflecting surface, the three-leg branches are used for extending the current flowing path so as to reduce the size of the regular hexagonal cells and further miniaturize the antenna, and the outer diameter L side length of the regular hexagonal aperture is L side length75mm-7mm, and the length L of the inner diameter side of the regular hexagon aperture54mm-6mm, side length L of three-leg branch65mm-7mm, width W of three-leg branch10.5mm to 0.7mm, in this example but not limited to 6mm for L2, 5mm for L3, 6mm for L4, and 0.6mm for W, the arrangement period P is the same as that of the partially reflective surface 1.
Referring to fig. 8, the parasitic patches 8 printed on the lower surface of the third dielectric substrate 7 have a spacing D4The two patches 81 and 82 are used as main radiating units in the fabry-perot resonator antenna, and the performance of the two patches directly affects the performance of the whole fabry-perot resonator antenna. The patches 81 and 82 are both square in shape with a side length L96mm-10mm, and the distance D from the parasitic patch 8 to the edge of the third dielectric substrate 70Is 4mm-7mm, and the example is not limited to L9Is 8mm, D0Is 5.5 mm.
Referring to fig. 9, the metal floor 9 printed on the upper surface of the fourth dielectric substrate 10 has two rectangular slits 91 and 92 etched in the middle thereof, the two slits being arranged in a row in a juxtaposed manner with a small distance D therebetween1The feed source antenna generates a new resonance point in the working frequency range, the occurrence of the resonance point can widen the working bandwidth of the Fabry-Perot resonant cavity antenna, and the broadband condition is provided for the Fabry-Perot resonant cavity antenna. The long side SL of the first rectangular slit 9116mm-10mm, short side SW1Is 0.5mm-3.5 mm; the long side SL of the second rectangular slit 9224mm-8mm, short side SW2Is 0.5mm-2 mm; the distance D between the rectangular gap 91 and one side of the metal floor 9230mm-40mm, the distance D between the rectangular gap 92 and the other side of the metal floor 93The distance D between the two rectangular gaps 91 and 92 is 32mm-36mm1Is 0.1mm-2 mm. This example is taken without limitation to SL1Is 7mm, SW11.5mm, SL2Is 6mm, SW2Is 1.5mm, D2Is 33mm, D3Is 34mm, D1Is 1 mm.
Referring to fig. 10, a graded microstrip feed line 11 printed on the lower surface of the fourth dielectric substrate 10 is perpendicular to two rectangular slots 91 and 92 on the metal floor, and the microstrip feed line mainly has two functions: the Fabry-Perot resonant cavity antenna is mainly used for transmitting radio-frequency signals and adjusting impedance matching of the Fabry-Perot resonant cavity antenna, and when the impedance of a feed unit of the antenna is matched, the radiation performance and the radiation efficiency of the antenna can be improved.
The microstrip feed line consists of an impedance microstrip line 111, an impedance microstrip line 112, an impedance microstrip line 113, an impedance microstrip line 114 and an impedance microstrip line 115, wherein the impedance microstrip line 111 and the impedance microstrip line 112 are arranged along the vertical direction and are connected end to end; the impedance microstrip line 112 and the impedance microstrip line 113 are vertically connected to each other; the impedance microstrip line 113 and the impedance microstrip line 114 are vertically connected to each other; the impedance microstrip line 114 and the impedance microstrip line 115 are arranged along the vertical direction, and are connected end to end. Wherein the width W of the impedance microstrip line 1112Is 1.8mm-2.2mm, and has a length L1011mm-14mm, width of the impedance microstrip line 112W32mm-4mm, length L1113mm-18mm, width W of the impedance microstrip line 1134Is 0.2mm-1mm, and has a length L122.5mm-4.5mm, the width W of the impedance microstrip line 1145Is 1mm-3mm, and has a length L132mm-5mm, width W of the impedance microstrip line 1146Is 0.5mm-1.5mm, and has a length L14Is 2mm-4 mm. This example is taken as but not limited to W2Is 1.9mm, L10Is 12mm, W3Is 3mm, L11Is 15mm, W4Is 0.3mm, L12Is 3.5mm, W5Is 2mm, L13Is 2mm, W6Is 1mm, L14Is 2.5 mm.
Referring to fig. 11, the height between the first dielectric substrate 2 and the second dielectric substrate 4 is H0The height between the second layer of dielectric substrate 4 and the fourth layer of dielectric substrate 10 is HcThe height between the third layer of dielectric substrate 7 and the fourth layer of dielectric substrate 10 is HaThese three heights have a significant effect on the performance of the antenna, where H0Has a significant influence on the gain bandwidth of the antenna, HcNot only the gain bandwidth of the antenna but also the matching of the antenna are significantly influenced, and the performance of the antenna can be optimized by reasonably adjusting the heights of the gain bandwidth and the matching of the antenna. H00.5mm-2.5mm, Hc10mm-30mm, Ha1.5mm-4.5 mm; this example is taken as but not limited to H0Is 1.5mm, HcIs 16mm, HaIs 2 mm.
The effect of the invention can be further explained by combining the simulation result:
1. simulation content:
simulation 1, a commercial simulation software HFSS — 15.0 is used to perform simulation calculation on the return loss parameter of the embodiment of the present invention, and the result is shown in fig. 12.
As can be seen from fig. 12, the working bandwidth of the feed structure in this embodiment is 9.4GHz:13GHz and the relative bandwidth thereof is 33%, and the working bandwidth of the fabry-perot resonator antenna is 9.2GHz:13GHz and the relative bandwidth thereof is 34.2%, based on the return loss being less than or equal to-10 dB.
Simulation 2, the gain parameter of the embodiment of the present invention was simulated and calculated by using commercial simulation software HFSS — 15.0, and the result is shown in fig. 13.
As can be seen from fig. 13, the gain of the feed source structure is stabilized near 7dBi and the highest gain is 8dBi, the highest gain of the fabry-perot resonator antenna is 14dBi, and the 3dB gain bandwidth of the fabry-perot resonator antenna is 9.1GHz:11.2GHz, and the relative bandwidth is 34.3%.
Simulation 3, simulation and test calculation are performed on the far-field radiation pattern of the embodiment of the present invention by using commercial simulation software HFSS — 15.0, and the result is shown in fig. 14, where:
FIG. 14(a) is the E-plane radiation pattern of the embodiment antenna at 9.5 GHz;
FIG. 14(b) is an H-plane radiation pattern of the antenna of the embodiment at 9.5 GHz;
FIG. 14(c) is the E-plane radiation pattern for the example antenna at 11 GHz;
FIG. 14(d) is an H-plane radiation pattern of the embodiment antenna at 11 GHz;
FIG. 14(E) is an E-plane radiation pattern for the embodiment antenna at 12.5 GHz;
fig. 14(f) shows the H-plane radiation pattern of the antenna of the embodiment at 12.5 GHz.
As can be seen from fig. 14(a), when the antenna according to the embodiment of the present invention operates at 9.5GHz, the maximum radiation direction of the radiation pattern of the E-plane is 0 degree, and the side lobe level is lower than-20 d, and the simulation result substantially matches the test result.
As can be seen from fig. 14(b), when the antenna according to the embodiment of the present invention operates at 9.5GHz, the maximum radiation direction of the radiation pattern of the H-plane is 0 degree, the level of the side lobe is lower than-17.5 dB, the symmetry of the pattern at the frequency point with respect to the 0 degree angle is relatively good, and in addition, the simulation result substantially matches the test result.
As can be seen from fig. 14(c), when the antenna according to the embodiment of the present invention operates at 11GHz, the maximum radiation direction of the radiation pattern of the E-plane is 0 degrees, and the sidelobe level is lower than-15 dB, although the symmetry of the antenna at the 0 degree angle is not good, the antenna has good high gain characteristics.
As can be seen from fig. 14(d), when the antenna according to the embodiment of the present invention operates at 11GHz, the maximum radiation direction of the radiation pattern of the H-plane is 0 degree, the side lobe level is lower than-17.5 dB, and the simulation result substantially matches the test result.
As can be seen from fig. 14(E), when the antenna of the embodiment of the present invention operates at 12.5GHz, the maximum radiation direction of the radiation pattern of the E-plane is 0 degrees, the level of the side lobe is lower than-12.5 dB, and the side lobe of the pattern after-35 ° starts to split.
As can be seen from fig. 14(f), when the antenna according to the embodiment of the present invention operates at 12.5GHz, the maximum radiation direction of the radiation pattern of the H-plane is 0 degree, and the side lobe level is lower than-16 dB, and the simulation result substantially matches the test result.
The simulation results show that when the double-layer partial reflection surface of the regular hexagon unit is used, the antenna is miniaturized, the working bandwidth and the 3dB gain bandwidth of the antenna are greatly widened, the gain in the maximum radiation direction is obviously improved, and the antenna has a good radiation directional diagram.

Claims (8)

1. A broadband miniaturization Fabry-Perot resonant cavity antenna comprises a first layer of dielectric substrate (2), a second layer of dielectric substrate (5), a third layer of dielectric substrate (7), a fourth layer of dielectric substrate (10) and a support piece (12), wherein the four substrates are fixed into a whole through the support piece (12) from top to bottom; the first layer of dielectric substrate (2) and the upper reflecting surface (1) and the lower reflecting surface (3) thereof form a first layer of reflecting structure; the second layer of dielectric substrate (5) and the upper reflecting surface (4) and the lower reflecting surface (6) thereof form a second layer of reflecting structure; the lower surface of the third layer of dielectric substrate (7) is provided with a parasitic patch (8), and the parasitic patch form a radiator structure; the upper surface of this fourth layer medium base plate (10) is metal floor (9), and the lower surface is gradual change type microstrip feeder (11), and the three forms feed structure, its characterized in that:
the upper and lower reflecting surfaces (1, 3) of the first layer of reflecting structure and the upper and lower reflecting surfaces (4, 6) of the second layer of reflecting structure both adopt regular hexagonal units which are periodically arranged, and the units are arranged along the perpendicular bisector direction of three adjacent sides of the regular hexagon;
the support piece (12) adopts a nylon frame with a low dielectric constant to form a narrow air band gap between the first layer of dielectric substrate (2) and the second layer of dielectric substrate (5), a Fabry-Perot resonant cavity is formed between the lower reflecting surface (6) of the second layer of reflecting structure and the metal floor (9), and an air band gap is formed between the parasitic patch (8) and the metal floor (9) to inhibit the excitation of the surface wave of the antenna;
the metal floor (9) is etched with two parallel rectangular gaps (91) and (92) to widen the impedance bandwidth of the antenna;
the regular hexagonal units of the upper reflecting surface (1) of the first layer of reflecting structure and the upper reflecting surface (4) of the second layer of reflecting structure are regular hexagonal patch structures;
the regular hexagonal units of the lower reflecting surface (3) of the first layer of reflecting structure are regular hexagonal annular structures;
the regular hexagonal units of the lower reflecting surface (6) of the second layer of reflecting structure are in a combined structure of a regular hexagonal ring and three-leg branches;
regular hexagon unit arrangement period of upper and lower reflecting surfaces (1, 3) of the first layer of reflecting structure and upper and lower reflecting surfaces (4, 6) of the second layer of reflecting structurePAll are 8mm-12 mm.
2. The antenna of claim 1, wherein:
the side length of the regular hexagon patch unit in the upper reflecting surface (1) of the first layer of reflecting structureL 1Is 3mm-5 mm;
the length of the outer diameter side of the regular hexagon ring in the lower reflecting surface (3) of the first layer of reflecting structureL 36mm-8mm, and the length of the inner diameter side of the regular hexagon ringL 2Is 4mm-6 mm;
the side length of the regular hexagon patch unit in the upper reflecting surface (4) of the second layer of reflecting structureL 45mm-7 mm;
the length of the outer diameter side of the regular hexagon ring in the lower reflecting surface (6) of the second layer of reflecting structureL 75mm-7mm, and the length of the inner diameter side of the regular hexagon ringL 54mm-6mm, side length of three-leg branchL 64mm-6mm, width of three-leg branchW 1Is 0.5mm-0.7 mm.
3. The antenna according to claim 1, characterized in that the support (12) comprises a square outer frame (121), a square inner frame (122), four support posts (123, 124, 125, 126) and three support brackets (127, 128, 129), and a first support post (123) is provided with two slots of a first slot (1231) and a second slot (1232), and a second support post (124) is provided with two slots of a first slot (1241) and a second slot (1242);
the square outer frame (121) is divided into an upper layer, a middle layer and a lower layer (1211, 1212 and 1213) and is fixed through four support columns (123, 124, 125 and 126);
the square inner frame (122) is fixed in the middle of a lower layer frame (1213) of the outer frame through three support frames (127, 128, 129);
the upper frame 1211 of the outer frame fixes the first layer dielectric substrate 2 in the inner part thereof in an embedding manner, the middle frame 1212 fixes the second layer dielectric substrate 5 in the inner part thereof in a manner that the first groove 1231 and the first notch 1241 are inserted, the lower frame 1213 fixes the fourth layer dielectric substrate 10 in the inner part thereof in a manner that the second groove 1232 and the second notch 1242 are inserted, and the square inner frame 122 fixes the third layer dielectric substrate 7 in the inner part thereof in an embedding manner.
4. The antenna of claim 3, wherein:
the upper and middle two layers (1211, 1212) of the square outer frame are separated by four support posts to form an air gap with a heightH 0Is 0.5mm-2.5 mm;
the upper and lower layers (1211, 1213) of the square outer frame are separated by four support columns to form a Fabry-Perot resonant cavity with a high heightH c Is 10mm-30 mm;
the square inner frame (122) is separated from the square outer frame lower layer (1213) by four support posts to form an air gap heightH a Is 1.5mm-4.5 mm.
5. The antenna of claim 1, wherein the first layer dielectric substrate (2), the second layer dielectric substrate (5) and the fourth layer dielectric substrate (10) are square dielectric substrates, and the side lengths and the dielectric constants of the three are completely the same, and the side lengths are the sameLHas a dielectric constant of 50-80 mm1Is 2.2; the thickness of the first layer of dielectric substrate (2) and the second layer of dielectric substrate (5)H 10.8mm-1.2mm, the thickness of the fourth layer of dielectric substrate (10)H 2Is 0.7mm-1 mm.
6. An antenna according to claim 1, characterized in that the third dielectric substrate (7) is rectangular in shape and longL 8Is 15mm-25mm wideW 1Is 8mm-12mm in thicknessH 30.8mm-1.2mm, a dielectric constant ε2Is 3.5; the lower surface of the third layer of dielectric substrate (7) is provided with two square parasitic patches which have the same size and are arranged in parallel, and the side length of each parasitic patchL 9Is 6mm-10mm, and the distance between the two patchesD 4Is 0.1mm-2 mm.
7. The antenna of claim 1, wherein: the distance between two rectangular gaps on the metal floor (9)D 1Is 0.1mm-2 mm; the long side SL of the first rectangular slit (91) of the strip16mm-10mm, short side SW1Is 0.5mm-3.5mm and is distant from one side of the metal floor (9)D 2Is 30mm-40 mm; the long side of the second rectangular slit (92)SL 24mm-8mm, short sideSW 2Is 0.5mm-2mm and is distant from the other side of the metal floor (9)D 3Is 32mm-36 mm.
8. An antenna according to claim 1, characterized in that the graded microstrip feed (11) consists of a first impedance microstrip line (111), a second impedance microstrip line (112), a third impedance microstrip line (113), a fourth impedance microstrip line (114) and a fifth impedance microstrip line (115);
the width of the first impedance microstrip line (111)W 2 Is 1.8mm-2.2mm in lengthL 10 Is 11mm-14mm in length,
the width of the second impedance microstrip line (112)W 3 2mm-4mm in lengthL 11Is 13mm-18mmmm，
The width of the third impedance microstrip line (113)W 4 Is 0.2mm-1mm in lengthL 12Is 2.5mm-4.5mmmm，
The width of the fourth impedance microstrip line (114)W 5 Is 1mm-3mm in lengthL 13Is 2mm-5mm，
The width of the fifth impedance microstrip line (115)W 6 Is 0.5mm-1.5mm in lengthL 14Is 2mm-4mm。
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