CN112511006A - Double-path resonance conversion circuit and control method - Google Patents

Double-path resonance conversion circuit and control method Download PDF

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Publication number
CN112511006A
CN112511006A CN202011204658.6A CN202011204658A CN112511006A CN 112511006 A CN112511006 A CN 112511006A CN 202011204658 A CN202011204658 A CN 202011204658A CN 112511006 A CN112511006 A CN 112511006A
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resistor
output
capacitor
control circuit
switch tube
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CN202011204658.6A
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CN112511006B (en
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宋祖梅
陈圣伦
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Hangzhou Ruiqi Electronic Technology Co ltd
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Hangzhou Letu Electronic Technology Co ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a two-way resonance conversion circuit and a control method thereof, and the two-way resonance conversion circuit comprises an input Vin, a capacitor C1, a capacitor C2, a resistor R1, a resistor R2, a switch tube S1, a switch tube S2, a diode D1, a diode D2, an inductor L1, a transformer T1, an output Vo1, an output Vo2, an output Io1 signal end, an Io2 signal end, a Vcr signal end and a driving control circuit. Has the advantages that: the invention utilizes charge control, automatically changes the upper and lower thresholds and the static offset of the charge control through an output feedback unit and a proportional offset adjusting unit to obtain the required frequency and duty ratio adjustment, and further obtains the final two paths of output voltage and current; the control method is simple to realize, and the system is more reliable and stable; compared with the scheme of multi-stage configuration of two DC/DC paths, the circuit is simple to implement and low in cost.

Description

Double-path resonance conversion circuit and control method
Technical Field
The invention relates to the field of resonant converter circuits, in particular to a double-path resonant converter circuit and a control method.
Background
Light-Emitting Diode (LED) products have the advantages of energy saving, environmental protection, long service life, high conversion rate, and the like, and are widely used in the field of illumination. The LED converter converts the input alternating current into direct current to supply to an LED load. The LED converters on the market mainly have two types, one is an LED driver outputting a constant current, and the other is an LED driver outputting a constant voltage.
At present, the design requirements for the LED driver are more and more strict, and the size of the driver needs to be reduced on the premise of ensuring the working efficiency of the LED driver. Therefore, in order to meet the requirement of miniaturization of the driver, a resonant converter is added in the circuit design of the LED driver, and the resonant soft switching technology is utilized to reduce the loss of the switching tube and improve the switching frequency of the switching tube. In some lighting occasions, the same driver is required to be used for driving two paths of loads simultaneously, in the prior art, two non-isolated direct current conversion circuits are added at the rear stage of a resonant converter to deal with the situation that the same driver is used for driving two paths of loads simultaneously, although two paths of outputs can be realized by the method, the circuit is complex, and the design cost is high.
An effective solution to the problems in the related art has not been proposed yet.
Disclosure of Invention
The present invention provides a two-way resonant converting circuit and a control method thereof, which are directed to the problems in the related art, so as to overcome the technical problems in the related art.
Therefore, the invention adopts the following specific technical scheme:
according to an aspect of the present invention, a two-way resonance converting circuit is provided, which includes an input Vin, a capacitor C1, a capacitor C2, a resistor R1, a resistor R2, a switching tube S1, a switching tube S2, a diode D1, a diode D2, an inductor L1, a transformer T1, an output Vo1, an output Vo2, an Io1 signal terminal, an Io2 signal terminal, a Vcr signal terminal, and a driving control circuit; the input Vin is connected in parallel with a capacitor C1, an anode of the capacitor C1 is connected with a first end of the switching tube S1, a cathode of the capacitor C1 is sequentially connected with a second end of the switching tube S2 and one end of the capacitor C2 and is grounded, a second end of the switching tube S1 is sequentially connected with a first end of the switching tube S2 and one end of the inductor L1, the other end of the inductor L1 is connected with a first input end of the transformer T1, a second input end of the transformer T1 is sequentially connected with the Vcr signal end and the other end of the capacitor C2, a first output end of the transformer T1 is connected with an anode of the diode D1, a cathode of the diode D1 is connected with an anode of the output Vo1, a cathode of the output Vo1 is sequentially connected with the Io1 signal end and one end of a resistor R1, and the other end of the resistor R1 is sequentially connected with a second output end of the transformer T1, A fourth output end of the transformer T1 and one end of the resistor R2 are connected to ground, the other end of the resistor R2 is sequentially connected to the Io2 signal end and the negative electrode of the output Vo2, the positive electrode of the output Vo2 is connected to the negative electrode of the diode D2, the positive electrode of the diode D2 is connected to the third output end of the transformer T1, a Vg _ S1 end of the driving control circuit is connected to the third end of the switching tube S1, a Vg _ S2 end of the driving control circuit is connected to the third end of the switching tube S2, a Vo1/Io1 end of the driving control circuit is connected to the Io1 signal end, and a Vo2/Io2 end of the driving control circuit is connected to the Io2 signal end.
Further, the capacitor C1 is a polar capacitor.
Further, the output Vo1 and the output Vo2 are polar capacitors, respectively.
Further, the drive control circuit comprises an output feedback unit, a charge control drive generation unit, a duty ratio static bias unit, a proportional bias regulation unit and a resistor R6; the output feedback unit is connected with the charge control drive generation unit, the charge control drive generation unit is sequentially connected with the duty ratio static bias unit and one end of a resistor R6, and the other end of the resistor R6 is connected with the proportional bias regulation unit.
Further, the output feedback unit comprises an operational amplifier OP1, a resistor R3, a resistor R4, a resistor R5 and a capacitor C3; the first input end of the operational amplifier OP1 is connected with a voltage reference, the second input end of the operational amplifier OP1 is sequentially connected with one end of the resistor R3, one end of the resistor R4 and one end of the resistor R5, the other end of the resistor R3 is connected with the Vo1/Io1 end of the driving control circuit, the other end of the resistor R4 is connected with the Vo2/Io2 end of the driving control circuit, the other end of the resistor R5 is connected with one end of the capacitor C3, and the other end of the capacitor C3 is sequentially connected with the output end of the operational amplifier OP1 and the charge control driving generation unit.
Further, the charge control drive generation unit comprises a first comparator, a second comparator, a first current source type AC-DC converter and an RS trigger; the third end of the first current source type AC-DC converter is connected with the output end of the operational amplifier OP1, the other end of the capacitor C3 and the second input end of the second comparator in sequence, a second terminal of the first current source type AC-DC converter is grounded, a first terminal of the first current source type AC-DC converter is connected with a first input terminal of the first comparator, the second input end of the first comparator is connected with the first input end of the second comparator, one end of the resistor R6 and the duty ratio static bias unit in sequence, the output end of the first comparator is connected with the first end of the RS trigger, the output end of the second comparator is connected with the second end of the RS trigger, the third end of the RS trigger is connected with the Vg _ S1 end of the drive control circuit, and the fourth end of the RS trigger is connected with the Vg _ S2 end of the drive control circuit.
Further, the duty cycle static bias unit comprises a second current source type AC-DC converter, a resistor R7, a capacitor C4 and a capacitor C5; the third end of the second current source type AC-DC converter is connected to the Vg _ S2 end of the driving control circuit, the second end of the second current source type AC-DC converter is connected to the Vg _ S1 end of the driving control circuit, the first end of the second current source type AC-DC converter is connected to one end of the resistor R7, the other end of the resistor R7 is sequentially connected to one end of the capacitor C4, one end of the capacitor C4, one end of the resistor R6, the first input end of the second comparator and the second input end of the first comparator, the other end of the capacitor C4 is connected to the Vcr signal end, and the other end of the capacitor C5 is grounded.
Further, the proportional bias adjusting unit comprises an operational amplifier OP2, a resistor R8, a resistor R9, a resistor R10, a capacitor C6 and an isolated DC-DC converter; a first input end of the operational amplifier OP2 is connected with a switch, a second input end of the operational amplifier OP2 is sequentially connected with a third end of the isolated DC-DC converter and one end of a resistor R8, the other end of the resistor R8 is connected with one end of a capacitor C6, the other end of the capacitor C6 is sequentially connected with an output end of the operational amplifier OP2 and the other end of a resistor R6, a second end of the isolated DC-DC converter is connected with one end of the resistor R9, the other end of the resistor R9 is connected with a Vo1/Io1 end of the driving control circuit, a first end of the isolated DC-DC converter is connected with one end of the resistor R10, and the other end of the resistor R10 is connected with a Vo2/Io3 end of the driving control circuit.
According to another aspect of the present invention, there is provided a method for controlling a two-way resonant conversion circuit to implement the control of the two-way resonant conversion circuit as claimed in any one of claims 1 to 8, the two-way resonant conversion circuit including a driving control circuit, wherein the driving control circuit includes an output feedback unit, a charge control driving generation unit, a duty static bias unit and a proportional bias adjustment unit, the method including the steps of:
when the switching tube S1 is switched on, the switching tube S2 is switched off, current passes through the switching tube S1, the inductor L1, the transformer T1, the capacitor C2 and the capacitor C1, and the secondary side of the transformer T1 supplies power to the output Vo1 through the diode D1;
when the switch tube S1 is turned off, the switch tube S2 is turned on, current passes through the switch tube S1, the inductor L1, the transformer T1 and the capacitor C2, and the secondary side of the transformer T1 supplies power to the output Vo2 through the diode D2;
the driving control circuit detects Vo1/Io1 and Vo2/Io2, correspondingly drives the switch tube S1 and the switch tube S2, and the switch tube S1 and the switch tube S2 are in complementary conduction;
the output feedback unit samples and feeds back multi-path average output voltage or current, and obtains a compensation signal Vcomp through an operational amplifier Op1 together with a set reference; when the output is below the set, Vcomp will increase; when the output is higher than set, Vcomp is reduced;
the charge control drive generation unit sets high-low comparison threshold voltages V _ th and V _ tl according to a feedback unit Vcomp signal, the higher the Vcomp is, the larger the V _ th is, the smaller the V _ tl is, the larger the difference between the V _ th and the Ttl is, and a resonant capacitor voltage division signal Vcap is sampled at the same time; resetting the RS trigger when Vcap is larger than V _ th, turning off the drive of the switch tube S1, and turning on the switch tube S2; when Vcap is lower than V _ tl, the RS trigger is set high, the driving of the switch tube S2 is turned off, and the switch tube S1 is turned on;
the duty ratio static bias unit takes the driving difference value of the upper and lower tubes as static direct current bias and can play a role in stabilizing a driving signal;
the proportion offset adjusting unit detects the proportion between the two output signals, compares the proportion with a set reference coefficient K, acts on a Vcap signal through negative feedback of the operational amplifier Op2, changes the static offset amount of the Vcap signal, can automatically adjust the duty ratios of the switch tube S1 and the switch tube S2 according to the actual effect, and finally enables the output amounts to meet the set proportion relation.
Furthermore, the output feedback unit is provided with an upper threshold and a lower threshold for charge control, which is equivalent to setting the total energy of the resonant cavity, and the proportional bias adjusting unit is equivalent to distributing energy according to a set proportion according to the load output quantity, and the proportional bias adjusting unit and the load output quantity respectively play their own roles and cooperate with each other to finally obtain the expected two-path output voltage and current values.
The invention has the beneficial effects that:
(1) the invention utilizes charge control, automatically changes the upper and lower thresholds and the static offset of the charge control through the output feedback unit and the proportional offset adjusting unit to obtain the required frequency and duty ratio adjustment, and further obtains the final two-way output voltage and current.
(2) The control method of the invention directly acts on the proportion distribution between the total energy and the two output quantities of the circuit, but not directly acts on the working frequency and the duty ratio of the regulating circuit, the realization is simple, and the system is more reliable and stable. Compared with the scheme of multi-stage configuration of two DC/DC paths, the circuit is simple to implement and low in cost.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings needed in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present invention, and it is obvious for those skilled in the art to obtain other drawings without creative efforts.
Fig. 1 is a circuit diagram of a two-way resonant conversion circuit and a control method according to an embodiment of the invention;
FIG. 2 is a schematic diagram of a drive control circuit according to an embodiment of the present invention;
fig. 3 shows the actual operating waveforms of a two-way resonant conversion circuit and a control method according to an embodiment of the invention.
Detailed Description
For further explanation of the various embodiments, the drawings which form a part of the disclosure and which are incorporated in and constitute a part of this specification, illustrate embodiments and, together with the description, serve to explain the principles of operation of the embodiments, and to enable others of ordinary skill in the art to understand the various embodiments and advantages of the invention, and, by reference to these figures, reference is made to the accompanying drawings, which are not to scale and wherein like reference numerals generally refer to like elements.
According to the embodiment of the invention, a two-way resonance conversion circuit and a control method are provided.
Referring now to the drawings and the detailed description, as shown in fig. 1-3, a two-way resonant converting circuit according to an embodiment of the present invention includes an input Vin, a capacitor C1, a capacitor C2, a resistor R1, a resistor R2, a switch tube S1, a switch tube S2, a diode D1, a diode D2, an inductor L1, a transformer T1, an output Vo1, an output Vo2, an Io1 signal terminal, an Io2 signal terminal, a Vcr signal terminal, and a driving control circuit; the input Vin is connected in parallel with a capacitor C1, an anode of the capacitor C1 is connected with a first end of the switching tube S1, a cathode of the capacitor C1 is sequentially connected with a second end of the switching tube S2 and one end of the capacitor C2 and is grounded, a second end of the switching tube S1 is sequentially connected with a first end of the switching tube S2 and one end of the inductor L1, the other end of the inductor L1 is connected with a first input end of the transformer T1, a second input end of the transformer T1 is sequentially connected with the Vcr signal end and the other end of the capacitor C2, a first output end of the transformer T1 is connected with an anode of the diode D1, a cathode of the diode D1 is connected with an anode of the output Vo1, a cathode of the output Vo1 is sequentially connected with the Io1 signal end and one end of a resistor R1, and the other end of the resistor R1 is sequentially connected with a second output end of the transformer T1, A fourth output end of the transformer T1 and one end of the resistor R2 are connected to ground, the other end of the resistor R2 is sequentially connected to the Io2 signal end and the negative electrode of the output Vo2, the positive electrode of the output Vo2 is connected to the negative electrode of the diode D2, the positive electrode of the diode D2 is connected to the third output end of the transformer T1, a Vg _ S1 end of the driving control circuit is connected to the third end of the switching tube S1, a Vg _ S2 end of the driving control circuit is connected to the third end of the switching tube S2, a Vo1/Io1 end of the driving control circuit is connected to the Io1 signal end, and a Vo2/Io2 end of the driving control circuit is connected to the Io2 signal end.
In one embodiment, the capacitor C1 is a polar capacitor.
In one embodiment, the output Vo1 and the output Vo2 are each polar capacitances.
In one embodiment, the drive control circuit comprises an output feedback unit, a charge control drive generation unit, a duty ratio static bias unit, a proportional bias regulation unit and a resistor R6; the output feedback unit is connected with the charge control drive generation unit, the charge control drive generation unit is sequentially connected with the duty ratio static bias unit and one end of a resistor R6, and the other end of the resistor R6 is connected with the proportional bias regulation unit.
In one embodiment, the output feedback unit comprises an OP-amp OP1, a resistor R3, a resistor R4, a resistor R5 and a capacitor C3; the first input end of the operational amplifier OP1 is connected with a voltage reference, the second input end of the operational amplifier OP1 is sequentially connected with one end of the resistor R3, one end of the resistor R4 and one end of the resistor R5, the other end of the resistor R3 is connected with the Vo1/Io1 end of the driving control circuit, the other end of the resistor R4 is connected with the Vo2/Io2 end of the driving control circuit, the other end of the resistor R5 is connected with one end of the capacitor C3, and the other end of the capacitor C3 is sequentially connected with the output end of the operational amplifier OP1 and the charge control driving generation unit.
In one embodiment, the charge control drive generation unit includes a first comparator, a second comparator, a first current source type AC-DC converter, and an RS flip-flop; the third end of the first current source type AC-DC converter is connected with the output end of the operational amplifier OP1, the other end of the capacitor C3 and the second input end of the second comparator in sequence, a second terminal of the first current source type AC-DC converter is grounded, a first terminal of the first current source type AC-DC converter is connected with a first input terminal of the first comparator, the second input end of the first comparator is connected with the first input end of the second comparator, one end of the resistor R6 and the duty ratio static bias unit in sequence, the output end of the first comparator is connected with the first end of the RS trigger, the output end of the second comparator is connected with the second end of the RS trigger, the third end of the RS trigger is connected with the Vg _ S1 end of the drive control circuit, and the fourth end of the RS trigger is connected with the Vg _ S2 end of the drive control circuit.
In one embodiment, the duty cycle static bias unit comprises a second current source type AC-DC converter, a resistor R7, a capacitor C4 and a capacitor C5; the third end of the second current source type AC-DC converter is connected to the Vg _ S2 end of the driving control circuit, the second end of the second current source type AC-DC converter is connected to the Vg _ S1 end of the driving control circuit, the first end of the second current source type AC-DC converter is connected to one end of the resistor R7, the other end of the resistor R7 is sequentially connected to one end of the capacitor C4, one end of the capacitor C4, one end of the resistor R6, the first input end of the second comparator and the second input end of the first comparator, the other end of the capacitor C4 is connected to the Vcr signal end, and the other end of the capacitor C5 is grounded.
In one embodiment, the proportional bias adjusting unit comprises an operational amplifier OP2, a resistor R8, a resistor R9, a resistor R10, a capacitor C6 and an isolated DC-DC converter; a first input end of the operational amplifier OP2 is connected with a switch, a second input end of the operational amplifier OP2 is sequentially connected with a third end of the isolated DC-DC converter and one end of a resistor R8, the other end of the resistor R8 is connected with one end of a capacitor C6, the other end of the capacitor C6 is sequentially connected with an output end of the operational amplifier OP2 and the other end of a resistor R6, a second end of the isolated DC-DC converter is connected with one end of the resistor R9, the other end of the resistor R9 is connected with a Vo1/Io1 end of the driving control circuit, a first end of the isolated DC-DC converter is connected with one end of the resistor R10, and the other end of the resistor R10 is connected with a Vo2/Io3 end of the driving control circuit.
According to an embodiment of the present invention, there is also provided a method for controlling a two-way resonant conversion circuit, where the two-way resonant conversion circuit includes a driving control circuit, the driving control circuit includes an output feedback unit, a charge control driving generation unit, a duty ratio static bias unit, and a proportional bias adjustment unit, and the method includes the following steps:
when the switching tube S1 is switched on, the switching tube S2 is switched off, current passes through the switching tube S1, the inductor L1, the transformer T1, the capacitor C2 and the capacitor C1, and the secondary side of the transformer T1 supplies power to the output Vo1 through the diode D1;
when the switch tube S1 is turned off, the switch tube S2 is turned on, current passes through the switch tube S1, the inductor L1, the transformer T1 and the capacitor C2, and the secondary side of the transformer T1 supplies power to the output Vo2 through the diode D2;
the driving control circuit detects Vo1/Io1 and Vo2/Io2, correspondingly drives the switch tube S1 and the switch tube S2, and the switch tube S1 and the switch tube S2 are in complementary conduction;
the output feedback unit samples and feeds back multi-path average output voltage or current, and obtains a compensation signal Vcomp through an operational amplifier Op1 together with a set reference; when the output is below the set, Vcomp will increase; when the output is higher than set, Vcomp is reduced;
the charge control drive generation unit sets high-low comparison threshold voltages V _ th and V _ tl according to a feedback unit Vcomp signal, the higher the Vcomp is, the larger the V _ th is, the smaller the V _ tl is, the larger the difference between the V _ th and the Ttl is, and a resonant capacitor voltage division signal Vcap is sampled at the same time; resetting the RS trigger when Vcap is larger than V _ th, turning off the drive of the switch tube S1, and turning on the switch tube S2; when Vcap is lower than V _ tl, the RS trigger is set high, the driving of the switch tube S2 is turned off, and the switch tube S1 is turned on;
the duty ratio static bias unit is mainly used for stabilizing the duty ratio. Because Vcap is an AC signal, it does not contain the DC component of the resonant tank. Without a static bias, the circuit is prone to unstable operation. The invention uses the driving difference value of the upper and lower tubes as the static DC bias, which can stabilize the driving signal;
the proportion offset adjusting unit detects the proportion between the two output signals, compares the proportion with a set reference coefficient K, acts on a Vcap signal through negative feedback of the operational amplifier Op2, changes the static offset amount of the Vcap signal, can automatically adjust the duty ratios of the switch tube S1 and the switch tube S2 according to the actual effect, and finally enables the output amounts to meet the set proportion relation.
In one embodiment, the output feedback unit sets upper and lower thresholds for charge control, which is equivalent to setting total energy of the resonant cavity, and the proportional bias adjusting unit is equivalent to distributing energy according to a set proportion according to the load output quantity, and the proportional bias adjusting unit and the load output quantity respectively play their own roles and cooperate with each other to finally obtain the expected two-way output voltage and current values.
In summary, the present invention utilizes charge control to automatically change the upper and lower thresholds and the static offset of charge control through the output feedback unit and the proportional bias adjustment unit to obtain the required frequency and duty ratio adjustment, and further obtain the final two-way output voltage and current. The control method of the invention directly acts on the proportion distribution between the total energy and the two output quantities of the circuit, but not directly acts on the working frequency and the duty ratio of the regulating circuit, the realization is simple, and the system is more reliable and stable. Compared with the scheme of multi-stage configuration of two DC/DC paths, the circuit is simple to implement and low in cost.
The above description is only for the purpose of illustrating the preferred embodiments of the present invention and is not to be construed as limiting the invention, and any modifications, equivalents, improvements and the like that fall within the spirit and principle of the present invention are intended to be included therein.

Claims (10)

1. A double-path resonance conversion circuit is characterized by comprising an input Vin, a capacitor C1, a capacitor C2, a resistor R1, a resistor R2, a switch tube S1, a switch tube S2, a diode D1, a diode D2, an inductor L1, a transformer T1, an output Vo1, an output Vo2, an Io1 signal end, an Io2 signal end, a Vcr signal end and a driving control circuit;
the input Vin is connected in parallel with a capacitor C1, an anode of the capacitor C1 is connected to a first end of the switching tube S1, a cathode of the capacitor C1 is sequentially connected to a second end of the switching tube S2 and one end of the capacitor C2 and grounded, a second end of the switching tube S1 is sequentially connected to a first end of the switching tube S2 and one end of the inductor L1, the other end of the inductor L1 is connected to a first input end of the transformer T1, a second input end of the transformer T1 is sequentially connected to the Vcr signal end and the other end of the capacitor C2, a first output end of the transformer T1 is connected to an anode of the diode D1, a cathode of the diode D1 is connected to an anode of the output Vo1, a cathode of the output Vo1 is sequentially connected to the Io1 signal end and one end of a resistor R1, and the other end of the resistor R1 is sequentially connected to a second output end of the transformer T1, A fourth output end of the transformer T1 and one end of the resistor R2 are connected to ground, the other end of the resistor R2 is sequentially connected to the Io2 signal end and the negative electrode of the output Vo2, the positive electrode of the output Vo2 is connected to the negative electrode of the diode D2, the positive electrode of the diode D2 is connected to the third output end of the transformer T1, a Vg _ S1 end of the driving control circuit is connected to the third end of the switching tube S1, a Vg _ S2 end of the driving control circuit is connected to the third end of the switching tube S2, a Vo1/Io1 end of the driving control circuit is connected to the Io1 signal end, and a Vo2/Io2 end of the driving control circuit is connected to the Io2 signal end.
2. A two-way resonant conversion circuit as in claim 1, wherein said capacitor C1 is a polar capacitor.
3. A two-way resonant conversion circuit as in claim 1, wherein said output Vo1 and said output Vo2 are both polar capacitors.
4. The two-way resonant conversion circuit according to claim 1, wherein the driving control circuit comprises an output feedback unit, a charge control driving generation unit, a duty ratio static bias unit, a proportional bias regulation unit and a resistor R6;
the output feedback unit is connected with the charge control drive generation unit, the charge control drive generation unit is sequentially connected with the duty ratio static bias unit and one end of a resistor R6, and the other end of the resistor R6 is connected with the proportional bias regulation unit.
5. The two-way resonant conversion circuit of claim 4, wherein the output feedback unit comprises an OP-amp OP1, a resistor R3, a resistor R4, a resistor R5 and a capacitor C3;
the first input end of the operational amplifier OP1 is connected with a voltage reference, the second input end of the operational amplifier OP1 is sequentially connected with one end of the resistor R3, one end of the resistor R4 and one end of the resistor R5, the other end of the resistor R3 is connected with the Vo1/Io1 end of the driving control circuit, the other end of the resistor R4 is connected with the Vo2/Io2 end of the driving control circuit, the other end of the resistor R5 is connected with one end of the capacitor C3, and the other end of the capacitor C3 is sequentially connected with the output end of the operational amplifier OP1 and the charge control driving generation unit.
6. A two-way resonant converting circuit according to claim 5, wherein said charge control drive generating unit comprises a first comparator, a second comparator, a first current source type AC-DC converter and an RS flip-flop;
wherein, the third terminal of the first current source type AC-DC converter is connected with the output terminal of the operational amplifier OP1, the other terminal of the capacitor C3 and the second input terminal of the second comparator in turn, a second terminal of the first current source type AC-DC converter is grounded, a first terminal of the first current source type AC-DC converter is connected with a first input terminal of the first comparator, the second input end of the first comparator is connected with the first input end of the second comparator, one end of the resistor R6 and the duty ratio static bias unit in sequence, the output end of the first comparator is connected with the first end of the RS trigger, the output end of the second comparator is connected with the second end of the RS trigger, the third end of the RS trigger is connected with the Vg _ S1 end of the drive control circuit, and the fourth end of the RS trigger is connected with the Vg _ S2 end of the drive control circuit.
7. The two-way resonant conversion circuit according to claim 6, wherein the duty cycle static bias unit comprises a second current source type AC-DC converter, a resistor R7, a capacitor C4 and a capacitor C5;
the third end of the second current source type AC-DC converter is connected to the Vg _ S2 end of the driving control circuit, the second end of the second current source type AC-DC converter is connected to the Vg _ S1 end of the driving control circuit, the first end of the second current source type AC-DC converter is connected to one end of the resistor R7, the other end of the resistor R7 is sequentially connected to one end of the capacitor C4, one end of the capacitor C4, one end of the resistor R6, the first input end of the second comparator and the second input end of the first comparator, the other end of the capacitor C4 is connected to the Vcr signal end, and the other end of the capacitor C5 is grounded.
8. The two-way resonant conversion circuit of claim 7, wherein the proportional bias adjustment unit comprises an operational amplifier OP2, a resistor R8, a resistor R9, a resistor R10, a capacitor C6 and an isolated DC-DC converter;
a first input end of the operational amplifier OP2 is connected to a switch, a second input end of the operational amplifier OP2 is sequentially connected to a third end of the isolated DC-DC converter and one end of a resistor R8, the other end of the resistor R8 is connected to one end of a capacitor C6, the other end of the capacitor C6 is sequentially connected to an output end of the operational amplifier OP2 and the other end of the resistor R6, a second end of the isolated DC-DC converter is connected to one end of the resistor R9, the other end of the resistor R9 is connected to a Vo1/Io1 end of the driving control circuit, a first end of the isolated DC-DC converter is connected to one end of the resistor R10, and the other end of the resistor R10 is connected to a Vo2/Io3 end of the driving control circuit.
9. A control method of a two-way resonant conversion circuit, so as to realize the control of the two-way resonant conversion circuit according to any one of claims 1 to 8, wherein the two-way resonant conversion circuit comprises a driving control circuit, and the driving control circuit comprises an output feedback unit, a charge control driving generation unit, a duty ratio static bias unit and a proportional bias regulation unit, and the method comprises the following steps:
when the switching tube S1 is switched on, the switching tube S2 is switched off, current passes through the switching tube S1, the inductor L1, the transformer T1, the capacitor C2 and the capacitor C1, and the secondary side of the transformer T1 supplies power to the output Vo1 through the diode D1;
when the switch tube S1 is turned off, the switch tube S2 is turned on, current passes through the switch tube S1, the inductor L1, the transformer T1 and the capacitor C2, and the secondary side of the transformer T1 supplies power to the output Vo2 through the diode D2;
the driving control circuit detects Vo1/Io1 and Vo2/Io2, correspondingly drives the switch tube S1 and the switch tube S2, and the switch tube S1 and the switch tube S2 are in complementary conduction;
the output feedback unit samples and feeds back multi-path average output voltage or current, and obtains a compensation signal Vcomp through an operational amplifier Op1 together with a set reference; when the output is below the set, Vcomp will increase; when the output is higher than set, Vcomp is reduced;
the charge control drive generation unit sets high-low comparison threshold voltages V _ th and V _ tl according to a feedback unit Vcomp signal, the higher the Vcomp is, the larger the V _ th is, the smaller the V _ tl is, the larger the difference between the V _ th and the Ttl is, and a resonant capacitor voltage division signal Vcap is sampled at the same time; resetting the RS trigger when Vcap is larger than V _ th, turning off the drive of the switch tube S1, and turning on the switch tube S2; when Vcap is lower than V _ tl, the RS trigger is set high, the driving of the switch tube S2 is turned off, and the switch tube S1 is turned on;
the duty ratio static bias unit takes the driving difference value of the upper and lower tubes as static direct current bias and can play a role in stabilizing a driving signal;
the proportion offset adjusting unit detects the proportion between the two output signals, compares the proportion with a set reference coefficient K, acts on a Vcap signal through negative feedback of the operational amplifier Op2, changes the static offset amount of the Vcap signal, can automatically adjust the duty ratios of the switch tube S1 and the switch tube S2 according to the actual effect, and finally enables the output amounts to meet the set proportion relation.
10. The method as claimed in claim 9, wherein the output feedback unit sets the upper and lower thresholds of charge control, which is equivalent to setting the total energy of the resonant cavity, and the proportional bias adjustment unit is equivalent to distributing energy according to the load output quantity and the set proportion, and the two units respectively perform their own functions and cooperate with each other to finally obtain the desired two-way output voltage and current values.
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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106304492A (en) * 2016-08-30 2017-01-04 康佳集团股份有限公司 A kind of two-way constant-current circuit and supply unit
CN110086353A (en) * 2018-01-25 2019-08-02 恩智浦有限公司 The device and method of the linearisation of control input for dual output resonance converter
CN110798938A (en) * 2019-11-07 2020-02-14 杭州优特电源有限公司 LED driver
CN111162660A (en) * 2020-01-08 2020-05-15 毛昭祺 Multi-channel resonance conversion circuit and multi-channel output control method based on multi-channel resonance conversion circuit

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106304492A (en) * 2016-08-30 2017-01-04 康佳集团股份有限公司 A kind of two-way constant-current circuit and supply unit
CN110086353A (en) * 2018-01-25 2019-08-02 恩智浦有限公司 The device and method of the linearisation of control input for dual output resonance converter
CN110798938A (en) * 2019-11-07 2020-02-14 杭州优特电源有限公司 LED driver
CN111162660A (en) * 2020-01-08 2020-05-15 毛昭祺 Multi-channel resonance conversion circuit and multi-channel output control method based on multi-channel resonance conversion circuit

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