CN112152525A - Unbalanced voltage compensation device and method for brushless doubly-fed induction generator - Google Patents

Unbalanced voltage compensation device and method for brushless doubly-fed induction generator Download PDF

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CN112152525A
CN112152525A CN202011066401.9A CN202011066401A CN112152525A CN 112152525 A CN112152525 A CN 112152525A CN 202011066401 A CN202011066401 A CN 202011066401A CN 112152525 A CN112152525 A CN 112152525A
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current
voltage
value
axis component
feedback value
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CN112152525B (en
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刘毅
张杨生
徐伟
林怡凡
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Huazhong University of Science and Technology
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Huazhong University of Science and Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P9/00—Arrangements for controlling electric generators for the purpose of obtaining a desired output
    • H02P9/007—Control circuits for doubly fed generators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/0003—Control strategies in general, e.g. linear type, e.g. P, PI, PID, using robust control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P9/00—Arrangements for controlling electric generators for the purpose of obtaining a desired output
    • H02P9/48—Arrangements for obtaining a constant output value at varying speed of the generator, e.g. on vehicle

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  • Control Of Eletrric Generators (AREA)

Abstract

The invention discloses an unbalanced voltage compensation device and method for a brushless doubly-fed induction generator, belonging to the technical field of brushless doubly-fed induction generator control, and comprising a PW voltage controller, a CW conversion angle generator, a PW voltage amplitude calculator, a PW reactive power compensator and a CW current regulator; the PW reactive power compensator comprises a PW current converter, a multiplier, a high-pass filter and a resonance controller; the multiplier is based on the current feedback value i of the d-axis component of the PW currentpd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n) calculating the current calculated value Q of the total reactive power of the brushless doubly-fed induction generatorp(n); high pass filter slave Qp(n) obtaining the current calculated value of the PW double-frequency reactive power
Figure DDA0002713875920000011
A resonance controller based on
Figure DDA0002713875920000012
Calculating q-axis compensation quantity of CW voltage
Figure DDA0002713875920000013
Q-axis compensation quantity of CW voltage output by PW reactive power compensator in the invention
Figure DDA0002713875920000014
The reactive power of the double frequency of the PW is eliminated, so that the frequency and the amplitude of the PW voltage are constant.

Description

Unbalanced voltage compensation device and method for brushless doubly-fed induction generator
Technical Field
The invention belongs to the technical field of brushless doubly-fed induction generator control, and particularly relates to an unbalanced voltage compensation device and method of a brushless doubly-fed induction generator.
Background
The brushless double-fed induction generator is a novel alternating current induction motor, comprises two sets of stator windings with different pole pairs, which are respectively called as a power winding and a control winding, and the stator windings are not directly coupled; the rotor of the brushless doubly-fed induction generator is specially designed, so that the rotating magnetic fields with different pole pairs generated by the two sets of stator windings can indirectly interact with each other, and the interaction of the rotating magnetic fields can be controlled to realize energy transfer. The motor can operate in a plurality of working modes, including an induction mode, a cascade mode and a double-fed mode.
The brushless doubly-fed induction generator can realize variable-speed constant-frequency power generation, simultaneously cancels an electric brush and a slip ring, has the advantages of simple and reliable structure, and has remarkable application advantages in the fields of wind power generation, hydroelectric generation, ship shaft power generation, electric vehicles and the like. Usually, the wind power generator is connected to the grid during operation, and the control objective of the wind power system is to regulate the active power and the reactive power. However, the independent power generation system of the brushless doubly-fed induction generator is not connected with the power grid, and the output voltage of the brushless doubly-fed induction motor needs to be directly controlled, so that the amplitude and the frequency of the output voltage of the brushless doubly-fed induction motor are kept constant when the rotating speed or the power load of the generator changes.
The control objective of the independent power generation system of the brushless doubly-fed induction generator is to keep the amplitude and frequency of the generator output voltage constant. However, unbalanced three-phase current occurs in a PW (powerwind, hereinafter referred to as PW) of the brushless doubly-fed induction generator due to the unbalanced load, and the unbalanced three-phase current generates different voltage drops on each phase internal impedance of the output voltage, so that the output voltage of the brushless doubly-fed induction generator is unbalanced, and thus, under a conventional control method, a control target that the amplitude and the frequency of the output voltage of the independent power generation system of the brushless doubly-fed induction generator are kept constant is difficult to achieve.
Disclosure of Invention
Aiming at the defects of the prior art, the invention aims to provide an unbalanced voltage compensation device and method for a brushless doubly-fed induction generator, and aims to solve the problem that the PW voltage amplitude and frequency cannot be ensured to be constant and further constant-voltage and constant-frequency power generation cannot be realized under the condition that an unbalanced load exists in an independent power generation system of the conventional brushless induction generator.
In order to achieve the above object, the present invention provides an unbalanced voltage compensation device for a brushless doubly-fed induction generator, which is applied to an independent power generation system of a brushless doubly-fed induction generator with reactive power, and comprises a PW voltage controller, a CW (Control Winding, hereinafter referred to as CW) conversion angle generator, a CW current regulator, a PW voltage amplitude calculator and a PW reactive power compensator;
the PW voltage controller is based on the given value of the PW voltage amplitude
Figure BDA0002713875900000021
Current feedback value U of PW voltage amplitudep(n) outputting the current set value of the d-axis component of the CW current
Figure BDA0002713875900000022
The amplitude closed-loop control is used for realizing the PW voltage;
CW conversion angle generator based on current rotor position theta of brushless doubly-fed induction generatorr(n) outputting the current set value of the CW phase together with the set value of the PW frequency
Figure BDA0002713875900000023
Realizing frequency closed-loop control of PW voltage;
CW current regulator reception
Figure BDA0002713875900000024
And the current compensation value of the q-axis component of the CW voltage
Figure BDA0002713875900000025
Outputting the current value u of the CW excitation voltagec_abc(n) to the control winding; realizing closed-loop control of d-axis component and q-axis component of CW current;
the PW voltage amplitude calculator receives a current value u of the PW voltagep_abc(n) given value of PW frequency
Figure BDA0002713875900000026
Calculating U through coordinate transformationp(n)；
The PW reactive power compensator receives the current feedback value i of the PW currentp_abc(n)、upq(n), given value of PW phase
Figure BDA0002713875900000027
Computing
Figure BDA0002713875900000028
Realizing closed-loop control of PW double-frequency reactive power caused by unbalanced load;
the PW reactive power compensator comprises a PW current converter, a multiplier, a high-pass filter and a resonance controller;
the PW current converter converts the current feedback value i of the PW current in an abc coordinate systemp_abc(n) current feedback value i converted into PW current d-axis component in dq rotation coordinate systempd(n)；
The multiplier is used for calculating the current calculation value Q of the total reactive power of the brushless doubly-fed induction generatorp(n); the calculation formula is as follows:
Figure BDA0002713875900000031
wherein Q isp(n) is a current calculated value of the total reactive power of the brushless doubly-fed induction generator, and comprises two parts corresponding to a balanced load and an unbalanced load; u. ofpq(n) is the current feedback value of the q-axis component of the PW voltage; i.e. ipd(n) is the current feedback value of the d-axis component of the PW current; qp(n) inputting to a high pass filter;
the high-pass filter is used for acquiring a current calculated value of PW double-frequency reactive power caused by unbalanced load in the brushless doubly-fed induction generator
Figure BDA0002713875900000032
The resonance controller is used for calculating the current compensation value of the q-axis component of the CW voltage
Figure BDA0002713875900000033
Figure BDA0002713875900000034
Wherein the content of the first and second substances,
Figure BDA0002713875900000035
a current compensation value of q-axis component of CW voltage;
Figure BDA0002713875900000036
the current given value of the reactive power to be compensated is obtained; krA resonant amplifier being a resonant controller; omegac4Is the cut-off angular frequency of the resonant controller; omega0Represents the resonant frequency;
Figure BDA0002713875900000037
calculating the current given value of the reactive power to be compensated for the n-1 st time;
Figure BDA0002713875900000038
respectively representing compensation values of q-axis components of the CW voltage obtained by the n-1 st calculation and the n-2 nd calculation;
Figure BDA0002713875900000039
input to the fourth adder.
Preferably, the PW voltage controller includes a first adder and a first PI controller;
the first adder calculates the given value of the PW voltage amplitude
Figure BDA00027138759000000310
Current feedback value U of PW voltage amplitudep(n) the difference between (n); n is the current operation times;
the first PI controller obtains the current given value of the d-axis component of the CW current
Figure BDA00027138759000000311
The CW transformation angle generator comprises a differentiator, a first low-pass filter, a proportional amplifier, a fifth adder and a first integrator;
the differentiator performs differentiation processing on the current rotor position of the brushless doubly-fed induction generator to obtain the current rotation speed omega containing noise of the brushless doubly-fed induction generatorr′(n)；
The first low-pass filter filters noise to obtain the current rotating speed omega of the brushless doubly-fed induction generatorr(n)；
Proportional amplifier pair omegar(n) amplifying the sum of the PW pole pair number and the CW pole pair number;
the fifth adder is used for subtracting the PW frequency given value from the proportional amplifier output to obtain the current given value of the CW frequency
Figure BDA0002713875900000041
The first integrator calculates the current given value of the CW phase according to the sampling period and the current given value of the CW frequency calculated each time
Figure BDA0002713875900000042
Preferably, the CW current regulator includes a second adder, a third adder, a fourth adder, a second PI controller, a third PI controller, a CW voltage converter, a CW current converter, a PWM signal generator, and a control winding converter;
the second adder calculates the current given value of the d-axis component of the CW current
Figure BDA0002713875900000043
Current feedback value i of d-axis component of CW currentcd(n) the difference between (n);
the second PI controller is used for calculating the current given value of the d-axis component of the CW voltage
Figure BDA0002713875900000044
The third adder calculates a given value of q-axis component of CW current
Figure BDA0002713875900000045
Current feedback value i of q-axis component of CW currentcq(n) the difference between (n);
the third PI controller is used for calculating the current given value u 'of the CW voltage q-axis component without considering the voltage compensation'cq(n)；
The fourth adder calculates the current given value u 'of the CW voltage q-axis component without considering the voltage compensation'cq(n) current compensation value with q-axis component of CW voltage
Figure BDA0002713875900000046
Summing;
the CW voltage converter converts the current set value of the q-axis component of the CW voltage in dq rotation coordinate system
Figure BDA0002713875900000047
And the current set point of the q-axis component of the CW voltage
Figure BDA0002713875900000048
Converting to a current set value of CW voltage under an abc coordinate system
Figure BDA0002713875900000049
The CW current converter converts the current feedback value i of the CW current in an abc coordinate systemc_abc(n) (i.e.: i)ca(n)、icb(n) and icc(n)) is transformed into the current feedback value i of the d-axis component of the CW current in the dq rotation coordinate systemcd(n) and the present feedback value i of the q-axis component of the CW currentcq(n)；
PWM signal generator according to CW voltage current set value under abc coordinate system
Figure BDA0002713875900000051
Generating a PWM signal;
controlling the winding side converter to invert the direct current into the alternating current according to the PWM signal and outputting the current value u of the three-phase excitation voltage required by CWc_abc(n) to a brushless doubly fed induction generator.
Preferably, the PW voltage amplitude calculator includes a second integrator, a PW voltage converter, an amplitude calculator, and a second low-pass filter;
the second integrator is used for giving a given value of PW frequency
Figure BDA0002713875900000052
Integral processing is carried out to obtain a given value of PW phase
Figure BDA0002713875900000053
PW voltage converter receiver
Figure BDA0002713875900000054
The current feedback value u of the PW voltage under the abc coordinate systemp_abc(n) converting the current feedback value u into the d-axis component of the PW voltage in the dq rotation coordinate systempd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n)；
An amplitude calculator calculates a PW voltage amplitude feedback value U 'containing noise at present'p(n)；
The second low-pass filter carries out filtering processing to obtain the current feedback value U of the PW voltage amplitudep(n)。
On the other hand, the invention provides a method based on an unbalanced voltage compensation device of a brushless doubly-fed induction generator, which comprises the following steps:
using a given value of the PW phase
Figure BDA0002713875900000055
Converting the current feedback value of the PW current into a current feedback value i of a d-axis component of the PW currentpd(n)；
To ipd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n) performing multiplication to obtain the current calculated value Q of the total reactive power of the brushless doubly-fed induction generatorp(n)；
To Qp(n) carrying out high-pass filtering to obtain a current calculated value of the PW double-frequency reactive power
Figure BDA0002713875900000056
Then, the current compensation value of the q-axis component of the CW voltage is calculated
Figure BDA0002713875900000057
Using a given value of the PW phase
Figure BDA0002713875900000061
And the current feedback value u of the PW voltagep_abc(n) obtaining the current feedback value U of the PW voltage amplitudep(n)；
Setting the PW voltage amplitude
Figure BDA0002713875900000062
Current feedback value U of PW voltage amplitudep(n) performing PI control after difference, and outputting the current given value of the d-axis component of the CW current
Figure BDA0002713875900000063
By using
Figure BDA0002713875900000064
And the current compensation value of the q-axis component of the CW voltage
Figure BDA0002713875900000065
Outputs the current value u of the CW excitation voltage through addition, PI control and coordinate transformationc_abc(n) to the control winding.
Preferably, QpThe acquisition formula of (n) is:
Figure BDA0002713875900000066
is obtained by the formula
Figure BDA0002713875900000067
Wherein the content of the first and second substances,
Figure BDA0002713875900000068
calculating the current given value of the reactive power to be compensated for the (n-1) th time; qp(n-1) calculating the total reactive power of the brushless doubly-fed induction generator obtained in the (n-1) th time; f. ofc3Is the cut-off frequency of the high-pass filter; t is the sampling period.
Preferably, by using
Figure BDA0002713875900000069
And
Figure BDA00027138759000000610
obtaining the current value u of CW excitation voltagec_abcThe method of (n) is:
given value of d-axis component of CW current
Figure BDA00027138759000000611
Current feedback value i of d-axis component of CW currentcd(n) performing PI control on the difference value to obtain the current given value of the d-axis component of the CW voltage
Figure BDA00027138759000000612
Calculating present set point of q-axis component of CW current
Figure BDA00027138759000000613
And CW currentCurrent feedback value i of q-axis componentcq(n) and PI control is carried out after the difference value between the two, and the current given value u 'of the CW voltage q-axis component without considering the voltage compensation is obtained'cq(n)；
Using the current compensation value of the q-axis component of the CW voltage
Figure BDA00027138759000000614
To u'cq(n) carrying out summation compensation to obtain the current given value of the q-axis component of the CW voltage
Figure BDA00027138759000000615
Using the current set-point of the CW phase
Figure BDA00027138759000000616
Will be provided with
Figure BDA00027138759000000617
And the current set point of the q-axis component of the CW voltage
Figure BDA00027138759000000618
Converted to the current set point of CW voltage
Figure BDA00027138759000000619
According to
Figure BDA0002713875900000071
The generated PWM signal is transmitted to a control winding side converter to output the current value u of the three-phase excitation voltage required by CWc_abc(n)。
Preferably, a current feedback value U of the PW voltage amplitude is obtainedpThe method of (n) is:
integrating the given value of PW frequency to obtain the given value of PW phase
Figure BDA0002713875900000072
Using a given value of the PW phase
Figure BDA0002713875900000073
The current feedback value u of the PW voltagep_abc(n) current feedback value u converted into d-axis component of PW Voltagepd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n)；
Using the current feedback value u of the d-axis component of the PW voltagepd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n) calculating the current feedback value U of the PW voltage amplitudep(n)。
It should be noted that the symmetric load is a special case of the asymmetric load, and the compensation method provided by the invention is also suitable for the operation control of the independent power generation system of the brushless doubly-fed induction generator under the condition of the symmetric load.
Preferably, the current set point of the CW phase is obtained
Figure BDA0002713875900000074
The method comprises the following steps:
the current rotating speed omega of the brushless doubly-fed induction generatorr(n) amplification to (p)p+pc)ωr(n)；
Will be provided with
Figure BDA0002713875900000075
And (p)p+pc)ωr(n) taking the difference to obtain the current set value of the CW frequency
Figure BDA0002713875900000076
The current given value of the CW frequency is subjected to integral processing, and the current given value of the CW phase is obtained by combining a sampling period
Figure BDA0002713875900000077
Wherein p ispPW pole pair number; p is a radical ofcIs the CW pole pair number.
The compensation method provided by the invention is simple and reliable, has strong robustness, can realize a constant-voltage constant-frequency power generation function under the condition that the power generation system has unbalanced load, and is suitable for an independent ship shaft power generation system, an independent hydroelectric power generation system and an independent wind power generation system based on the brushless doubly-fed induction generator.
Through the technical scheme, compared with the prior art, the invention has the following beneficial effects:
the invention discloses a PW reactive power compensator which comprises a PW current converter, a multiplier, a high-pass filter and a resonance controller, wherein the multiplier adopts a formula
Figure BDA0002713875900000078
The control function of the resonant controller is:
Figure BDA0002713875900000081
calculating and acquiring current compensation value of q-axis component of CW voltage
Figure BDA0002713875900000082
The q-axis component of the CW voltage is compensated, so that a converter at the side of a control winding actively generates PW double-frequency reactive power caused by unbalanced load, thereby ensuring the balance of the PW voltage and realizing that the compensation method does not depend on the resistance and inductance parameters of a motor.
The invention adopts the PW voltage controller and the CW transformation angle generator to respectively carry out independent closed-loop control on the amplitude and the frequency of the PW voltage, realizes the decoupling control of the amplitude and the frequency of the PW voltage and enhances the robustness of an independent power generation system.
The CW current regulator disclosed by the invention realizes the decoupling control of the d-axis component and the q-axis component of the CW current, wherein the conversion reference angles of the CW voltage converter and the CW current converter do not depend on the resistance and inductance parameters of the motor, so that the CW current regulator has strong robustness to the variation of the resistance and inductance parameters in the operation process of the motor independent power generation system.
Drawings
Fig. 1 is a method for compensating an unbalanced voltage of an independent power generation system according to an embodiment of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.
The invention discloses an unbalanced voltage compensation device, which is applied to an independent power generation system of a brushless doubly-fed induction generator and specifically comprises the following components:
the PW voltage controller sets the given value of the PW voltage amplitude
Figure BDA0002713875900000083
Current feedback value U of PW voltage amplitudep(n) performing PI control after difference, and outputting the current given value of the d-axis component of the CW current
Figure BDA0002713875900000084
CW transform angle generator for providing a current given value of the CW phase
Figure BDA0002713875900000085
The PW voltage amplitude calculator receives a current value u of the PW voltagep_abc(n) given value of PW frequency
Figure BDA0002713875900000086
Calculating U through coordinate transformationp(n)；
The input end of the PW reactive power compensator is connected with the PW voltage amplitude calculator, the output end of the PW reactive power compensator is connected with the CW current regulator, and the current compensation value of the q-axis component of the CW voltage is calculated
Figure BDA0002713875900000091
Comprises a PW current converter, a multiplier, a high-pass filter and a resonance controller which are connected in sequence;
the PW current converter converts the current feedback value of the PW current into a current feedback value i of the d-axis component of the PW currentpd(n); the multiplier is based on ipd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n) calculating the current calculated value Q of the total reactive power of the brushless doubly-fed induction generatorp(n); high-pass filter for obtaining PW double-frequency reactive powerRate current calculation value
Figure BDA0002713875900000092
Resonance controller calculation
Figure BDA0002713875900000093
Input to a CW current regulator;
CW current regulator reception
Figure BDA0002713875900000094
And the current compensation value of the q-axis component of the CW voltage
Figure BDA0002713875900000095
Outputs the current value u of the CW excitation voltage through addition, PI control and coordinate transformationc_abc(n) to the control winding.
Preferably, the multiplier is based on
Figure BDA0002713875900000096
Calculating Qp(n); the resonance controller is based on
Figure BDA0002713875900000097
Computing
Figure BDA0002713875900000098
Wherein the content of the first and second substances,
Figure BDA0002713875900000099
calculating the current given value of the reactive power to be compensated for the (n-1) th time; qp(n-1) calculating the total reactive power of the brushless doubly-fed induction generator obtained in the (n-1) th time; f. ofc3Is the cut-off frequency of the high-pass filter; t is the sampling period.
Preferably, the CW conversion angle generator includes a proportional amplifier, a fifth adder, and a first integrator, which are connected in sequence;
the proportional amplifier is used for converting the current rotating speed omega of the brushless doubly-fed induction generatorr(n) amplification to (p)p+pc)ωr(n)；
The fifth adder is used for adding
Figure BDA00027138759000000910
And (p)p+pc)ωr(n) taking the difference to obtain the current set value of the CW frequency
Figure BDA00027138759000000911
The first integrator integrates the current given value of the CW frequency, and the current given value of the CW phase is obtained by combining the sampling period
Figure BDA0002713875900000101
Wherein p ispPW pole pair number; p is a radical ofcIs the CW pole pair number.
Preferably, the CW current regulator includes:
the input end of the second adder is connected with the output end of the PW voltage controller, and the output end of the second adder is connected with the input end of the PI controller; calculating the present set point of the d-axis component of the CW current
Figure BDA0002713875900000102
Current feedback value i of d-axis component of CW currentcd(n) the difference between (n);
the output end of the second PI controller is connected with the input end of the CW voltage converter; calculating the current set point of the d-axis component of the CW voltage
Figure BDA0002713875900000103
The input end of the third adder is connected with the output end of the CW current converter, and the output end of the third adder is connected with the third PI controller; calculating present set point of q-axis component of CW current
Figure BDA0002713875900000104
Current feedback value i of q-axis component of CW currentcq(n) the difference between (n);
the output end of the third PI controller is connected with the first input end of the fourth adderConnecting; calculating a current setpoint value u 'of the CW voltage q-axis component without taking into account the voltage compensation'cq(n)；
The second input end of the fourth adder is connected with the output end of the PW reactive power compensator, and the output end of the fourth adder is connected with the input end of the CW voltage converter; calculating a current setpoint value u 'of the CW voltage q-axis component without taking into account the voltage compensation'cq(n) and
Figure BDA0002713875900000105
summing;
the output end of the CW voltage converter is connected with the input end of the PWM signal generator; will be provided with
Figure BDA0002713875900000106
And the current set point of the q-axis component of the CW voltage
Figure BDA0002713875900000107
Converted to the current set point of CW voltage
Figure BDA0002713875900000108
CW current converterc_abc(n) is transformed into icd(n) and icq(n)；
PWM signal generator based on
Figure BDA0002713875900000109
Generating a PWM signal;
controlling the winding side converter to invert the direct current into the alternating current according to the PWM signal and outputting the current value u of the three-phase excitation voltage required by CWc_abc(n)。
Preferably, the PW voltage amplitude calculator includes a second integrator, a PW voltage converter, an amplitude calculator, and a second low-pass filter, which are connected in sequence;
the second integrator calculates the given value of the PW phase according to the sampling period and the given value of the PW frequency
Figure BDA0002713875900000111
PW voltage converterFor applying the current feedback value u of the PW voltagep_abc(n) current feedback value u converted into d-axis component of PW Voltagepd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n)；
The amplitude calculator is used for calculating a PW voltage amplitude feedback value containing noise at present;
the second low-pass filter is used for calculating the current feedback value U of the PW voltage amplitudep(n)。
The method for the unbalanced voltage compensation device based on the above disclosure comprises the following steps:
using a given value of the PW phase
Figure BDA0002713875900000112
Converting the current feedback value of the PW current into a current feedback value i of a d-axis component of the PW currentpd(n)；
To ipd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n) performing multiplication to obtain the current calculated value Q of the total reactive power of the brushless doubly-fed induction generatorp(n)；
To Qp(n) carrying out high-pass filtering to obtain a current calculated value of the PW double-frequency reactive power
Figure BDA0002713875900000113
And (6) finally. Calculating the current compensation value of the q-axis component of the CW voltage
Figure BDA0002713875900000114
Using a given value of the PW phase
Figure BDA0002713875900000115
And the current feedback value u of the PW voltagep_abc(n) obtaining the current feedback value U of the PW voltage amplitudep(n)；
Setting the PW voltage amplitude
Figure BDA0002713875900000116
Current feedback value U of PW voltage amplitudep(n) performing PI control after difference to output CW current d-axis componentCurrent set point of quantity
Figure BDA0002713875900000117
By using
Figure BDA0002713875900000118
And the current compensation value of the q-axis component of the CW voltage
Figure BDA0002713875900000119
Outputs the current value u of the CW excitation voltage through addition, PI control and coordinate transformationc_abc(n) to the control winding.
Preferably, QpThe acquisition formula of (n) is:
Figure BDA00027138759000001110
is obtained by the formula
Figure BDA00027138759000001111
Wherein the content of the first and second substances,
Figure BDA00027138759000001112
calculating the current given value of the reactive power to be compensated for the (n-1) th time; qp(n-1) calculating the total reactive power of the brushless doubly-fed induction generator obtained in the (n-1) th time; f. ofc3Is the cut-off frequency of the high-pass filter; t is the sampling period.
Preferably, by using
Figure BDA0002713875900000121
And
Figure BDA0002713875900000122
obtaining the current value u of CW excitation voltagec_abcThe method of (n) is:
current set point of d-axis component of CW current
Figure BDA0002713875900000123
Current feedback value i of d-axis component of CW currentcd(n) betweenPerforming PI control to obtain the current given value of the d-axis component of the CW voltage
Figure BDA0002713875900000124
Calculating present set point of q-axis component of CW current
Figure BDA0002713875900000125
Current feedback value i of q-axis component of CW currentcq(n) and PI control is carried out after the difference value between the two, and the current given value u 'of the CW voltage q-axis component without considering the voltage compensation is obtained'cq(n)；
Using the current compensation value of the q-axis component of the CW voltage
Figure BDA0002713875900000126
To u'cq(n) carrying out summation compensation to obtain the current given value of the q-axis component of the CW voltage
Figure BDA0002713875900000127
Using the current set-point of the CW phase
Figure BDA0002713875900000128
Will be provided with
Figure BDA0002713875900000129
And the current set point of the q-axis component of the CW voltage
Figure BDA00027138759000001210
Converted to the current set point of CW voltage
Figure BDA00027138759000001211
According to
Figure BDA00027138759000001212
The generated PWM signal is input to a control winding side converter to output the current value u of the three-phase excitation voltage required by CWc_abc(n)。
Preferably, the amplitude of the PW voltage is obtainedCurrent feedback value UpThe method of (n) is:
integrating the given value of PW frequency to obtain the given value of PW phase
Figure BDA00027138759000001213
Using a given value of the PW phase
Figure BDA00027138759000001214
The current feedback value u of the PW voltagep_abc(n) current feedback value u converted into d-axis component of PW Voltagepd(n) and the current feedback value u of the d-axis component of the PW Voltagepq(n)；
Using the current feedback value u of the d-axis component of the PW voltagepd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n) calculating the current feedback value U of the PW voltage amplitudep(n)。
Preferably, the current set point of the CW phase is obtained
Figure BDA00027138759000001215
The method comprises the following steps:
the current rotating speed omega of the brushless doubly-fed induction generatorr(n) amplification to (p)p+pc)ωr(n)；
Will be provided with
Figure BDA0002713875900000131
And (p)p+pc)ωr(n) taking the difference to obtain the current set value of the CW frequency
Figure BDA0002713875900000132
The current given value of the CW frequency is subjected to integral processing, and the current given value of the CW phase is obtained by combining a sampling period
Figure BDA0002713875900000133
Wherein p ispPW pole pair number; p is a radical ofcIs the CW pole pair number.
Examples
As shown in fig. 1, the present embodiment discloses an unbalanced voltage compensation apparatus, which is applied to an independent power generation system of a brushless doubly-fed induction generator with reactive power, and specifically includes a PW voltage controller, a CW conversion angle generator, a CW current regulator, a PW voltage amplitude calculator and a PW reactive power compensator;
the PW voltage controller comprises a first adder and a first PI controller;
the first adder is used for adding a given value of the PW voltage amplitude
Figure BDA0002713875900000134
Current feedback value U of PW voltage amplitudep(n) making a difference;
the first PI controller is used for calculating the current given value of the d-axis component of the CW current
Figure BDA0002713875900000135
The method comprises the following specific steps:
Figure BDA0002713875900000136
wherein the content of the first and second substances,
Figure BDA0002713875900000137
the current given value of the d-axis component of the CW current obtained by the nth calculation is obtained;
Figure BDA0002713875900000138
is a given value of PW voltage amplitude; u shapep(n) is the current feedback value of the PW voltage amplitude; kp1And τi1Respectively is a proportional amplification factor and an integral time constant of the first PI controller; 0<The sampling period T is less than or equal to 1ms and is determined by hardware adopted by a user; the operation times j are 1.·, n; u shapep(j) The PW voltage amplitude fed back for the jth time; current set point of d-axis component of CW current
Figure BDA0002713875900000139
Feeding into a CW current regulator so that the current inverse of the PW voltage magnitudeValue of Up(n) successive approximation
Figure BDA00027138759000001310
Thereby making it possible to
Figure BDA00027138759000001311
0, the calculation result is not changed;
parameter K of the first PI controllerp1And τi1Debugging is carried out in the following way: firstly, tau isi1To infinity, gradually increase Kp1Recording the frequency f of the PW voltage amplitude oscillation until the PW voltage amplitude oscillation occurs1At this time, Kp1Is a maximum value Kp1_maxSetting Kp1＝0.45Kp1_max、
Figure BDA00027138759000001312
The CW conversion angle generator includes a differentiator, a first low pass filter, a proportional amplifier, a fifth adder, and a first integrator:
the differentiator is used for acquiring the current noise-containing rotating speed omega 'of the brushless doubly-fed induction generator'r(n)：
Figure BDA0002713875900000141
Wherein, thetar(n) and thetar(n-1) respectively obtaining the current rotor position of the brushless doubly-fed induction generator and the rotor position of the brushless doubly-fed induction generator obtained by the n-1 th calculation; omega'r(n) is the current noise-containing rotating speed of the brushless doubly-fed induction generator; t is a sampling period;
the first low-pass filter is used for obtaining the current rotating speed of the brushless doubly-fed induction generator, and specifically comprises the following steps:
Figure BDA0002713875900000142
wherein, ω isr(n) is brushless doubly-fed induction generator presentA rotational speed; omega'r(n) is the current noise-containing rotating speed of the brushless doubly-fed induction generator; f. ofc1F is 5Hz or less of the cut-off frequency of the first low-pass filterc1≤10Hz，fc1The larger the filtering effect is, the better the filtering effect is; 0<The sampling period T is less than or equal to 1 ms; omegar(n-1) calculating the rotating speed of the brushless doubly-fed induction generator in the (n-1) th time; inputting the current rotating speed of the brushless doubly-fed induction generator into a fifth adder;
current rotating speed omega of brushless doubly-fed induction generatorr(n) is amplified to (p) by a proportional amplifierp+pc)ωr(n) wherein ppPW pole pair number; p is a radical ofcIs the CW pole pair number; inputting the operation result into a fifth adder;
the fifth adder is used for calculating the current given value of CW frequency
Figure BDA0002713875900000143
Figure BDA0002713875900000144
Wherein the content of the first and second substances,
Figure BDA0002713875900000145
is the current given value of the CW frequency; p is a radical ofpPW pole pair number; p is a radical ofcIs the CW pole pair number; omegar(n) is the current rotating speed of the brushless doubly-fed induction motor;
Figure BDA0002713875900000146
is a given value of the PW frequency;
Figure BDA0002713875900000147
inputting the signal into a first integrator;
the first integrator is used for calculating the current given value of the CW phase
Figure BDA0002713875900000148
Figure BDA0002713875900000149
Wherein the content of the first and second substances,
Figure BDA0002713875900000151
is the current given value of the CW phase; t is a sampling period; the operation times j are 1.·, n;
Figure BDA0002713875900000152
calculating the current given value of the CW frequency for the jth time;
Figure BDA0002713875900000153
an input CW current regulator;
the CW current regulator comprises a second adder, a third adder, a fourth adder, a second PI controller, a third PI controller, a CW voltage converter, a CW current converter, a PWM signal generator and a control winding converter;
the second adder calculates the current given value of the d-axis component of the CW current
Figure BDA0002713875900000154
Current feedback value i of d-axis component of CW currentcd(n) the difference between (n) and (n),
Figure BDA0002713875900000155
inputting the current operation times into a second PI controller, wherein n is the current operation times;
the second PI controller is used for calculating the current given value of the d-axis component of the CW voltage
Figure BDA0002713875900000156
Figure BDA0002713875900000157
Wherein the content of the first and second substances,
Figure BDA0002713875900000158
the current given value of the d-axis component of the CW voltage;
Figure BDA0002713875900000159
the current given value of the d-axis component of the CW current; i.e. icd(n) is the current feedback value of the d-axis component of the CW current; kp2And τi2Respectively is a proportional amplification factor and an integral time constant of the second PI controller; i.e. icd(j) The d-axis component value of the CW current fed back for the jth time;
Figure BDA00027138759000001510
an input CW voltage converter;
the third adder calculates the current given value of q-axis component of CW current
Figure BDA00027138759000001511
Current feedback value i of q-axis component of CW currentcq(n) the difference between (n) and (n),
Figure BDA00027138759000001512
inputting a third PI controller;
the third PI controller is used for calculating the current given value u 'of the CW voltage q-axis component without considering the voltage compensation'cq(n)；
Figure BDA00027138759000001513
Wherein u'cq(n) is the current set point of the q-axis component of the CW voltage without considering the voltage compensation;
Figure BDA00027138759000001514
the current given value of the q-axis component of the CW current; i.e. icq(n) is the current feedback value of the q-axis component of the CW current; kp3And τi3Proportional amplification factor and integral time constant of the third PI controller respectively; i.e. icq(j) The q-axis component value of the CW current fed back for the jth time; u'cq(n) input to a fourth adder;
the fourth adder calculates the current given value u 'of the CW voltage q-axis component without considering the voltage compensation'cq(n) current compensation value with q-axis component of CW voltage
Figure BDA0002713875900000161
Sum, operation result
Figure BDA0002713875900000162
An input CW voltage converter;
the CW transformation angle generator calculates a current given value of the CW phase
Figure BDA0002713875900000163
Input to a CW voltage converter and a CW current converter;
the CW voltage converter converts the current given value of the d-axis component of the CW voltage in the dq rotation coordinate system
Figure BDA0002713875900000164
And the current set point of the q-axis component of the CW voltage
Figure BDA0002713875900000165
Converting to a current set value of CW voltage under an abc coordinate system
Figure BDA0002713875900000166
(namely:
Figure BDA0002713875900000167
and
Figure BDA0002713875900000168
) Inputting the PWM signal generator; the concrete transformation formula is as follows:
Figure BDA0002713875900000169
wherein the reference angle is changed
Figure BDA00027138759000001610
Is the current given value of the CW phase;
the CW current converter converts the current feedback value i of the CW current in an abc coordinate systemc_abc(n) (i.e.: i)ca(n)、icb(n) and icc(n)) is transformed into the current feedback value i of the d-axis component of the CW current in the dq rotation coordinate systemcd(n) and the present feedback value i of the q-axis component of the CW currentcq(n) mixing icd(n) input to a second adder, add icd(n) input to a third adder; the specific transformation formula is as follows:
Figure BDA00027138759000001611
wherein the reference angle is changed
Figure BDA00027138759000001612
Is the current given value of the CW phase;
PWM signal generator according to CW voltage current set value under abc coordinate system
Figure BDA0002713875900000171
Generating a PWM signal, and inputting the PWM signal to a control winding side converter;
controlling the current value u of the three-phase excitation voltage required by the winding-side converter to output CW according to the PWM signalc_abc(n) to a brushless doubly fed induction generator.
The PW voltage amplitude calculator comprises a second integrator, a PW voltage converter, an amplitude calculator and a second low-pass filter;
the second integrator is used for calculating a given value of the PW phase
Figure BDA0002713875900000172
Figure BDA0002713875900000173
Wherein the content of the first and second substances,
Figure BDA0002713875900000174
is a given value of the PW phase and is input into a PW voltage converter and a PW current converter,
Figure BDA0002713875900000175
is a given value of the PW frequency;
the PW voltage converter converts the current feedback value u of the PW voltage in an abc coordinate systemp_abc(n) (i.e., u)pa(n)、upb(n) and upc(n)) is converted into the current feedback value u of the d-axis component of the PW voltage in the dq rotation coordinate systempd(n), current feedback value u of q-axis component of PW voltagepq(n)；
The specific transformation formula is as follows:
Figure BDA0002713875900000176
wherein the reference angle is changed
Figure BDA0002713875900000177
A given value of PW phase;
the amplitude calculator is used for calculating a PW voltage amplitude feedback value U 'containing noise at present'p(n)；
Figure BDA0002713875900000178
Wherein, U'p(n) is a PW voltage amplitude feedback value containing noise at present; u. ofpd(n) is the current feedback value of the d-axis component of the PW voltage; u. ofpq(n) is the current feedback value of the q-axis component of the PW voltage; u'p(n) input to a second low pass filter;
the second low-pass filter calculates the current feedback value U of the PW voltage amplitudep(n)；
Figure BDA0002713875900000181
Wherein, Up(n) is the current feedback value of the PW voltage amplitude; u'p(n) is a PW voltage amplitude feedback value containing noise at present; f. ofc2Is the cut-off frequency of the second low-pass filter; u shapep(n-1) is calculated for the (n-1) th timeThe feedback value of the amplitude of the obtained PW voltage; u shapep(n) to the first adder.
The PW reactive power compensator comprises a PW current converter, a multiplier, a high-pass filter and a resonance controller;
the PW current converter converts the current feedback value i of the PW current in an abc coordinate systemp_abc(n) (i.e., i)pa(n)、ipb(n) and ipc(n)) is converted into the current feedback value i of the d-axis component of the PW current under the dq rotation coordinate systempd(n) and input it to the multiplier;
the transformation formula is as follows:
Figure BDA0002713875900000182
wherein the reference angle is changed
Figure BDA0002713875900000183
A given value of PW phase;
multiplier for calculating current calculation value Q of total reactive power of brushless doubly-fed induction generatorp(n)；
Figure BDA0002713875900000184
Wherein Q isp(n) is a current calculated value of the total reactive power of the brushless doubly-fed induction generator, and comprises two parts corresponding to a balanced load and an unbalanced load; u. ofpq(n) is the current feedback value of the q-axis component of the PW voltage; i.e. ipd(n) is the current feedback value of the d-axis component of the PW current; qp(n) inputting to a high pass filter;
the high-pass filter is used for acquiring a current calculated value of PW double-frequency reactive power caused by unbalanced load in the brushless doubly-fed induction generator
Figure BDA0002713875900000185
Figure BDA0002713875900000191
Wherein the content of the first and second substances,
Figure BDA0002713875900000192
the current calculation value of the PW double-frequency reactive power caused by the unbalanced load in the brushless doubly-fed induction generator is the current given value of the reactive power to be compensated; qp(n) is a current calculated value of the total reactive power of the brushless doubly-fed induction generator, and comprises two parts corresponding to a balanced load and an unbalanced load; f. ofc3Is the cut-off frequency of the high-pass filter;
Figure BDA0002713875900000193
calculating the current given value of the reactive power to be compensated for the (n-1) th time; qp(n-1) calculating the total reactive power of the brushless doubly-fed induction generator obtained in the (n-1) th time;
Figure BDA0002713875900000194
inputting to a resonance controller;
the resonance controller is used for calculating the current compensation value of the q-axis component of the CW voltage
Figure BDA0002713875900000195
Figure BDA0002713875900000196
Wherein the content of the first and second substances,
Figure BDA0002713875900000197
a current compensation value of q-axis component of CW voltage;
Figure BDA0002713875900000198
the current given value of the reactive power to be compensated is obtained; krA resonant amplifier being a resonant controller; omegac4Is the cut-off angular frequency of the resonant controller; omega0Represents the resonant frequency;
Figure BDA0002713875900000199
calculating the current given value of the reactive power to be compensated for the n-1 st time;
Figure BDA00027138759000001910
respectively representing compensation values of q-axis components of the CW voltage obtained by the n-1 st calculation and the n-2 nd calculation;
Figure BDA00027138759000001911
input to the fourth adder.
It should be noted that the symmetric load is a special case of the asymmetric load, and the compensation method provided by the invention is also suitable for the operation control of the independent power generation system of the brushless doubly-fed induction generator under the condition of the symmetric load.
The compensation method provided by the invention is simple and reliable, has strong robustness, can realize a constant-voltage constant-frequency power generation function under the condition that the power generation system has unbalanced load, and is suitable for an independent ship shaft power generation system, an independent hydroelectric power generation system and an independent wind power generation system based on the brushless doubly-fed induction generator.
Compared with the prior art, the technical scheme of the invention can obtain the following beneficial effects:
the invention discloses a PW reactive power compensator which comprises a PW current converter, a multiplier, a high-pass filter and a resonance controller, wherein the multiplier adopts a formula
Figure BDA00027138759000001912
The control function of the resonant controller is:
Figure BDA0002713875900000201
calculating and acquiring current compensation value of q-axis component of CW voltage
Figure BDA0002713875900000202
The q-axis component of the CW voltage is compensated, so that the converter at the side of the control winding actively generates PW double-frequency reactive power caused by unbalanced load, thereby ensuring the PW voltageAnd balancing is realized, and the compensation method is independent of resistance and inductance parameters of the motor.
The invention adopts the PW voltage controller and the CW transformation angle generator to respectively carry out independent closed-loop control on the amplitude and the frequency of the PW voltage, realizes the decoupling control of the amplitude and the frequency of the PW voltage and enhances the robustness of an independent power generation system.
The CW current regulator disclosed by the invention realizes the decoupling control of the d-axis component and the q-axis component of the CW current, wherein the conversion reference angles of the CW voltage converter and the CW current converter do not depend on the resistance and inductance parameters of the motor, so that the CW current regulator has strong robustness to the variation of the resistance and inductance parameters in the operation process of the motor independent power generation system.
It will be understood by those skilled in the art that the foregoing is only a preferred embodiment of the present invention, and is not intended to limit the invention, and that any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention should be included in the scope of the present invention.

Claims (10)

1. The utility model provides an unbalanced voltage compensation arrangement of brushless doubly-fed induction generator, is applied to the independent power generation system of brushless doubly-fed induction generator, its characterized in that includes:
the PW voltage controller sets the given value of the PW voltage amplitude
Figure FDA0002713875890000011
Current feedback value U of PW voltage amplitudep(n) performing PI control after difference, and outputting the current given value of the d-axis component of the CW current
Figure FDA0002713875890000012
CW transform angle generator for providing a current given value of the CW phase
Figure FDA0002713875890000013
The PW voltage amplitude calculator receives a current value u of the PW voltagep_abc(n) given value of PW frequency
Figure FDA0002713875890000014
Calculating U through coordinate transformationp(n)；
The output end of the PW reactive power compensator is connected with the CW current regulator and comprises a PW current converter, a multiplier, a high-pass filter and a resonance controller which are connected in sequence;
the PW current converter feeds a current feedback value i of the PW currentp_abc(n) current feedback value i converted into d-axis component of PW currentpd(n); the multiplier is based on ipd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n) calculating the current calculated value Q of the total reactive power of the brushless doubly-fed induction generatorp(n); high pass filter slave Qp(n) obtaining the current calculated value of the PW double-frequency reactive power
Figure FDA0002713875890000015
A resonance controller based on
Figure FDA0002713875890000016
Calculating the current compensation value of the q-axis component of the CW voltage
Figure FDA0002713875890000017
CW current regulator reception
Figure FDA0002713875890000018
And
Figure FDA0002713875890000019
outputting the current value u of the CW excitation voltage through addition operation, PI control and coordinate transformationc_abc(n)。
2. A brushless doubly fed induction generator unbalanced voltage compensation arrangement as claimed in claim 1 wherein said multiplier is based on
Figure FDA00027138758900000110
ComputingQp(n); the resonance controller is based on
Figure FDA00027138758900000111
Computing
Figure FDA00027138758900000112
Wherein the content of the first and second substances,
Figure FDA00027138758900000113
calculating the current given value of the reactive power to be compensated for the (n-1) th time; qp(n-1) calculating the total reactive power of the brushless doubly-fed induction generator obtained in the (n-1) th time; f. ofc3Is the cut-off frequency of the high-pass filter; t is the sampling period.
3. The unbalanced voltage compensation apparatus of a brushless doubly fed induction generator as claimed in claim 1, wherein the CW conversion angle generator comprises a proportional amplifier, a fifth adder and a first integrator which are connected in sequence;
the proportional amplifier is used for converting the current rotating speed omega of the brushless doubly-fed induction generatorr(n) amplification to (p)p+pc)ωr(n)；
The fifth adder is used for adding
Figure FDA0002713875890000021
And (p)p+pc)ωr(n) taking the difference to obtain the current set value of the CW frequency
Figure FDA0002713875890000022
The first integrator integrates the current given value of the CW frequency, and the current given value of the CW phase is obtained by combining the sampling period
Figure FDA0002713875890000023
Wherein p ispPW pole pair number; p is a radical ofcIs a CW pole pairAnd (4) counting.
4. A brushless doubly fed induction generator unbalanced voltage compensation arrangement as claimed in claim 2 wherein said CW current regulator comprises:
the input end of the second adder is connected with the output end of the PW voltage controller, and the output end of the second adder is connected with the input end of the PI controller; calculating the present set point of the d-axis component of the CW current
Figure FDA0002713875890000024
Current feedback value i of d-axis component of CW currentcd(n) the difference between (n);
the output end of the second PI controller is connected with the input end of the CW voltage converter; obtaining the current given value of the d-axis component of the CW voltage by PI control
Figure FDA0002713875890000025
The input end of the third adder is connected with the output end of the CW current converter, and the output end of the third adder is connected with the third PI controller; calculating present set point of q-axis component of CW current
Figure FDA0002713875890000026
Current feedback value i of q-axis component of CW currentcq(n) the difference between (n);
the output end of the third PI controller is connected with the first input end of the fourth adder; obtaining a current given value u 'of a CW voltage q-axis component without considering voltage compensation through PI control'cq(n)；
The second input end of the fourth adder is connected with the output end of the PW reactive power compensator, and the output end of the fourth adder is connected with the input end of the CW voltage converter; calculating a current setpoint value u 'of the CW voltage q-axis component without taking into account the voltage compensation'cq(n) and
Figure FDA0002713875890000031
summing;
the output end of the CW voltage converter is connected with the input end of the PWM signal generator;will be provided with
Figure FDA0002713875890000032
And the current set point of the q-axis component of the CW voltage
Figure FDA0002713875890000033
Converted to the current set point of CW voltage
Figure FDA0002713875890000034
CW current converterc_abc(n) is transformed into icd(n) and icq(n)；
PWM signal generator based on
Figure FDA0002713875890000035
Generating a PWM signal;
controlling the winding side converter to invert the direct current into the alternating current according to the PWM signal and outputting the current value u of the three-phase excitation voltage required by CWc_abc(n)。
5. A brushless doubly-fed induction generator unbalanced voltage compensation arrangement according to any one of claims 1 to 4, wherein said PW voltage magnitude calculator comprises a second integrator, a PW voltage converter, a magnitude calculator and a second low pass filter connected in series;
the second integrator calculates the given value of the PW phase according to the sampling period and the given value of the PW frequency
Figure FDA0002713875890000036
The PW voltage converter is used for converting the current feedback value u of the PW voltagep_abc(n) current feedback value u converted into d-axis component of PW Voltagepd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n)；
The amplitude calculator is used for calculating a PW voltage amplitude feedback value U 'containing noise at present'p(n)；
For the second low-pass filterFrom U'p(n) obtaining the current feedback value U of the PW voltage amplitudep(n)。
6. A method for compensating the unbalanced voltage of the brushless doubly fed induction generator according to claim 1, characterized by comprising the following steps:
using a given value of the PW phase
Figure FDA0002713875890000037
Converting the current feedback value of the PW current into a current feedback value i of a d-axis component of the PW currentpd(n)；
To ipd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n) performing multiplication to obtain the current calculated value Q of the total reactive power of the brushless doubly-fed induction generatorp(n)；
To Qp(n) carrying out high-pass filtering to obtain a current calculated value of the PW double-frequency reactive power
Figure FDA0002713875890000041
Then, the current compensation value of the q-axis component of the CW voltage is calculated
Figure FDA0002713875890000042
Using a given value of the PW phase
Figure FDA0002713875890000043
And the current feedback value u of the PW voltagep_abc(n) obtaining the current feedback value U of the PW voltage amplitudep(n)；
Setting the PW voltage amplitude
Figure FDA0002713875890000044
Current feedback value U of PW voltage amplitudep(n) performing PI control after difference, and outputting the current given value of the d-axis component of the CW current
Figure FDA0002713875890000045
By using
Figure FDA0002713875890000046
And the current compensation value of the q-axis component of the CW voltage
Figure FDA0002713875890000047
Outputs the current value u of the CW excitation voltage through addition, PI control and coordinate transformationc_abc(n) to the control winding.
7. The method of claim 6, wherein Q ispThe acquisition formula of (n) is:
Figure FDA0002713875890000048
Figure FDA0002713875890000049
is obtained by the formula
Figure FDA00027138758900000410
Wherein the content of the first and second substances,
Figure FDA00027138758900000411
calculating the current given value of the reactive power to be compensated for the (n-1) th time; qp(n-1) calculating the total reactive power of the brushless doubly-fed induction generator obtained in the (n-1) th time; f. ofc3Is the cut-off frequency of the high-pass filter; t is the sampling period.
8. Method according to claim 6, characterized by using
Figure FDA00027138758900000412
And
Figure FDA00027138758900000413
obtaining the current value u of CW excitation voltagec_abcThe method of (n) is:
given value of d-axis component of CW current
Figure FDA00027138758900000414
Current feedback value i of d-axis component of CW currentcd(n) performing PI control on the difference value to obtain the current given value of the d-axis component of the CW voltage
Figure FDA00027138758900000415
Calculating present set point of q-axis component of CW current
Figure FDA0002713875890000051
Current feedback value i of q-axis component of CW currentcq(n) and PI control is carried out after the difference value between the two, and the current given value u 'of the CW voltage q-axis component without considering the voltage compensation is obtained'cq(n)；
Using the current compensation value of the q-axis component of the CW voltage
Figure FDA0002713875890000052
To u'cq(n) carrying out summation compensation to obtain the current given value of the q-axis component of the CW voltage
Figure FDA0002713875890000053
Using the current set-point of the CW phase
Figure FDA0002713875890000054
Will be provided with
Figure FDA0002713875890000055
And the current set point of the q-axis component of the CW voltage
Figure FDA0002713875890000056
Converted to the current set point of CW voltage
Figure FDA0002713875890000057
According to
Figure FDA0002713875890000058
The generated PWM signal is transmitted to a control winding side converter to output the current value u of the three-phase excitation voltage required by CWc_abc(n)。
9. The method of claim 6, wherein a current feedback value U of the PW voltage amplitude is obtainedpThe method of (n) is:
integrating the given value of PW frequency to obtain the given value of PW phase
Figure FDA0002713875890000059
Using a given value of the PW phase
Figure FDA00027138758900000510
The current feedback value u of the PW voltagep_abc(n) current feedback value u converted into d-axis component of PW Voltagepd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n)；
Using the current feedback value u of the d-axis component of the PW voltagepd(n) and the current feedback value u of the q-axis component of the PW Voltagepq(n) calculating the current feedback value U of the PW voltage amplitudep(n)。
10. Method according to any of claims 6 to 9, characterized in that the current setpoint value of the CW phase is obtained
Figure FDA00027138758900000511
The method comprises the following steps:
the current rotating speed omega of the brushless doubly-fed induction generatorr(n) amplification to (p)p+pc)ωr(n)；
Will be provided with
Figure FDA00027138758900000512
And (p)p+pc)ωr(n) taking the difference to obtain the current set value of the CW frequency
Figure FDA00027138758900000513
The current given value of the CW frequency is subjected to integral processing, and the current given value of the CW phase is obtained by combining a sampling period
Figure FDA00027138758900000514
Wherein p ispPW pole pair number; p is a radical ofcIs the CW pole pair number.
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