CN106452235B - Brushless dual-feed motor stand alone generating system excitation control method under asymmetric load - Google Patents
Brushless dual-feed motor stand alone generating system excitation control method under asymmetric load Download PDFInfo
- Publication number
- CN106452235B CN106452235B CN201611042019.8A CN201611042019A CN106452235B CN 106452235 B CN106452235 B CN 106452235B CN 201611042019 A CN201611042019 A CN 201611042019A CN 106452235 B CN106452235 B CN 106452235B
- Authority
- CN
- China
- Prior art keywords
- sequence
- negative
- phase
- positive
- rotating frame
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P9/00—Arrangements for controlling electric generators for the purpose of obtaining a desired output
- H02P9/007—Control circuits for doubly fed generators
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P9/00—Arrangements for controlling electric generators for the purpose of obtaining a desired output
- H02P9/48—Arrangements for obtaining a constant output value at varying speed of the generator, e.g. on vehicle
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Control Of Ac Motors In General (AREA)
- Control Of Motors That Do Not Use Commutators (AREA)
Abstract
The invention discloses brushless dual-feed motor stand alone generating system excitation control methods under a kind of asymmetric load, this method is based on just, the double dq coordinate systems of negative phase-sequence, it is positive-sequence component and negative sequence component by the power winding PW voltage decompositions of brushless dual-feed motor, then PW voltage positive-sequence component controllers are respectively adopted and negative sequence component controller adjusts the amplitude and frequency of PW voltages positive sequence and negative sequence component, control winding CW voltages positive sequence needed for obtaining and negative sequence component, CW voltages are just, negative sequence component is added up to final CW voltage given values, PWM modulation signal is generated according to the given value, and then inverter is driven to control CW, finally the amplitude of PW voltage positive-sequence components and frequency is made to track given value respectively, the amplitude of PW voltage negative sequence components converges to 0.Constant frequency and constant voltage generating function of brushless dual-feed motor stand alone generating system under the conditions of asymmetric load is can be well realized using this method, control method is simple and reliable, strong robustness.
Description
Technical field
The invention belongs to brushless dual-feed motor technical field of power generation control, more particularly, to a kind of asymmetric load item
The excitation control method of brushless dual-feed motor stand alone generating system under part.
Background technology
Brushless dual-feed motor is a kind of novel AC induction motor, this motor by two sets of different numbers of pole-pairs stator winding
It is constituted with a set of rotor windings.Its basic principle, which is the rotor by special designing, makes two sets of stator winding generate different numbers of pole-pairs
Rotating excitation field Indirect Interaction, and can interact and be controlled to realize energy transmission to it.Brushless dual-feed motor
Two sets of stator winding are referred to as power winding (power winding, hereinafter referred to as PW) and control winding (control
Winding, hereinafter referred to as CW), which can be used as motor running, can also generator is used as to run, have asynchronous machine concurrently
And the characteristics of synchronous motor.
Asymmetric load can make existing unbalanced three-phase currents in the PW of brushless dual-feed motor, and unbalanced three-phase currents are in PW
Each phase internal impedance on generate different pressure drops so that the output voltage (i.e. PW voltages) of electricity generation system occur it is asymmetric,
This makes under conventional control method, the output voltage amplitude and frequency constant of brushless dual-feed motor stand alone generating system
Control targe be difficult to realize.
Both included positive-sequence component according to Instantaneous Symmetrical Components theory, in asymmetric voltage or includes negative sequence component.It is sending out
A kind of bright excitation controlling device (application number of brushless dual-feed motor stand alone generating system of patent：201510391869.8) provided
Control method in, the control to CW electric currents is based on single rotating coordinate system, and this method can not be to PW voltages intrinsically
In positive-sequence component and negative sequence component be carried out at the same time control.In order to make brushless dual-feed motor stand alone generating system in asymmetric load
Under the conditions of also can stable operation, need to build new control method.
Invention content
It is an object of the invention to overcome the deficiencies of the prior art and provide brushless double-fed under the conditions of a kind of asymmetric load
Machine stand alone generating system excitation control method realizes that brushless dual-feed motor stand alone generating system also can under the conditions of asymmetric load
Realize the constant frequency and constant voltage generating function under speed change varying duty operating mode.The method is suitable for the independent ship based on brushless dual-feed motor
Oceangoing ship Shaft-Generator, independent hydroelectric power system and independent wind generator system etc..
In order to realize the technical purpose of the present invention, present invention employs following technical solutions：
Brushless dual-feed motor stand alone generating system excitation control method, includes the following steps under asymmetric load：
(1) sampling PW three-phase voltage instantaneous values u1a、u1bAnd u1c, PW electricity is calculated using double Second Order Generalized Integrator phaselocked loops
The amplitude of positive pressure order componentsAnd the amplitude of negative sequence component
(2) sampling CW three-phase current instantaneous values i2a、i2bAnd i2c, calculate positive sequence d, q of the CW electric currents in positive synchronous rotating frame
ComponentWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWith
(3) sampling PW three-phase current instantaneous values i1a、i1bAnd i1c, calculate positive sequence d, q of the PW electric currents in positive synchronous rotating frame
ComponentWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWith
(4) according to the amplitude of PW voltage positive-sequence componentsPositive sequence d, q component of the CW electric currents in positive synchronous rotating frameCW three-phase voltage positive-sequence component given values are calculated using PW voltage positive-sequence component controllers
With
(5) according to the amplitude of PW voltage negative sequence componentsNegative phase-sequence d, q component of the CW electric currents in negative synchronous rotating frame
WithCW three-phase voltage negative sequence component given values are calculated using PW voltage negative sequence component controllersWith
(6) positive sequence of CW voltages is added to obtain CW voltage given values with negative sequence component given valueWith
Modulated signal is generated using SVPWM algorithms, and then inverter is made to export corresponding voltage to CW；
(7) repeat the above steps (1)~(6), and the amplitude of PW voltage positive-sequence components and frequency is made to track given value respectively, bears
The amplitude of order components converges to 0.
Further, the specific implementation of the step (2) is：
The phase of CW negative-sequence currents is calculated first
Wherein, θ1For PW voltage positive-sequence component phases,For the phase of CW forward-order currents
Then the phase of CW forward-order currents is usedBy CW three-phase current instantaneous values i2a、i2bAnd i2cBecome from abc coordinate systems
Transformation changes to positive synchronous rotating frame, obtains d, q component of the CW electric currents in positive synchronous rotating frameWithUsing CW negative phase-sequence electricity
The phase of streamBy CW three-phase current instantaneous values i2a、i2bAnd i2cFrom abc coordinate system transformation to negative synchronous rotating frame, CW electricity is obtained
Flow d, q component in negative synchronous rotating frameWithIt is as follows to convert expression formula：
It is right respectively using notch filterWithIt is filtered, obtains CW electric currents in positive synchronous rotating frame
In positive sequence d, q componentWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWith
Further, the concrete methods of realizing of the step (3) is：
The phase of PW forward-order currents is calculated firstWith the phase of PW negative-sequence currents
Wherein p1For the number of pole-pairs of power winding PW, p2The number of pole-pairs of winding CW in order to control, machineries of the η between PW and CW
Angular deviation；
Then the phase of PW forward-order currents is usedBy PW three-phase current instantaneous values i1a、i1bAnd i1cFrom abc coordinate system transformations
Positive synchronous rotating frame is transformed to obtainWithUsing the phase of PW negative-sequence currentsBy PW three-phase current instantaneous values i1a、i1bWith
i1cNegative synchronous rotating frame is transformed to from abc coordinate system transformations to obtainWithIt is as follows to convert expression formula：
It is right respectively using notch filterWithIt is filtered, obtains PW electric currents in positive synchronous rotating frame
In positive sequence d, q componentWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWith
Further, the concrete methods of realizing of the step (4) is：
Calculate the amplitude of PW voltage positive-sequence componentsWith given amplitudeDifference, adjusted the difference as the first PI
The output of the input of device, the first pi regulator is CW electric current positive sequence amplitude regulated quantitys Before CW electric current positive sequence amplitudes
Feedback amountAddition obtains the given value of CW electric current positive sequence amplitudes
Calculate PW electric voltage frequencies ω1With given frequencyDifference, using the difference as the input of the second pi regulator,
The output of two pi regulators is CW power frequency regulated quantitys With CW power frequency feedforward amountsAddition is obtaining CW just
The frequency of sequence electric currentIt is rightIntegral obtains the phase of CW forward-order currents
Enable positive sequence d axis component given value of the CW electric currents in positive synchronous rotating frameIt is equal toIt calculatesWith's
Difference, using the difference as the input of third pi regulator, the output of third pi regulator and CW voltages are in positive synchronous rotating frame
In positive sequence d axis feedforward amountsIt is added, obtains positive sequence d axis given value of the CW voltages in positive synchronous rotating frame
Enable positive sequence q axis component given value of the CW electric currents in positive synchronous rotating frameEqual to 0, calculateWithDifference
Value, using the difference as the input of the 4th pi regulator, the output of the 4th pi regulator and CW voltages are in positive synchronous rotating frame
Positive sequence q axis feedforward amountsIt is added, obtains positive sequence q axis given value of the CW voltages in positive synchronous rotating frame
Finally use the phase of CW forward-order currentsIt willWithAbc coordinate systems are transformed to from positive synchronous rotating frame,
Obtain the CW three-phase voltage positive-sequence component given values in abc coordinate systemsWith
Further, the CW electric currents positive sequence amplitude feedforward amountCW power frequency feedforward amountsCW voltage positive sequences d
Axis feedforward amountWith CW voltage positive sequence q axis feedforward amountsComputational methods be：
In formula,
In formula,
In formula,
WhereinFor the leakage inductance coefficient of CW, ωrFor motor speed, ω1For PW electric voltage frequencies,
For the frequency of CW forward-order currents, L1rMutual inductance between PW and rotor, L2rMutual inductance between CW and rotor, L1For PW from
Sense, L2For the self-induction of CW, LrFor the self-induction of rotor, R1For the phase resistance of PW, R2For the phase resistance of CW, RrFor the phase resistance of rotor；
It willWithThe expression formula that abc coordinate systems are transformed to from positive synchronous rotating frame is：
In the present invention, ωrIt can calculate as follows：
(1-1) sample motor rotor-position signal instantaneous value θr；
The θ of (1-2) to adjacent double samplingrCarry out calculus of differences；
(1-3) is filtered (1-2) result being calculated using low-pass first order filter, obtains motor speed ωr。
Further, the concrete methods of realizing of the step (5) is as follows：
Calculate the amplitude of PW voltage negative sequence componentsWith given amplitudeDifference, using the difference as the 5th PI tune
The input of device is saved, the output of the 5th pi regulator is CW electric current negative phase-sequence amplitude regulated quantitys With CW electric current negative phase-sequence amplitudes
Feedforward amountAddition obtains the given value of CW electric current negative phase-sequence amplitudes
Enable negative phase-sequence d axis component given value of the CW electric currents in negative synchronous rotating frameIt is equal toCW electric currents are calculated negative
Negative phase-sequence d components in sequence dq coordinate systemsWithDifference, using the difference as the input of the 6th pi regulator, the 6th PI
Output and negative phase-sequence d axis feedforward amount of the CW voltages in negative synchronous rotating frame of adjusterIt is added, obtains CW voltages in negative phase-sequence
Negative phase-sequence d axis given values in dq coordinate systems
Enable negative phase-sequence q axis component given value of the CW electric currents in negative synchronous rotating frameEqual to 0, CW electric currents are calculated in negative phase-sequence
Negative phase-sequence q components in dq coordinate systemsWithDifference, using the difference as the input of the 7th pi regulator, the 7th PI is adjusted
Output and negative phase-sequence q axis feedforward amount of the CW voltages in negative synchronous rotating frame of deviceIt is added, obtains CW voltages and sat in negative phase-sequence dq
Negative phase-sequence q axis given values in mark system
Finally use the phase of CW negative-sequence currentsIt willWithAbc coordinate systems are transformed to from negative synchronous rotating frame,
Obtain the CW three-phase voltage negative sequence component given values in abc coordinate systemsWith
Further, the CW electric currents negative phase-sequence amplitude feedforward amountNegative phase-sequence d axis of the CW voltages in negative synchronous rotating frame
Feedforward amountWith negative phase-sequence q component of the CW electric currents in negative synchronous rotating frameComputational methods be：
In formula,
In formula,
In formula,
WhereinFor the leakage inductance coefficient of CW, ωrFor motor speed, ω1For PW electric voltage frequencies,For CW negative phase-sequences
The frequency of electric current, L1rMutual inductance between PW and rotor, L2rMutual inductance between CW and rotor, L1For the self-induction of PW, L2For CW
Self-induction, LrFor the self-induction of rotor, R1For the phase resistance of PW, R2For the phase resistance of CW, RrFor the phase resistance of rotor.
It willWithThe expression formula that abc coordinate systems are transformed to from negative synchronous rotating frame is：
Further, the CW three-phase voltage given values in the step (6)WithIt is to be calculated by step (5)
Obtained CW three-phase voltage positive-sequence component given values are added with the CW three-phase voltage negative sequence component given values that step (6) is calculated
It obtains, expression formula is：
The advantageous effects of the present invention are embodied in：
Brushless dual-feed motor stand alone generating system excitation control method is under the conditions of asymmetric load provided by the present invention
Based on the double dq coordinate systems of positive and negative sequence, PW voltage positive-sequence component controllers are according to the positive-sequence component amplitude of PW voltages and giving for frequency
Definite value and value of feedback adjust CW voltage positive-sequence components, and PW voltage negative sequence component controllers are according to the negative sequence component amplitudes of PW voltages
Given value and value of feedback adjust CW voltage negative sequence components, and PW voltage negatives sequence controller need not be to the frequency of PW voltage negative sequence components
It is controlled, this is because the frequency of positive-sequence component and the frequency of negative sequence component are identical, if to the frequency of positive-sequence component
Good tracking is realized, then also realizing the tracking to negative sequence component frequency naturally.CW voltage positive and negative sequence components are added
CW voltage given values finally are obtained, PWM modulation signal are generated according to the given value, and then inverter is driven to control CW.
Balanced load is a kind of special circumstances of asymmetric load, and control method provided by the present invention can equally be well applied to balanced load
Under the conditions of brushless dual-feed motor stand alone generating system operation control.
Description of the drawings
Fig. 1 be the embodiment of the present invention asymmetric load under brushless dual-feed motor stand alone generating system excitation control method stream
Cheng Tu；
Fig. 2 is the functional block diagram that the embodiment of the present invention decomposes CW electric currents in positive-negative sequence rotating coordinate system；
Fig. 3 is the functional block diagram that the embodiment of the present invention decomposes PW electric currents in positive-negative sequence rotating coordinate system；
Fig. 4 is the PW voltage positive-sequence component controller principle block diagrams of the embodiment of the present invention；
Fig. 5 is the PW voltage negative sequence component controller principle block diagrams of the embodiment of the present invention；
Fig. 6 (a) is to use to control described in a kind of excitation controlling device of brushless dual-feed motor stand alone generating system of patent of invention
PW line voltage waveforms when method processed；
Fig. 6 (b) is to use to control described in a kind of excitation controlling device of brushless dual-feed motor stand alone generating system of patent of invention
CW phase current waveforms when method processed；
Fig. 7 (a) is the PW line voltage waveforms of the embodiment of the present invention；
Fig. 7 (b) is the CW phase current waveforms of the embodiment of the present invention.
Specific implementation mode
In order to make the purpose , technical scheme and advantage of the present invention be clearer, with reference to the accompanying drawings and embodiments, right
The present invention is further elaborated.It should be appreciated that the specific embodiments described herein are merely illustrative of the present invention, and
It is not used in the restriction present invention.
In embodiments of the present invention, as shown in Figure 1, including the following steps：
(1) sampling PW three-phase voltage instantaneous values u1a、u1bAnd u1c, PW electricity is calculated using double Second Order Generalized Integrator phaselocked loops
The amplitude of positive pressure order componentsAnd the amplitude of negative sequence component
(2) sampling CW three-phase current instantaneous values i2a、i2bAnd i2c, calculate positive sequence d, q of the CW electric currents in positive synchronous rotating frame
ComponentWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWith
(3) sampling PW three-phase current instantaneous values i1a、i1bAnd i1c, calculate positive sequence d, q of the PW electric currents in positive synchronous rotating frame
ComponentWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWith
(4) CW three-phase voltage positive-sequence component given values are calculated using PW voltage positive-sequence component controllers
With
(5) CW three-phase voltage negative sequence component given values are calculated using PW voltage negative sequence component controllers
With
(6) positive sequence of CW three-phase voltages is added to obtain CW three-phase voltage given values with negative sequence component given valueWithModulated signal is generated using SVPWM algorithms, and then inverter is made to export corresponding voltage to CW；
(7) repeat the above steps (1)~(6), and the amplitude of PW voltage positive-sequence components and frequency is made to track given value respectively, bears
The amplitude of order components converges to 0.
In embodiments of the present invention, as shown in Fig. 2, the specific implementation mode of step (2) is：
The phase of CW negative-sequence currents is calculated firstThen the phase of CW forward-order currents is usedIt will as reference angle
i2a、i2bAnd i2cPositive synchronous rotating frame is transformed to from abc coordinate system transformations, obtains d, q in positive synchronous rotating frame points of CW electric currents
AmountWithUsing the phase of CW negative-sequence currentsBy i2a、i2bAnd i2cFrom abc coordinate system transformation to negative synchronous rotating frame, obtain
To d, q component of the CW electric currents in negative synchronous rotating frameWithUse damped coefficient forTrap frequency is 2 times of PW electricity
Press the notch filter of rated frequency right respectivelyWithIt is filtered, obtains CW electric currents in positive synchronous rotating frame
In positive sequence d, q componentWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWith
In embodiments of the present invention, as shown in figure 3, the specific implementation mode of step (3) is：
The phase of PW forward-order currents is calculated firstWith the phase of PW negative-sequence currentsThen PW forward-order currents are used
PhaseBy i1a、i1bAnd i1cPositive synchronous rotating frame is transformed to from abc coordinate system transformations to obtainWithUsing PW negative-sequence currents
PhaseBy i1a、i1bAnd i1cNegative synchronous rotating frame is transformed to from abc coordinate system transformations to obtainWithUsing damped coefficient
ForTrap frequency is that the notch filter of 2 times of PW voltagerating frequencies is right respectivelyWithIt is filtered,
Obtain positive sequence d, q component of the PW electric currents in positive synchronous rotating frameWithAnd negative phase-sequence d, q in negative synchronous rotating frame point
AmountWith
In embodiments of the present invention, as shown in figure 4, the specific implementation mode of step (4) is：
Calculate the amplitude of PW voltage positive-sequence componentsWith given amplitudeDifference, using the difference as pi regulator 1
Input, the output of pi regulator 1 is CW electric current positive sequence amplitude regulated quantitys With CW electric current positive sequence amplitude feedforward amountsAddition obtains the given value of CW electric current positive sequence amplitudesCalculate PW electric voltage frequencies ω1With given frequencyDifference, will
The output of input of the difference as pi regulator 2, pi regulator 2 is CW power frequency regulated quantitys With CW electric currents
Frequency feedforward amountAddition obtains the frequency of CW forward-order currentsIt is rightIntegral obtains the phase of CW forward-order currentsIt enables
Positive sequence d axis component given value of the CW electric currents in positive synchronous rotating frameIt is equal toIt calculatesWithDifference, by the difference
It is worth the input as pi regulator 3, output and positive sequence d axis feedforward amount of the CW voltages in positive synchronous rotating frame of pi regulator 3It is added, obtains positive sequence d axis given value of the CW voltages in positive synchronous rotating frameEnable CW electric currents in positive synchronous rotating frame
In positive sequence q axis component given valuesEqual to 0, calculateWithDifference, using the difference as the defeated of pi regulator 4
Enter, output and positive sequence q axis feedforward amount of the CW voltages in positive synchronous rotating frame of pi regulator 4It is added, obtains CW voltages
Positive sequence q axis given values in positive synchronous rotating frameFinally use the phase of CW forward-order currentsIt willWithFrom
Positive synchronous rotating frame transforms to abc coordinate systems, obtains the CW three-phase voltage positive-sequence component given values in abc coordinate systemsWith
In embodiments of the present invention, as shown in figure 5, the specific implementation mode of step (5) is：
Calculate the amplitude of PW voltage negative sequence componentsWith given amplitudeDifference, using the difference as pi regulator 5
Input, the output of pi regulator 5 is CW electric current negative phase-sequence amplitude regulated quantitys With CW electric current negative phase-sequence amplitude feedforward amountsAddition obtains the given value of CW electric current negative phase-sequence amplitudesEnable negative phase-sequence d axis component of the CW electric currents in negative synchronous rotating frame to
Definite valueIt is equal toIt calculatesWithDifference, using the difference as the input of pi regulator 6, pi regulator 6 it is defeated
Go out the negative phase-sequence d axis feedforward amounts in negative synchronous rotating frame with CW voltagesIt is added, obtains CW voltages in negative synchronous rotating frame
Negative phase-sequence d axis given valuesEnable negative phase-sequence q axis component given value of the CW electric currents in negative synchronous rotating frameEqual to 0, calculateWithDifference, using the difference as the input of pi regulator 7, the output of pi regulator 7 is sat with CW voltages in negative phase-sequence dq
Negative phase-sequence q axis feedforward amounts in mark systemIt is added, obtains negative phase-sequence q axis given value of the CW voltages in negative synchronous rotating frame
Finally use the phase of CW negative-sequence currentsIt willWithAbc coordinate systems are transformed to from negative synchronous rotating frame, obtain abc seats
CW three-phase voltage negative sequence component given values in mark systemWith
In embodiments of the present invention, CW three-phase voltage positive-sequence component given values step (4) being calculatedThe CW three-phase voltage negative sequence component given values being calculated with step (5)
Corresponding be added obtains the CW three-phase voltage given values in step (6)With,Then it utilizes SVPWM algorithms to generate to adjust
Signal processed, and then inverter is made to export corresponding voltage to CW.
In the present embodiment, it is respectively 1 and 3, PW that the rated power of brushless dual-feed motor, which is the number of pole-pairs of 30kw, PW and CW,
Rated voltage with CW is respectively 380V and 320V, and the rated current of PW and CW are respectively 45A and 40A, synchronous rotational speed 750r/
Mutual inductance L between min, PW and rotor1rFor 0.1175H, the mutual inductance L between CW and rotor2rFor 0.3359H, the self-induction L of PW1For
The self-induction L of 0.4519H, CW2For 0.4977H, the self-induction L of rotorrFor 0.0366H, the phase resistance R of PW1For 2.73 Ω, the phase of CW
Resistance R2For 1.16 Ω, the phase resistance R of rotorrFor 0.1822 Ω.Used asymmetric load in the present embodiment, A phases are 25
Ω resistive loads, B phases and C phases are 100 Ω resistive loads.Brushless dual-feed motor output line voltage (i.e. PW voltages) virtual value
Given given value with frequency is respectively 380V, 50Hz, and the rotating speed of brushless dual-feed motor is maintained at 930rpm when being tested.
Fig. 6 (a) is to use to control described in a kind of excitation controlling device of brushless dual-feed motor stand alone generating system of patent of invention
PW line voltage waveforms when method processed.The ordinate of Fig. 6 (a) is PW line voltages, unit V；Abscissa is time, unit s.
Fig. 6 (b) is to use to control described in a kind of excitation controlling device of brushless dual-feed motor stand alone generating system of patent of invention
CW phase current waveforms when method processed.The ordinate of Fig. 6 (b) is CW phase currents, unit A；Abscissa is time, unit s.
Fig. 7 (a) is the PW line voltage waveforms of the embodiment of the present invention.The ordinate of Fig. 7 (a) is PW line voltages, unit V；
Abscissa is time, unit s.
Fig. 7 (b) is the CW phase current waveforms of the embodiment of the present invention.The ordinate of Fig. 7 (b) is CW phase currents, unit A；
Abscissa is time, unit s.
As shown in Fig. 6 (a), in brushless dual-feed motor stand alone generating system band asymmetric load, according to patent of invention
Control method described in a kind of excitation controlling device of brushless dual-feed motor stand alone generating system, PW line voltage waveforms occur it is serious not
Symmetrically.The asymmetry of PW voltages makes CW phase currents also produce distortion, such as Fig. 6 by the coupling of brushless double-fed machine rotor
(b) shown in.
As shown in Fig. 7 (a), in brushless dual-feed motor stand alone generating system band asymmetric load, according to institute of the present invention
Control method is stated, PW line voltage waveforms significantly improve.And CW phase currents show as being superimposed on the basis of fundamental wave centainly
The harmonic wave of amount, as shown in Fig. 7 (b).
As it will be easily appreciated by one skilled in the art that the foregoing is merely illustrative of the preferred embodiments of the present invention, not to
The limitation present invention, all within the spirits and principles of the present invention made by all any modification, equivalent and improvement etc., should all include
Within protection scope of the present invention.
Claims (8)
1. brushless dual-feed motor stand alone generating system excitation control method, feature exist under asymmetric load, include the following steps：
(1) sampling PW three-phase voltage instantaneous values u1a、u1bAnd u1c, PW voltages are being calculated just using double Second Order Generalized Integrator phaselocked loops
The amplitude of order componentsAnd the amplitude of negative sequence componentPW is power winding；
(2) sampling CW three-phase current instantaneous values i2a、i2bAnd i2c, calculate positive sequence d, q component of the CW electric currents in positive synchronous rotating frameWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWithCW windings in order to control；
(3) sampling PW three-phase current instantaneous values i1a、i1bAnd i1c, calculate positive sequence d, q component of the PW electric currents in positive synchronous rotating frameWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWith
(4) according to the amplitude of PW voltage positive-sequence componentsPositive sequence d, q component of the CW electric currents in positive synchronous rotating frameCW three-phase voltage positive-sequence component given values are calculated using PW voltage positive-sequence component controllers
With
(5) according to the amplitude of PW voltage negative sequence componentsNegative phase-sequence d, q component of the CW electric currents in negative synchronous rotating frameWithCW three-phase voltage negative sequence component given values are calculated using PW voltage negative sequence component controllersWith
(6) positive sequence of CW three-phase voltages is added to obtain CW three-phase voltage given values with negative sequence component given valueWithModulated signal is generated using SVPWM algorithms, and then inverter is made to export corresponding voltage to CW；
(7) repeat the above steps (1)~(6), and the amplitude of PW voltage positive-sequence components and frequency is made to track given value, negative phase-sequence point respectively
The amplitude of amount converges to 0.
2. brushless dual-feed motor stand alone generating system excitation control method under asymmetric load according to claim 1,
It is characterized in that, the specific implementation of the step (2) is：
The phase of CW negative-sequence currents is calculated first
Wherein, θ1For PW voltage positive-sequence component phases,For the phase of CW forward-order currents
Then the phase of CW forward-order currents is usedBy CW three-phase current instantaneous values i2a、i2bAnd i2cIt is converted from abc coordinate system transformations
To positive synchronous rotating frame, d, q component of the CW electric currents in positive synchronous rotating frame is obtainedWithUsing the phase of CW negative-sequence currents
PositionBy CW three-phase current instantaneous values i2a、i2bAnd i2cFrom abc coordinate system transformation to negative synchronous rotating frame, CW electric currents are obtained negative
D, q component in sequence dq coordinate systemsWithIt is as follows to convert expression formula：
It is right respectively using notch filterWithIt is filtered, obtains CW electric currents in positive synchronous rotating frame
Positive sequence d, q componentWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWith
3. brushless dual-feed motor stand alone generating system excitation control method under asymmetric load according to claim 2,
It is characterized in that, the concrete methods of realizing of the step (3) is：
The phase of PW forward-order currents is calculated firstWith the phase of PW negative-sequence currents
Wherein p1For the number of pole-pairs of power winding PW, p2The number of pole-pairs of winding CW in order to control, mechanical angles of the η between PW and CW
Deviation；
Then the phase of PW forward-order currents is usedBy PW three-phase current instantaneous values i1a、i1bAnd i1cFrom abc coordinate system transformations to just
Sequence dq coordinate systems obtainWithUsing the phase of PW negative-sequence currentsBy PW three-phase current instantaneous values i1a、i1bAnd i1cFrom abc
Coordinate system transformation transforms to negative synchronous rotating frame and obtainsWithIt is as follows to convert expression formula：
It is right respectively using notch filterWithIt is filtered, obtains PW electric currents in positive synchronous rotating frame
Positive sequence d, q componentWithAnd negative phase-sequence d, the q component in negative synchronous rotating frameWith
4. brushless dual-feed motor stand alone generating system excitation control method under asymmetric load according to claim 1,
It is characterized in that, the concrete methods of realizing of the step (4) is：
Calculate the amplitude of PW voltage positive-sequence componentsWith given amplitudeDifference, using the difference as the first pi regulator
The output of input, the first pi regulator is CW electric current positive sequence amplitude regulated quantitysWith CW electric current positive sequence amplitude feedforward amountsAddition obtains the given value of CW electric current positive sequence amplitudes
Calculate PW electric voltage frequencies ω1With given frequencyDifference, using the difference as the input of the second pi regulator, the 2nd PI
The output of adjuster is CW power frequency regulated quantitysWith CW power frequency feedforward amountsAddition obtains CW positive sequences
The frequency of electric currentIt is rightIntegral obtains the phase of CW forward-order currents
Enable positive sequence d axis component given value of the CW electric currents in positive synchronous rotating frameIt is equal toIt calculatesWithDifference
Value, using the difference as the input of third pi regulator, the output of third pi regulator and CW voltages are in positive synchronous rotating frame
Positive sequence d axis feedforward amountsIt is added, obtains positive sequence d axis given value of the CW voltages in positive synchronous rotating frame
Enable positive sequence q axis component given value of the CW electric currents in positive synchronous rotating frameEqual to 0, calculateWithDifference, will
Input of the difference as the 4th pi regulator, output and positive sequence of the CW voltages in positive synchronous rotating frame of the 4th pi regulator
Q axis feedforward amountsIt is added, obtains positive sequence q axis given value of the CW voltages in positive synchronous rotating frame
Finally use the phase of CW forward-order currentsIt willWithAbc coordinate systems are transformed to from positive synchronous rotating frame, are obtained
CW three-phase voltage positive-sequence component given values in abc coordinate systemsWith
5. brushless dual-feed motor stand alone generating system excitation control method under asymmetric load according to claim 4,
It is characterized in that, the CW electric currents positive sequence amplitude feedforward amountCW power frequency feedforward amountsCW voltage positive sequence d axis feedforward amountsWith CW voltage positive sequence q axis feedforward amountsComputational methods be：
In formula,
In formula,
In formula,
WhereinFor the leakage inductance coefficient of CW, ωrFor motor speed, ω1For PW electric voltage frequencies,For CW positive sequences
The frequency of electric current, L1rMutual inductance between PW and rotor, L2rMutual inductance between CW and rotor, L1For the self-induction of PW, L2For CW
Self-induction, LrFor the self-induction of rotor, R1For the phase resistance of PW, R2For the phase resistance of CW, RrFor the phase resistance of rotor, p1For power around
The number of pole-pairs of group PW, p2The number of pole-pairs of winding CW in order to control；
It willWithThe expression formula that abc coordinate systems are transformed to from positive synchronous rotating frame is：
6. brushless dual-feed motor stand alone generating system excitation control method under asymmetric load according to claim 1,
It is characterized in that, the concrete methods of realizing of the step (5) is as follows：
Calculate the amplitude of PW voltage negative sequence componentsWith given amplitudeDifference, using the difference as the 5th pi regulator
The output of input, the 5th pi regulator is CW electric current negative phase-sequence amplitude regulated quantitysWith CW electric current negative phase-sequence amplitude feedforward amountsAddition obtains the given value of CW electric current negative phase-sequence amplitudes
Enable negative phase-sequence d axis component given value of the CW electric currents in negative synchronous rotating frameIt is equal toCW electric currents are calculated in negative phase-sequence dq
Negative phase-sequence d components in coordinate systemWithDifference, using the difference as the input of the 6th pi regulator, the 6th PI is adjusted
Output and negative phase-sequence d axis feedforward amount of the CW voltages in negative synchronous rotating frame of deviceIt is added, obtains CW voltages and sat in negative phase-sequence dq
Negative phase-sequence d axis given values in mark system
Enable negative phase-sequence q axis component given value of the CW electric currents in negative synchronous rotating frameEqual to 0, calculates CW electric currents and sat in negative phase-sequence dq
Negative phase-sequence q components in mark systemWithDifference, using the difference as the input of the 7th pi regulator, the 7th pi regulator
Output with negative phase-sequence q axis feedforward amount of the CW voltages in negative synchronous rotating frameIt is added, obtains CW voltages in negative phase-sequence dq coordinates
Negative phase-sequence q axis given values in system
Finally use the phase of CW negative-sequence currentsIt willWithAbc coordinate systems are transformed to from negative synchronous rotating frame, are obtained
CW three-phase voltage negative sequence component given values in abc coordinate systemsWith
7. brushless dual-feed motor stand alone generating system excitation control method under asymmetric load according to claim 6,
It is characterized in that, the CW electric currents negative phase-sequence amplitude feedforward amountNegative phase-sequence d axis feedforward amount of the CW voltages in negative synchronous rotating frameWith negative phase-sequence q component of the CW electric currents in negative synchronous rotating frameComputational methods be：
In formula,
In formula,
In formula,
WhereinFor the leakage inductance coefficient of CW, ωrFor motor speed, ω1For PW electric voltage frequencies,For CW negative phase-sequences
The frequency of electric current, L1rMutual inductance between PW and rotor, L2rMutual inductance between CW and rotor, L1For the self-induction of PW, L2For CW
Self-induction, LrFor the self-induction of rotor, R1For the phase resistance of PW, R2For the phase resistance of CW, RrFor the phase resistance of rotor, p2In order to control around
The number of pole-pairs of group CW；
It willWithThe expression formula that abc coordinate systems are transformed to from negative synchronous rotating frame is：
8. brushless dual-feed motor stand alone generating system excitation control method under asymmetric load according to claim 1,
It is characterized in that, the CW three-phase voltage given values in the step (6)WithIt is the CW being calculated by step (4)
Three-phase voltage positive-sequence component given value is added to obtain with the CW three-phase voltage negative sequence component given values that step (5) is calculated,
Expression formula is：
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201611042019.8A CN106452235B (en) | 2016-11-21 | 2016-11-21 | Brushless dual-feed motor stand alone generating system excitation control method under asymmetric load |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201611042019.8A CN106452235B (en) | 2016-11-21 | 2016-11-21 | Brushless dual-feed motor stand alone generating system excitation control method under asymmetric load |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN106452235A CN106452235A (en) | 2017-02-22 |
| CN106452235B true CN106452235B (en) | 2018-11-06 |
Family
ID=58217992
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201611042019.8A Active CN106452235B (en) | 2016-11-21 | 2016-11-21 | Brushless dual-feed motor stand alone generating system excitation control method under asymmetric load |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN106452235B (en) |
Families Citing this family (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN108471263B (en) * | 2018-03-28 | 2019-09-27 | 华中科技大学 | The exciter control system of brushless dual-feed motor Independent Power Generation under a kind of nonlinear load |
| CN112436766B (en) * | 2020-12-03 | 2022-02-11 | 华中科技大学 | Load disturbance resisting control device and method for brushless doubly-fed generator |
| CN113517834B (en) * | 2021-07-14 | 2023-03-21 | 中国第一汽车股份有限公司 | Motor control method, device and system |
Family Cites Families (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1983785A (en) * | 2005-12-15 | 2007-06-20 | 中国科学院电工研究所 | Controller of exciting power-supply net sided converter for double-feedback speed-variable frequency-constant wind-driven generator |
| CN104865523A (en) * | 2015-01-22 | 2015-08-26 | 华北电力大学 | Doubly-fed generator simulation system and method |
| CN104980071B (en) * | 2015-07-07 | 2017-10-13 | 华中科技大学 | A kind of excitation controlling device of brushless dual-feed motor stand alone generating system |
| CN105024607B (en) * | 2015-07-14 | 2017-05-17 | 浙江大学 | Matrix converter excitation-based DFIG control method under unbalanced network voltage |
| CN105958534B (en) * | 2016-06-04 | 2018-04-13 | 重庆大学 | A kind of double-fed wind power system asymmetry high voltage fail traversing control method |
-
2016
- 2016-11-21 CN CN201611042019.8A patent/CN106452235B/en active Active
Also Published As
| Publication number | Publication date |
|---|---|
| CN106452235A (en) | 2017-02-22 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| Phan et al. | Control strategy for harmonic elimination in stand-alone DFIG applications with nonlinear loads | |
| Shao et al. | Dynamic control of the brushless doubly fed induction generator under unbalanced operation | |
| US9252601B2 (en) | Method for controlling a power converter in a wind turbine generator | |
| US8253393B2 (en) | Method and a controlling arrangement for controlling an AC generator | |
| US10491146B2 (en) | System and method for compensating for generator-induced flicker in a wind turbine | |
| CN104579060B (en) | The indirect power control method of cage-type rotor brushless dual-feedback wind power generator | |
| CN104980071A (en) | Excitation control device of brushless doubly-fed motor independent power generation system | |
| CN108448966B (en) | Negative sequence voltage suppression system of independent brushless doubly-fed generator under unbalanced load | |
| EP3494635A1 (en) | Control arrangement for a generator | |
| WO2013065512A1 (en) | Power conversion device | |
| CN106452235B (en) | Brushless dual-feed motor stand alone generating system excitation control method under asymmetric load | |
| CN106257821A (en) | A kind of variable speed permanent magnetism alternator system and voltage stabilizing control method thereof | |
| CN106452262B (en) | Independent brushless double feed influence generator Speedless sensor direct voltage control method | |
| Li et al. | Bidirectional harmonic current control of brushless doubly fed motor drive system based on a fractional unidirectional converter under a weak grid | |
| CN103986381B (en) | The microgrid of sea wave power generation system builds optimized power factor composite control method | |
| CN108039843A (en) | A kind of stator frequency control method of DFIG-DC systems | |
| CN107248744A (en) | Double feedback electric engine is based on pusher side and grid side converter coordinated passivity control method | |
| CN110086398A (en) | A kind of Direct Torque Control based on duty ratio control | |
| CN110198050A (en) | DFIG virtual synchronous control method based on the idle Collaborative Control of torque-under a kind of unbalanced power grid | |
| CN109494799A (en) | Based on the magneto alternator direct grid-connected system and its control method for opening winding construction | |
| CN109412478A (en) | A kind of power droop control method of brushless dual-feed motor | |
| CN104993756B (en) | The failure operation method of double-fed wind power generator rotor magnetic linkage weak magnetic control | |
| El Achkar et al. | Modeling and control of a stand alone cascaded doubly fed induction generator supplying an isolated load | |
| Hu et al. | A vector control strategy of grid-connected brushless doubly fed induction generator based on the vector control of doubly fed induction generator | |
| CN108964117A (en) | A kind of control method of the virtual synchronous generator with unbalanced load and its parallel connection |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |