CN112054674A - Power supply device for electric vehicle - Google Patents

Power supply device for electric vehicle Download PDF

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Publication number
CN112054674A
CN112054674A CN202010371184.8A CN202010371184A CN112054674A CN 112054674 A CN112054674 A CN 112054674A CN 202010371184 A CN202010371184 A CN 202010371184A CN 112054674 A CN112054674 A CN 112054674A
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CN
China
Prior art keywords
current
control circuit
power supply
inverter
frequency
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Granted
Application number
CN202010371184.8A
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Chinese (zh)
Other versions
CN112054674B (en
Inventor
河野佑介
河村恒毅
南贵彦
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Toshiba Corp
Toshiba Infrastructure Systems and Solutions Corp
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Toshiba Corp
Toshiba Infrastructure Systems and Solutions Corp
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Publication of CN112054674A publication Critical patent/CN112054674A/en
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Publication of CN112054674B publication Critical patent/CN112054674B/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4815—Resonant converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/72—Electric energy management in electromobility

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Electric Propulsion And Braking For Vehicles (AREA)
  • Inverter Devices (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention provides a power supply device for an electric vehicle, which can restrain ripple current. A power supply device for an electric vehicle according to an embodiment includes a plurality of high-frequency transformers, a plurality of step-up choppers, a plurality of inverters, and a control circuit. The plurality of step-up choppers step up a dc voltage supplied from a dc power supply. The plurality of inverters supply ac current to the high-frequency transformers using dc voltage supplied from the respective step-up choppers. The control circuit switches each of the boost choppers and each of the inverters so that a relationship between a switching phase of each of the boost choppers and a switching phase of each of the inverters is constant.

Description

Power supply device for electric vehicle
Technical Field
Embodiments of the present invention relate to a power supply device for an electric vehicle.
Background
An electric vehicle (moving object) includes a power supply device that converts a dc voltage supplied from a high-voltage electric vehicle line (e.g., an overhead electric vehicle line or a 3 rd track) into a voltage corresponding to a load and outputs the dc voltage to the load. For example, an electric vehicle includes, as a power supply device for an electric vehicle, a power supply device for driving a traveling motor and an auxiliary power supply device for supplying electric power to other devices such as lighting and air conditioning.
The auxiliary power supply device includes: a high-frequency transformer (insulation transformer) that is excited by a high-frequency alternating current; a boost chopper (boost chopper) for adjusting a direct-current voltage from the trolley wire; and an inverter for converting the output of the step-up chopper into a high-frequency alternating current and supplying the high-frequency alternating current to the high-frequency transformer. Further, the following power supply devices are also put into practical use: the inverter is provided with a plurality of sets of a high-frequency transformer, a step-up chopper, and an inverter, and by operating the plurality of inverters in different phases (phases), ripple current (ripple current) of power supplied to a load is suppressed.
However, due to the offset of the currents supplied to the plurality of transformers, there is a possibility that the amplitudes of the currents generated on the secondary side via the high-frequency transformer may vary, and the ripple current may increase.
Such a device is disclosed in japanese laid-open patent publication and japanese laid-open patent publication No. 2014-233121 (hereinafter, referred to as patent document 1).
Disclosure of Invention
The present invention addresses the problem of providing a power supply device for an electric vehicle, which can suppress ripple current.
A power supply device for an electric vehicle according to an embodiment includes a plurality of high-frequency transformers, a plurality of step-up choppers, a plurality of inverters, and a control circuit. The plurality of step-up choppers step up a dc voltage supplied from a dc power supply. The plurality of inverters supply ac current to the high-frequency transformers using the dc voltage supplied from each of the step-up choppers. The control circuit switches the respective boost choppers and the respective inverters so that a relationship between a switching (switching) phase of the respective boost choppers and a switching phase of the respective inverters is constant.
Drawings
Fig. 1 is a diagram for explaining an example of the configuration of an electric power supply device for an electric vehicle according to embodiment 1.
Fig. 2 is an explanatory diagram for explaining an example of the operation of the control circuit of the electric power supply device for an electric vehicle according to embodiment 1.
Fig. 3 is an explanatory diagram for explaining an example of an output current of the electric power supply device for an electric vehicle according to embodiment 1.
Fig. 4 is an explanatory diagram for explaining another example of the output current of the electric power supply device for an electric vehicle according to embodiment 1.
Fig. 5 is an explanatory diagram for explaining an example of the operation of the control circuit of the electric power supply device for an electric vehicle according to embodiment 1.
Fig. 6 is an explanatory diagram for explaining an example of the configuration of the control circuit of the electric power supply device for an electric vehicle according to embodiment 1.
Fig. 7 is an explanatory diagram for explaining an example of the configuration of the control circuit of the electric power supply device for an electric vehicle according to embodiment 1.
Fig. 8 is an explanatory diagram for explaining an example of the operation of the control circuit of the electric power supply device for an electric vehicle according to embodiment 1.
Fig. 9 is an explanatory diagram for explaining an example of the operation of the control circuit of the electric power supply device for an electric vehicle according to embodiment 1.
Fig. 10 is a diagram for explaining an example of the configuration of the electric vehicle power supply device according to embodiment 2.
Description of the symbols
1: a power supply device for an electric vehicle; 1A: a power supply device for an electric vehicle; 2: a trolley wire; 3: a current collector; 4: a load; 5: a line; 11: a boost circuit; 11A: a boost circuit; 12: a power conversion circuit; 13: a current detector; 14: a control circuit; 14A: a control circuit; 21: 1 st boost chopper; 22: a 2 nd boost chopper; 31: a 1 st resonant inverter; 32: 1 st high frequency transformer; 33: a 1 st rectifier; 34: a 2 nd resonant inverter; 35: a 2 nd high frequency transformer; 36: a 2 nd rectifier; 71: an FET analysis section; 72: an operation switching determination unit; 73: a band-pass filter; c1: a 1 st capacitor; c2: a 2 nd capacitor; c3: a 3 rd capacitor; c4: a 4 th capacitor; c5: a 5 th capacitor; c6: a 6 th capacitor; c7: a filter capacitor; c8: a filter capacitor; d1: a 1 st diode; d2: a 2 nd diode; s1: a 1 st switch; s2: a 2 nd switch; s3: a 3 rd switch; s4: a 4 th switch; s5: a 5 th switch; s6: and 6 th switch.
Detailed Description
Hereinafter, embodiments will be described with reference to the drawings.
(embodiment 1)
Fig. 1 is an explanatory diagram showing a configuration example of an electric power supply device 1 for an electric vehicle according to embodiment 1. The power supply device 1 for an electric vehicle is mounted on a mobile body such as an electric vehicle. The electric vehicle power supply device 1 receives dc power from a power line 2 such as an overhead power line or a 3 rd track via a collector 3, and outputs the received dc power from an output terminal 4. In the present embodiment, a case will be described where the electric vehicle power supply device 1 is an auxiliary power supply device that supplies power to a load such as lighting and air conditioning of an electric vehicle. The electric vehicle includes a main power supply device, not shown, for driving the electric motor for running. The main power supply device drives the electric motor for running by using the dc power received from the trolley wire 2 via the collector 3, thereby running the electric vehicle on the line 5.
A device that operates at a lower voltage than the electric motor for running is connected to the electric power supply device 1 for electric vehicle as an auxiliary power supply device. Therefore, the power supply device 1 for an electric vehicle needs to insulate the primary side to which electric power is input and the secondary side from which electric power is output.
In order to ensure insulation between the primary side and the secondary side, there is a transformer in which the primary side and the secondary side are insulated using a transformer provided with a pair of windings (coils) that are electromagnetically coupled. The lower the excitation frequency, the larger the transformer. For example, a transformer set to an excitation frequency corresponding to the frequency of a commercial power supply is large. Therefore, the power supply device 1 for an electric vehicle according to the present embodiment is designed to insulate the primary side and the secondary side by using a high-frequency transformer, and to be compact.
First, the configuration of the power supply device 1 for an electric vehicle will be described.
The electric vehicle power supply device 1 includes a booster circuit 11 and a power conversion circuit 12. Further, the power supply device 1 for an electric vehicle includes: a current detector 13 that detects a current flowing in the output terminal; and a control circuit 14 that controls the booster circuit 11 and the power conversion circuit 12.
The booster circuit 11 boosts the dc power input from the trolley wire 2 via the collector 3. The booster circuit 11 includes a booster reactor (reactor) L, a 1 st boost chopper 21, and a 2 nd boost chopper 22. The booster circuit 11 may further include a filter capacitor and a reactor that constitute an LCL filter (filter) together with the booster reactor L.
The 1 st boost chopper 21 includes a 1 st switch (switch) S1 and a 1 st diode D1. The 1 st boost chopper 21 controls the current flowing through the boost reactor L by ON/OFF controlling (ON/OFF controlling) the 1 st switch S1 based ON the control of the control circuit 14. Thereby, the 1 st step-up chopper 21 outputs a dc voltage boosted by electromagnetic energy (electro-magnetic energy) accumulated in the step-up reactor L. The 1 st boost chopper 21 may include a smoothing capacitor for stabilizing the output dc voltage.
The 2 nd boost chopper 22 includes a 2 nd switch S2 and a 2 nd diode D2. The 2 nd boost chopper 22 controls the current flowing through the boost reactor L by on-off controlling the 2 nd switch S2 based on the control of the control circuit 14. Thereby, the 2 nd step-up chopper 22 outputs a dc voltage boosted by the electromagnetic energy stored in the step-up reactor L. The 2 nd boost chopper 22 may also include a smoothing capacitor for stabilizing the output dc voltage.
The power conversion circuit 12 converts the dc power output from the voltage boost circuit 11 into power for a dc load. The power conversion circuit 12 includes, for example, a 1 st resonant inverter 31, a 1 st high-frequency transformer 32, a 1 st rectifier 33, a 1 st capacitor C1, a 2 nd resonant inverter 34, a 2 nd high-frequency transformer 35, a 2 nd rectifier 36, and a 2 nd capacitor C2.
The 1 st resonant inverter 31 is an inverter circuit that uses the dc voltage supplied from the 1 st step-up chopper 21 to flow an ac current (an inverter current, a single-phase ac current, or the like) to the 1 st high-frequency transformer 32. The 1 st resonant inverter 31 is configured as a resonant single-phase half-bridge inverter (half bridge inverter), for example. The 1 st resonant inverter 31 includes a 3 rd switch S3, a 4 th switch S4, a 3 rd capacitor C3, and a 4 th capacitor C4. A 1 st high frequency transformer 32 is connected to a connection point between the 3 rd switch S3 and the 4 th switch S4 and a connection point between the 3 rd capacitor C3 and the 4 th capacitor C4. The 1 st resonant inverter 31 controls ON/OFF (ON/OFF) of the 3 rd switch S3 and the 4 th switch S4 under the control of the control circuit 14, thereby supplying an alternating current to the 1 st high-frequency transformer 32. The side of switch S3 of resonant inverter 31 1 at position 3 is referred to as the upper arm (arm) of resonant inverter 31 at position 1, and the side of switch S4 of resonant inverter 31 at position 4 is referred to as the lower arm of resonant inverter 31 at position 1. The 1 st resonant inverter 31 may further include a smoothing capacitor C7 for smoothing the dc power supplied from the 1 st boost chopper 21.
The 1 st high-frequency transformer 32 is an insulation transformer (insulation transformer) having a primary winding (primary winding) that generates magnetic flux (flux), and a secondary winding (secondary winding) that is insulated from the primary winding and excited by the magnetic flux generated by the primary winding. When an ac current is supplied from the 1 st resonant inverter 31 to the primary winding of the 1 st high-frequency transformer 32, a magnetic flux is generated in the primary winding. The magnetic flux generated by the primary winding induces an induced current in the secondary winding. Thus, the 1 st high-frequency transformer 32 supplies power to the secondary side in accordance with the ac current input from the primary side.
The 1 st rectifier 33 is a circuit that rectifies (rectify) the electric power generated in the secondary winding of the 1 st high-frequency transformer 32. The 1 st rectifier 33 is configured as a bridge (bridge) composed of a plurality of diodes, for example.
The 1 st capacitor C1 smoothes (smoothing) the positive voltage supplied from the 1 st rectifier 33. The 1 st capacitor C1 outputs a dc voltage from the output terminal 4 connected in parallel.
The 2 nd resonant inverter 34 is an inverter circuit that uses the dc voltage supplied from the 2 nd step-up chopper 22 to flow an ac current (an inverter current, a single-phase ac current, or the like) to the 2 nd high-frequency transformer 35. The 2 nd resonant inverter 34 is configured as a resonant single-phase half-bridge inverter (half bridge inverter), for example. The 2 nd resonant inverter 34 includes a 5 th switch S5, a 6 th switch S6, a 5 th capacitor C5, and a 6 th capacitor C6. A 2 nd high frequency transformer 35 is connected to a connection point between the 5 th switch S5 and the 6 th switch S6 and a connection point between the 5 th capacitor C5 and the 6 th capacitor C6. The 2 nd resonant inverter 34 controls the 5 th switch S5 and the 6 th switch S6 to be turned on and off under the control of the control circuit 14, thereby supplying an ac current to the 2 nd high-frequency transformer 35. The side of the 5 th switch S5 of the 2 nd resonant inverter 34 is referred to as the upper arm of the 2 nd resonant inverter 34, and the side of the 6 th switch S6 of the 2 nd resonant inverter 34 is referred to as the lower arm of the 2 nd resonant inverter 34. The 2 nd resonant inverter 34 may also include a smoothing capacitor C8 that smoothes the dc power supplied from the 2 nd boost chopper 22.
The 2 nd high-frequency transformer 35 is an insulating transformer having a primary side winding (primary winding) that generates magnetic flux, and a secondary side winding (secondary winding) that is insulated from the primary winding and excited by the magnetic flux generated by the primary winding. When an ac current is supplied from the 2 nd resonant inverter 34 to the primary winding of the 2 nd high-frequency transformer 35, a magnetic flux is generated in the primary winding. The magnetic flux generated by the primary winding induces an induced current in the secondary winding. Thereby, the 2 nd high-frequency transformer 35 supplies power to the secondary side in accordance with the ac current input from the primary side.
The 2 nd rectifier 36 is a circuit for rectifying electric power generated in the secondary winding of the 2 nd high-frequency transformer 35. The 2 nd rectifier 36 is configured as a rectifier bridge composed of a plurality of diodes, for example.
The 2 nd capacitor C2 smoothes the positive voltage supplied from the 2 nd rectifier 36. The 2 nd capacitor C2 outputs a dc voltage from the output terminal 4 connected in parallel. With this configuration, the sum of the dc voltages from the 1 st capacitor C1 and the 2 nd capacitor C2 is output from the output terminal 4. The dc power output from the output terminal 4 is converted into 50Hz or 60Hz ac power by a circuit such as an inverter, not shown.
The current detector 13 detects a current value of the current output from the output terminal 4, and supplies the detection result to the control circuit 14. The current detector 13 can detect a current value at any position as long as it is closer to the output terminal 4 than the connection point of the 1 st capacitor C1 and the 2 nd capacitor C2.
The control circuit 14 controls the booster circuit 11 and the power conversion circuit 12. The control circuit 14 is configured as a logic circuit that generates a pulse signal (pulse signal), for example. Further, the control circuit 14 may be configured to include: a processor (processor) which is an arithmetic element for executing arithmetic processing; and a memory (memory) that stores a program (program) and data (data) used in the program, and generates a pulse signal by the processor executing the program.
The control circuit 14 inputs a pulse signal (pulse signal) to the booster circuit 11 and the power conversion circuit 12, respectively, to thereby control the operations of the booster circuit 11 and the power conversion circuit 12. For example, the control circuit 14 performs PWM (Pulse Width Modulation) control for adjusting an ON/OFF duty ratio (ON/OFF duty ratio) of the Pulse signal. Thereby, the control circuit 14 adjusts the output of the booster circuit 11 and the output of the power conversion circuit 12, respectively.
As described above, the control circuit 14 supplies the pulse signal to the 1 st resonant inverter 31 and the 2 nd resonant inverter 34. Thereby, the control circuit 14 converts the dc power supplied from the trolley wire 2 into ac power, and outputs inverter currents from the 1 st resonant inverter 31 and the 2 nd resonant inverter 34, respectively.
Further, the dc voltage supplied from the trolley wire 2 may be unstable. Therefore, the control circuit 1 supplies a pulse signal to the 1 st boost chopper 21 and the 2 nd boost chopper 22 of the boost circuit 11. Thus, the control circuit 14 controls the supply of stable dc voltages from the 1 st boost chopper 21 to the 1 st resonant inverter 31 and from the 2 nd boost chopper 22 to the 2 nd resonant inverter 34, respectively.
Fig. 2 is an explanatory diagram for explaining the operation of the control circuit 14.
The control circuit 14 is input with a voltage command 41 and a triangular wave 42. The voltage command 41 is a control signal (voltage value) supplied from a driver's cab of the electric vehicle or a control device that controls the travel of the electric vehicle. The triangular wave (triangular or radial wave)42 is a triangular wave supplied from a driver's cab of the electric vehicle, a control device that controls traveling of the electric vehicle, or another circuit that outputs a carrier wave. The control circuit 14 may be configured to generate the triangular wave 42 by itself.
Based ON the voltage command 41 and the triangular wave 42, the control circuit 14 generates a 1 st step-up chopper ON/OFF (chopper ON/OFF) command 43, a 2 nd step-up chopper ON/OFF command 44, a 1 st resonant inverter upper arm ON/OFF command 45, a 1 st resonant inverter lower arm ON/OFF (arm ON/OFF) command 46, a 2 nd resonant inverter upper arm ON/OFF command 47, and a 2 nd resonant inverter lower arm ON/OFF command 48.
The 1 st boost chopper on-off command 43 is a pulse signal for on-off controlling the 1 st switch S1 of the 1 st boost chopper 21. The control circuit 14 generates a 1 st step-up chopper on/off command 43 based on the result of comparison between the voltage command 41 and the triangular wave 42. For example, the control circuit 14 generates the following 1 st boost chopper on-off command 43: at a timing (timing) when the voltage command 41 is equal to or higher than the triangular wave 42, the 1 st step-up chopper 21 is turned on, and at a timing when the voltage command 41 is lower than the triangular wave 42, the 1 st step-up chopper 21 is turned off. The control circuit 14 supplies the 1 st boost chopper on/off command 43 to the 1 st boost chopper 21.
The 1 st resonant inverter upper arm on/off command 45 is a pulse signal for on/off control of the 3 rd switch S3, which is the upper arm of the 1 st resonant inverter 31. The control circuit 14 generates a 1 st resonant inverter upper arm on-off command 45 based on the triangular wave 42. For example, control circuit 14 generates 1 st resonant inverter upper arm on/off command 45 having the same frequency as triangular wave 42. That is, the frequency of the 1 st resonant inverter upper arm on-off command 45 is the same as the frequency of the 1 st boost chopper on-off command 43. More specifically, the control circuit 14 generates the following 1 st resonant inverter upper arm on-off command 45: triangular wave 42 is compared with a predetermined fixed value, and the upper arm of 1 st resonant inverter 31 is turned on at a timing when the fixed value is equal to or higher than triangular wave 42, and the lower arm of 1 st resonant inverter 31 is turned on at a timing when the fixed value is lower than triangular wave 42. The fixed value is set so that the on/off duty of the 1 st resonant inverter upper arm on/off command 45 becomes 50%. The control circuit 14 supplies the 1 st resonant inverter upper arm on/off command 45 to the 3 rd switch S3.
The 1 st resonant inverter lower arm on/off command 46 is a pulse signal for on/off control of the 4 th switch S4, which is the lower arm of the 1 st resonant inverter 31. Control circuit 14 generates a 1 st resonant inverter lower arm on-off command 46 by reversing the 1 st resonant inverter upper arm on-off command 45. That is, the frequency of the 1 st resonant inverter lower arm on-off command 46 is the same as the frequency of the 1 st boost chopper on-off command 43. The control circuit 14 supplies the 1 st resonant inverter lower arm on/off command 46 to the 4 th switch S4.
The 2 nd boost chopper on-off command 44 is a pulse signal for on-off controlling the 2 nd switch S2 of the 2 nd boost chopper 22. The control circuit 14 generates a 2 nd boost chopper on/off command 44 by shifting the phase of the 1 st boost chopper on/off command 43. For example, the control circuit 14 generates the 2 nd boost chopper on-off command 44 by shifting the phase of the 1 st boost chopper on-off command 43 by 180 degrees. The control circuit 14 supplies the 2 nd boost chopper on/off command 44 to the 2 nd boost chopper 22.
The 2 nd resonant inverter upper arm on/off command 47 is a pulse signal for on/off control of the 5 th switch S5, which is the upper arm of the 2 nd resonant inverter 34. Control circuit 14 generates 2 nd resonant inverter upper arm on-off command 47 by shifting the phase of 1 st resonant inverter upper arm on-off command 45. That is, the frequency of the 2 nd resonant inverter upper arm on-off command 47 is the same as the frequency of the 2 nd boost chopper on-off command 44. For example, the control circuit 14 generates the 2 nd resonant inverter upper arm on/off command 47 by shifting the phase of the 1 st resonant inverter upper arm on/off command 45 by 90 degrees. Control circuit 14 supplies 2 nd resonant inverter upper arm on/off command 47 to 5 th switch S5.
The 2 nd resonant inverter lower arm on/off command 48 is a pulse signal for on/off controlling the 6 th switch S6, which is the lower arm of the 2 nd resonant inverter 34. Control circuit 14 generates a 2 nd resonant inverter lower arm on-off command 48 by reversing the 2 nd resonant inverter upper arm on-off command 47. That is, the frequency of the 2 nd resonant inverter lower arm on-off command 48 is the same as the frequency of the 2 nd boost chopper on-off command 44. The control circuit 14 supplies the 2 nd resonant inverter lower arm on/off command 48 to the 6 th switch S6.
As described above, control circuit 14 operates 1 st step-up chopper 21 and 1 st resonant inverter 31 at the same switching frequency, and operates 2 nd step-up chopper 22 and 2 nd resonant inverter 34 at the same switching frequency. The control circuit 14 shifts the phase of the 1 st step-up chopper 21 and the 2 nd step-up chopper 22 by 180 degrees. Further, control circuit 14 shifts the phase by 90 degrees in 1 st resonant inverter 31 and 2 nd resonant inverter 34.
The control circuit 14 supplies the 1 st step-up chopper on/off command 43 to the 1 st step-up chopper 21, the 1 st resonant inverter upper arm on/off command 45 to the 3 rd switch S3, and the 1 st resonant inverter lower arm on/off command 46 to the 4 th switch S4, thereby supplying the inverter current to the 1 st high-frequency transformer 32. This generates ac power on the secondary side of the 1 st high-frequency transformer 32. Graph (graph)51 of fig. 2 shows an example of the alternating current generated on the secondary side of the 1 st high-frequency transformer 32.
The control circuit 14 supplies the 2 nd boost chopper on/off command 44 to the 2 nd boost chopper 22, the 2 nd resonant inverter upper arm on/off command 47 to the 5 th switch S5, and the 2 nd resonant inverter lower arm on/off command 48 to the 6 th switch S6, thereby supplying the inverter current to the 2 nd high frequency transformer 35. Thereby, ac power is generated on the secondary side of the 2 nd high-frequency transformer 35. Graph 52 of fig. 2 shows an example of an alternating current generated on the secondary side of the 2 nd high-frequency transformer 35.
Fig. 3 is an explanatory diagram for explaining a relationship between an alternating current generated on the secondary side of the 1 st high-frequency transformer 32 and the secondary side of the 2 nd high-frequency transformer 35 and a current output from the output terminal 4.
The alternating current generated on the secondary side of the 1 st high-frequency transformer 32 shown in the 1 st graph 51 is rectified by the 1 st rectifier 33. As a result, as shown in the 3 rd graph 53, the 1 st rectifier 33 outputs a pulsating current (1 st pulsating current) whose negative amplitude is converted to positive amplitude.
Further, the alternating current generated on the secondary side of the 2 nd high-frequency transformer 35 shown in the 2 nd graph 52 is rectified by the 2 nd rectifier 36. As a result, as shown in the 4 th graph 54, the 2 nd rectifier 36 outputs a pulsating current (2 nd pulsating current) whose negative side amplitude is converted into positive side amplitude.
The 5 th graph 55 of fig. 3 shows the current obtained by adding the 1 st ripple current to the 2 nd ripple current. The 1 st ripple current is a harmonic (doubleharmony) of 2 times the switching frequency of the 1 st resonant inverter 31, and has two peaks (peaks) in 1 cycle. The 2 nd ripple current is a higher harmonic of 2 times the switching frequency of the 2 nd resonant inverter 34, and has two peaks (peak) in one cycle. The phase of the 1 st pulsating current and the phase of the 2 nd pulsating current are different by 90 degrees. Therefore, when the 1 st ripple current and the 2 nd ripple current are added, the valley of the 1 st ripple current overlaps the peak of the 2 nd ripple current. As a result, the current shown in the graph 55 of fig. 5 is a harmonic wave of a multiple of 4 with the harmonic wave of a multiple of 2 cancelled out. That is, the current shown in the 5 th graph 55 has 4 peaks (peaks) in one cycle. The ripple current of the current shown in the 5 th graph 55 is suppressed compared to the 1 st ripple current and the 2 nd ripple current.
In practice, the 1 st ripple current is smoothed by the 1 st capacitor C1, the 2 nd ripple current is smoothed by the 2 nd capacitor C2, and the smoothed 1 st ripple current and the 2 nd ripple current are added and output from the output terminal 4. That is, the current shown in the 5 th graph 55 is smoothed by the 1 st capacitor C1 and the 2 nd capacitor C2 and is output from the output terminal 4.
As described above, the electric power supply device 1 for an electric vehicle according to embodiment 1 includes: a plurality of high-frequency transformers (a 1 st high-frequency transformer 32 and a 2 nd high-frequency transformer 35); a plurality of step-up choppers (1 st step-up chopper 21 and 2 nd step-up chopper 22), a plurality of inverters (1 st resonance inverter 31 and 2 nd resonance inverter 34), and a control circuit 14. The control circuit 14 controls the switching timing of each switch of the resonant inverter and the switching timing of the switch of the boost chopper to be constant for each cycle of the switching of the resonant inverter. That is, the control circuit 14 switches the respective boost choppers and the respective resonant inverters so that the relationship between the switching phase of the respective boost choppers and the switching phase of the respective resonant inverters becomes constant.
Thus, the power supply device 1 for an electric vehicle can maintain a state in which the peaks and troughs of the currents output from the secondary sides of the plurality of high-frequency transformers cancel each other out. This can suppress a ripple current of a current generated on the secondary side via the high-frequency transformer. Further, this makes it possible to reduce the size of the smoothing capacitor for smoothing the current generated on the secondary side via the high-frequency transformer and the filter reactor (filter reactor) connected to the output terminal 4 and thereafter.
Further, control circuit 14 switches 1 st boost chopper 21 and 2 nd boost chopper 22 with a phase shift of 180 degrees, and switches 1 st resonant inverter 31 and 2 nd resonant inverter 34 with a phase shift of 90 degrees. Thus, the valley of the current generated on the secondary side of the 1 st high-frequency transformer 32 overlaps the peak of the current generated on the secondary side of the 2 nd high-frequency transformer 35. As a result, a ripple current that generates a current on the secondary side via the high-frequency transformer can be suppressed.
In the above embodiment, the balance between the ac current supplied from the 1 st resonant inverter 31 to the 1 st high-frequency transformer 32 and the ac current supplied from the 2 nd resonant inverter 34 to the 2 nd high-frequency transformer 35 may be shifted for various reasons. The reason for this is, for example, deterioration of the element, variation in temperature distribution in the circuit, and the like.
When the balance (balance) between the ac current supplied to the 1 st high-frequency transformer 32 and the ac current supplied to the 2 nd high-frequency transformer 35 is shifted, the balance of the ac current on the secondary side is also shifted.
Fig. 4 is an explanatory diagram for explaining an example in which the balance of the alternating current generated on the secondary side of the 1 st high-frequency transformer 32 and the secondary side of the 2 nd high-frequency transformer 35 is shifted.
Graph 61 of fig. 4 shows the alternating current generated on the secondary side of the 1 st high frequency transformer 32. Graph 62 of fig. 4 shows the ac current generated on the secondary side of the 2 nd high frequency transformer 35. The maximum value of the amplitude of the 2 nd graph 62 is lower than that of the 1 st graph 61. This is because, when the ac currents supplied to the plurality of transformers vary from one transformer to another, a difference occurs between the maximum value of the amplitude of the ac current generated on the secondary side of the 1 st high-frequency transformer 32 and the maximum value of the amplitude of the ac current generated on the secondary side of the 2 nd high-frequency transformer 35.
The alternating current generated on the secondary side of the 1 st high-frequency transformer 32 shown in the 1 st graph 61 of fig. 4 is rectified by the 1 st rectifier 33. As a result, as shown in the 3 rd graph 63, the 1 st rectifier 33 outputs a pulsating current (1 st pulsating current) whose negative side amplitude is converted into positive side amplitude.
Further, the alternating current generated on the secondary side of the 2 nd high-frequency transformer 35 shown in the 2 nd graph 62 is rectified by the 2 nd rectifier 36. As a result, as shown in the 4 th graph 64, the 2 nd rectifier 36 outputs a pulsating current (2 nd pulsating current) whose negative side amplitude is converted into positive side amplitude. As shown in the 3 rd curve 63 and the 4 th curve 64 of fig. 4, the maximum values of the amplitudes of the 1 st ripple current and the 2 nd ripple current are different from each other.
A 5 th curve 65 in fig. 4 shows a current obtained by adding the 1 st ripple current of the 3 rd curve 63 to the 2 nd ripple current of the 4 th curve 64. The 1 st ripple current is a harmonic of 2 times the switching frequency of the 1 st resonant inverter 31, and has two peaks (peaks) in 1 cycle. The 2 nd ripple current is a higher harmonic of 2 times the switching frequency of the 2 nd resonant inverter 34, and has two peaks in one cycle. The phase of the 1 st pulsating current is 90 degrees different from that of the 2 nd pulsating current. Therefore, in the case of adding the 1 st ripple current and the 2 nd ripple current, the valley of the 1 st ripple current overlaps the peak of the 2 nd ripple current. However, the maximum value of the amplitude of the 2 nd ripple current in the 4 th graph 64 is lower than the maximum value of the amplitude of the 1 st ripple current in the 3 rd graph 63. Therefore, the 2 times higher harmonic of the current shown in graph 55 of fig. 5 is not cancelled. That is, the valley of the 1 st pulsating current is not cancelled by the peak of the 2 nd pulsating current. As a result, the current shown in curve 5, curve 55, has a waveform having a plurality of peaks (peaks) and a plurality of troughs in one cycle.
In practice, the 1 st ripple current is smoothed by the 1 st capacitor C1, the 2 nd ripple current is smoothed by the 2 nd capacitor C2, and the smoothed 1 st ripple current and the 2 nd ripple current are added and output from the output terminal 4. That is, the current shown in the 5 th graph 55 is smoothed by the 1 st capacitor C1 and the 2 nd capacitor C2 and is output from the output terminal 4. However, the 1 st capacitor C1 and the 2 nd capacitor C2 are configured to smooth currents having harmonics of 4 times by canceling the troughs of the 1 st ripple current with the peaks of the 2 nd ripple current. Therefore, as shown in the 5 th graph 65 of fig. 4, there is a possibility that a smoothing residue of the 1 st capacitor C1 and the 2 nd capacitor C2 occurs in the current in which the 2 nd harmonic is not cancelled.
Therefore, the control circuit 14 may change the control constants of the booster circuit 11 and the power converter circuit 12 (switching frequency, phase difference, and the like of the power converter circuit 12) based on the detection result supplied from the current detector 13.
Fig. 5 is an explanatory diagram for explaining control in the control circuit 14.
The control circuit 14 acquires the detection result of the current from the current detector 13 (step S11). As a result of detection of the current supplied from the current detector 13, the 5 th graph 65 of fig. 4 shows the current smoothed by the 1 st capacitor C1 and the 2 nd capacitor C2. The control circuit 14 obtains the detection result supplied from the current detector 13 for a predetermined amount of time.
The control circuit 14 analyzes the detection result of the current supplied from the current detector 13 (step) S12). When the detection result of the current is analyzed, the control circuit 14 determines whether or not the continuous operation is possible (step S13). The control circuit 14 determines whether or not to change the control constant (step S14).
When it is determined that the operation can be continued (yes in step S13) and the control constant is changed (yes in step S14), the control circuit 14 changes the control constant (step S15).
When the control constant is changed in step S15 or when it is determined in step S14 that the control constant is not changed (no in step S14), the control circuit 14 determines whether or not to stop the operation of the electric vehicle power supply device 1 (step S16). For example, the control circuit 14 determines that the operation of the electric power supply device 1 for an electric vehicle is stopped when a signal instructing the end of the operation is received from a driver's seat, not shown. If it is determined that the operation of the electric-powered-vehicle power supply device 1 is not to be stopped (no in step S16), the control circuit 14 proceeds to step S11 and continues the analysis of the current detection result.
If it is determined in step S13 that the continuous operation is not possible (no in step S13) or if it is determined in step S16 that the operation of the electric vehicle power supply device 1 is stopped (yes in step S16), the control circuit 14 stops the operation of the electric vehicle power supply device 1 (step S17) and ends the processing of fig. 5.
As described above, the control circuit 14 changes the control constant when it is determined that the operation of the electric power supply device 1 for an electric vehicle can be continued if the control constant is changed based on the analysis result of the current value. That is, control circuit 14 changes any control constant of the switching frequency of power conversion circuit 12, the phase difference between the switches of 1 st resonant inverter 31 and the switches of 2 nd resonant inverter 34, and the like.
Next, the analysis of the detection result of the current in step S12, the determination of whether or not the continuous operation is possible in step S13, and the determination of whether or not the control constant is changed in step S14 will be described.
Fig. 6 shows an example of the configuration of the control circuit 14 for analyzing the current. For example, in the example of fig. 6, the control circuit 14 includes a Fast Fourier Transform (FET) analysis unit 71 and an operation switching determination unit 72. Fig. 7 shows another example of the configuration of the control circuit 14 for analyzing the current. In the example of fig. 7, for example, the control circuit 14 includes a band-pass filter (band-pass filter)73 and an operation switching determination unit 72.
The FET analysis unit 71 is a circuit that performs fourier transform on an input signal and outputs the result. The FET analysis section 71 performs fourier transform on the detection result (current detection value) of the current supplied from the current detector 13, and outputs the result. Based on the result output from the FET analysis unit 71, it is possible to detect the change in the content of the harmonic of 2 times or the harmonic of even number times remaining without being cancelled out.
The band-pass filter 73 is a circuit that passes only a predetermined frequency and cuts off other frequencies. The band-pass filter 73 outputs a signal of a predetermined frequency included in a detection result (current detection value) of the current supplied from the current detector 13. Based on the result output from the band pass filter 73, it is possible to detect changes in the content of the harmonic of 2 times or the harmonic of even number times remaining without being cancelled out.
The operation switching determination unit 72 determines whether to continue the operation of the electric-vehicle power supply device 1 without changing the control constant (controlling constant), to continue the operation of the electric-vehicle power supply device 1 by changing the control constant, or to stop the operation of the electric-vehicle power supply device 1.
The operation switching determination unit 72 in fig. 6 determines whether or not the operation of the electric power supply device 1 for an electric vehicle is continued, whether or not the control constant is changed, and the like, based on the result output from the FET analysis unit 71. The operation switching determination unit 72 in fig. 7 determines whether or not the operation of the electric power supply device 1 for an electric vehicle is continued, whether or not the control constant is changed, and the like, based on the result output from the band-pass filter 73.
For example, the operation switching determination unit 72 determines whether or not the harmonic of 2 times exceeds the allowable current rating of the 1 st capacitor C1 and the 2 nd capacitor C2.
The operation switching determination unit 72 determines that the operation of the electric vehicle power supply device 1 is continued without changing the control constant when determining that the harmonic of 2 times does not exceed the allowable current rating of the 1 st capacitor C1 and the 2 nd capacitor C2.
The operation switching determination unit 72 determines that the control constant is changed and the operation of the electric vehicle power supply device 1 is continued when the harmonic of 2 times converges within the allowable current rating of the 1 st capacitor C1 and the 2 nd capacitor C2 by changing the frequency.
The operation switching determination unit 72 determines that the operation of the electric-powered vehicle power supply device 1 is stopped when the frequency and the 2 nd harmonic do not fall within the allowable current rating of the 1 st capacitor C1 and the 2 nd capacitor C2 even when the frequency and the 2 nd harmonic are changed.
When the operation switching determination unit 72 determines that the control constant is to be changed and the operation of the electric vehicle power supply device 1 is to be continued, the control circuit 14 changes one or both of the switching frequencies of the 1 st resonant inverter 31 and the 2 nd resonant inverter 34 and the phase difference between the switches of the 1 st resonant inverter 31 and the switches of the 2 nd resonant inverter 34.
First, an example of changing the switching frequency (switching frequency) will be described.
Fig. 8 shows an example in which the frequency of the switching of the 1 st resonant inverter 31 and the switching of the 2 nd resonant inverter 34 of the power conversion circuit 12 is set to 2 times the switching frequency of the 1 st boost chopper (boost chopper)21 and the 2 nd boost chopper 22 of the booster circuit 11. The frequencies of the switching of the 1 st resonant inverter 31 and the switching of the 2 nd resonant inverter 34 may be integral multiples (integral multiples) such as 3 times or 4 times the switching frequencies of the 1 st boost chopper 21 and the 2 nd boost chopper 22 of the boost circuit 11.
By changing the frequency of the switches of 1 st resonant inverter 31 and 2 nd resonant inverter 34 to be high in this manner, the peak current per unit time can be suppressed. That is, the amplitudes of the peaks of the 3 rd curve 63 and the 4 th curve 64 in fig. 4 can be reduced. As a result, ripple current can be suppressed.
In addition, the capacity of the capacitors of the 1 st resonant inverter 31 and the 2 nd resonant inverter 34 decreases due to aging (managed determination). This increases the excitation frequency of 1 st resonant inverter 31 and 2 nd resonant inverter 34. However, as described above, by increasing the switching frequency of the 1 st resonant inverter 31 and the 2 nd resonant inverter 34, it is possible to prevent a deviation between the excitation frequency and the switching frequency of the 1 st resonant inverter 31 and the 2 nd resonant inverter 34. As described above, the 1 st boost chopper 21 and the 2 nd boost chopper 22 are set so that the switching timing is constant for the 1 st resonant inverter 31 and the 2 nd resonant inverter 34. Therefore, when the switching frequencies of the 1 st resonant inverter 31 and the 2 nd resonant inverter 34 are changed according to the deterioration of the elements, the control circuit 14 also changes the switching frequencies of the 1 st boost chopper 21 and the 2 nd boost chopper 22.
Fig. 9 shows an example in which the frequencies of the switching of the 1 st resonant inverter 31 and the switching of the 2 nd resonant inverter 34 of the power conversion circuit 12 are set to 1/2 times the switching frequencies of the 1 st boost chopper 21 and the 2 nd boost chopper 22 of the booster circuit 11. That is, an example in which the switching frequency of the 1 st boost chopper 21 and the 2 nd boost chopper 22 of the boost circuit 11 is set to be 2 times the switching frequency of the 1 st resonant inverter 31 and the switching frequency of the 2 nd resonant inverter 34 is shown.
In this manner, the frequencies of the switches of 1 st resonant inverter 31 and 2 nd resonant inverter 34 may be changed to be low.
Next, an example of changing the phase difference between the switches of the 1 st resonant inverter 31 and the switches of the 2 nd resonant inverter 34 will be described.
The control circuit 14 may also perform control so as to reduce the ripple current in the current shown in the 5 th graph 65 of fig. 4 by adjusting the phases of the switches of the 1 st resonant inverter 31 and the switches of the 2 nd resonant inverter 34. Specifically, control circuit 14 calculates a 5 th graph 65 in a case where the phases of the switches of 1 st resonant inverter 31 and the switches of 2 nd resonant inverter 34 are slightly shifted each time, and uses a phase difference with which the ripple current becomes minimum based on the calculation result.
As described above, the control circuit 14 of the power supply device 1 for an electric vehicle analyzes the current value supplied from the current detector 13 to control the control constant of the power conversion circuit 12. Thus, even when the power conversion circuit 12 is degraded, the control circuit 14 can suppress the ripple current.
Further, the control circuit 14 controls the switching frequency of the 1 st resonant inverter 31 and the switching frequency of the 2 nd resonant inverter 34 of the power conversion circuit 12 based on the analysis result of the current value supplied from the current detector 13. Thus, ripple current can be suppressed even when the excitation frequencies of the 1 st resonant inverter 31 and the 2 nd resonant inverter 34 change due to aging.
Further, the control circuit 14 controls the phase difference between the switching of the 1 st resonant inverter 31 and the switching of the 2 nd resonant inverter 34 of the power conversion circuit 12 based on the analysis result of the current value supplied from the current detector 13. Thus, even when the characteristics of the 1 st resonant inverter 31 and the 2 nd resonant inverter 34 change due to aging, ripple current can be suppressed.
(embodiment 2)
Next, a power supply device 1A for an electric vehicle according to embodiment 2 will be described.
The electric vehicle power supply device 1A is different from the electric vehicle power supply device 1 of embodiment 1 in the configuration of the booster circuit and the control circuit. The same components as those in embodiment 1 are denoted by the same reference numerals, and detailed description thereof is omitted.
Fig. 10 is an explanatory diagram for explaining an example of the electric vehicle power supply device 1A according to embodiment 2. The electric vehicle power supply device 1A includes a booster circuit 11A, a power conversion circuit 12, a current detector 13, and a control circuit 14.
The booster circuit 11A includes two booster reactors L, a 1 st booster chopper 21, and a 2 nd booster chopper 22. The two voltage boosting reactors L are connected in parallel with respect to the current collector 3, respectively. The 1 st step-up chopper 21 and the 2 nd step-up chopper 22 are connected to the subsequent stage of each step-up reactor L. That is, the booster circuit 11A is connected in parallel to the collector 3 with the 1 st boost chopper 21 and the 2 nd boost chopper 22. With such a configuration, the electric power supply device 1A for an electric vehicle can suppress a ripple current of a current flowing to the secondary side via the high-frequency transformer by performing the same control as in embodiment 1.
Several embodiments of the present invention have been described, but these embodiments are presented as examples and are not intended to limit the scope of the invention. These new embodiments can be implemented in other various ways, and various omissions, substitutions, and changes can be made without departing from the spirit of the invention. These embodiments and modifications thereof are included in the scope and gist of the invention, and are included in the invention described in the claims and the scope equivalent thereto.

Claims (7)

1. A power supply device for an electric vehicle is provided with:
a plurality of high frequency transformers;
a plurality of step-up choppers for stepping up a dc voltage supplied from a dc power supply;
a plurality of inverters for supplying an ac current to the high-frequency transformers using the dc voltage supplied from each of the step-up choppers; and
and a control circuit for switching each of the boost choppers and each of the inverters so that a relationship between a switching phase of each of the boost choppers and a switching phase of each of the inverters is constant.
2. The power supply apparatus for electric vehicles according to claim 1,
the plurality of high frequency transformers have a 1 st high frequency transformer and a 2 nd high frequency transformer,
the inverters include a 1 st inverter for supplying an AC current to the 1 st high-frequency transformer and a 2 nd inverter for supplying an AC current to the 2 nd high-frequency transformer,
the plurality of boost choppers include a 1 st boost chopper for supplying a dc voltage to the 1 st inverter and a 2 nd boost chopper for supplying a dc voltage to the 2 nd inverter,
the control circuit switches the 1 st boost chopper and the 2 nd boost chopper with a phase shift of 180 degrees, and switches the 1 st inverter and the 2 nd inverter with a phase shift of 90 degrees.
3. The power supply apparatus for electric vehicles according to claim 2,
the control circuit causes each of the inverters to switch at a switching frequency that is an integral multiple of a switching frequency of each of the boost choppers.
4. The power supply apparatus for electric vehicles according to claim 2,
the control circuit causes each of the boost choppers to switch at a switching frequency that is an integral multiple of 2 or more of a switching frequency of each of the inverters.
5. The power supply apparatus for electric vehicles according to claim 2,
further comprises a current detector for detecting currents outputted from the secondary sides of the plurality of high-frequency transformers,
the control circuit analyzes the current value detected by the current detector, extracts a harmonic current that is an even multiple of the switching frequency of each inverter, and changes the switching frequency of each inverter and each boost chopper based on the harmonic current.
6. The power supply apparatus for electric vehicles according to claim 2,
further comprises a current detector for detecting currents outputted from the secondary sides of the plurality of high-frequency transformers,
the control circuit analyzes the current value detected by the current detector, extracts a harmonic current that is an even multiple of the switching frequency of each of the inverters, and adjusts the phase difference between the 1 st inverter and the 2 nd inverter based on the harmonic current.
7. The power supply apparatus for electric vehicles according to claim 2,
further comprises a current detector for detecting currents outputted from the secondary sides of the plurality of high-frequency transformers,
the control circuit analyzes the current value detected by the current detector, extracts a harmonic current that is an even multiple of the switching frequency of each inverter, and determines whether or not to stop each inverter and each boost chopper based on the harmonic current.
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