CN112019181B - Design method of extremely-high-frequency broadband linearizer - Google Patents
Design method of extremely-high-frequency broadband linearizer Download PDFInfo
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- CN112019181B CN112019181B CN202010692983.5A CN202010692983A CN112019181B CN 112019181 B CN112019181 B CN 112019181B CN 202010692983 A CN202010692983 A CN 202010692983A CN 112019181 B CN112019181 B CN 112019181B
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
- H03H7/38—Impedance-matching networks
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
- Y02D30/00—Reducing energy consumption in communication networks
- Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks
Abstract
The invention provides a design method of an extremely high frequency broadband linearizer. The linearizer comprises a 3dB directional coupler, a nonlinear load and a matching network, and the design method comprises the following steps: step 1, setting gain compensation quantity and phase compensation quantity required by a linearizer at different frequencies; step 2, obtaining impedance values of the nonlinear load at different frequencies under different input powers through measurement, and converting the impedance values of the nonlinear load into admittance values of the nonlinear load; step 3, according to the admittance value of the nonlinear load, obtaining a port impedance value required by the matching network under the condition of meeting the gain compensation quantity and the phase compensation quantity given in the step 1 by an optimization method; and 4, designing a matching network according to the port impedance value. The invention provides the design method of the linearizer with gain and phase compensation quantities at given different frequencies for the first time, and overcomes the defect that the prior design method can not compensate each frequency.
Description
Technical Field
The invention relates to the technical field of microwaves, in particular to a design method of an ultrahigh-frequency broadband linearizer.
Background
In recent years, military and government satellite communication demands have continued to increase as the competition for space spectrum resources has accelerated, and the space electromagnetic environment has become increasingly complex. However, the existing Ku-band and Ka-band satellite communication systems cannot meet the requirements of people on communication quality at present. It is a research direction of researchers to select a higher frequency band for communication to obtain a higher capacity and design a better satellite communication system. The search for higher frequency bands mainly involves the extremely high frequency bands outside the Ka band, i.e. the Q/V band (about 40-75 GHz) and the W band (75-100 GHz). This results in extremely high device and process requirements due to the significant atmospheric attenuation and free-space path loss in the very high frequency band. The power amplifier, which is a crucial module in a satellite transponder, determines the propagation distance and quality of a signal in free space. For better signal quality, the power amplifier usually needs to back off the output power. However, this reduces the efficiency of the power amplifier, further hindering the miniaturization and weight reduction of the satellite.
The linearization technology can widen the linear working interval of the power amplifier, greatly reduce the output power back-off quantity of the power amplifier, and ensure that the power amplifier still works in a high-efficiency state while ensuring the quality of an output signal. This makes the design of current very high frequency wideband linearizers difficult, since the non-linear characteristics of the power amplifier are not only dependent on the input power, but also on the frequency in the very high frequency band. Zhang et al, prediction Linearizer for Wideband AM/PMcompensation with a Left-hand delayed Line [ J ]. IEEE Microwave & Wireless Components letters.2017,27 (9): 794-796. The document only gives the phase compensation capability of the Linearizer at different frequencies, does not relate to the gain compensation capability at different frequencies, and the design structure of the circuit is complex.
In addition, no design method of the extremely-high frequency broadband linearizer exists at present, so the research on the design method can effectively solve the problems of high-frequency atmospheric attenuation and nonlinear distortion encountered in future satellite development, is beneficial to the miniaturization and light weight of the future satellite, and can provide powerful support for the further development of the satellite in China.
Disclosure of Invention
Aiming at the problems that the existing design method of a linearizer cannot perform gain compensation on each frequency and the design method of an extremely high frequency broadband linearizer is lacked, the invention provides a design method of the extremely high frequency broadband linearizer.
The invention provides a design method of an extremely high frequency broadband linearizer, wherein the linearizer comprises a 3dB directional coupler, a nonlinear load and a matching network, and the design method comprises the following steps:
and 4, designing a matching network according to the port impedance value.
Further, step 1 specifically comprises:
the gain compensation amount and the phase compensation amount of the linearizer at different frequencies are determined from gain and phase curves of the power amplifier measured at different frequencies and powers.
Further, step 3 comprises:
setting the transmission matrix of the matching network as
Parameters A, B, C and D of the matching network are solved according to equation (2):
wherein a and b are respectively the gain compensation amount and the phase compensation amount given in step 1, IL is the insertion loss of the system, and Z 0 The port impedance value of the coupling end of the 3dB directional coupler is conjugate operation G s And B s Admittance value, G, for a non-linear load sh And B sh Admittance value, G, for a non-linear load at maximum input power sl And B sl Admittance value, Γ, for a non-linear load at minimum input power h And Γ l The value of the reflection coefficient at maximum input power and the value at minimum input power, phi, respectively Γh And phi Γl Respectively representing the phase value of the reflection coefficient at maximum input power and the phase value at minimum input power.
Further, step 3 further comprises:
calculating according to the parameters of the matching network and the formula (3) to obtain the port impedance value Z of the matching network opt ：
Further, step 4 comprises:
when designing a matching network, selecting a specific matching network structure, and adopting formula (4) as an objective function of the matching network:
wherein λ is i Is wave number, Z opt (λ i ) Port impedance value, Z, of the matching network obtained in step 3 at different frequencies in (λ i ) N represents the number of frequencies that need to be matched for a port impedance value at a particular matching network configuration at different frequencies.
The invention has the beneficial effects that:
1. the design method of the linearizer with the gain compensation amount and the phase compensation amount at different given frequencies is given for the first time, the defect that the prior design method can not carry out gain compensation on each frequency is overcome, and the method provides a theoretical basis for the automatic design of the linearizer;
2. the circuit adopted by the invention has simple structure and clear design flow;
3. the circuit adopted by the invention is an analog circuit, and has the advantages of small volume, low cost, wide bandwidth, stable performance and the like;
4. the method is not limited to specific working frequency, and is a universal design method.
Drawings
FIG. 1 is a schematic flow chart of a method for designing an ultra-high frequency broadband linearizer according to an embodiment of the present invention;
FIG. 2 is a circuit block diagram of a linearizer provided in an embodiment of the present invention;
fig. 3 is a circuit structure diagram of a hybrid T-type matching network according to an embodiment of the present invention;
FIG. 4 is a circuit diagram of a linearizer in Q/V band (46-52 GHz) designed by the design method of the present invention according to an embodiment of the present invention;
FIG. 5 is a view illustrating gain compensation measurement of a linearizer in Q/V band (46-52 GHz) according to an embodiment of the present invention;
FIG. 6 is a diagram illustrating a phase compensation measurement of a linearizer in the Q/V band (46-52 GHz), according to an embodiment of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention clearer, the technical solutions in the embodiments of the present invention will be clearly described below with reference to the accompanying drawings in the embodiments of the present invention, and it is obvious that the described embodiments are some, but not all, embodiments of the present invention. All other embodiments, which can be obtained by a person skilled in the art without making any creative effort based on the embodiments in the present invention, belong to the protection scope of the present invention.
Example 1
As shown in fig. 1, an embodiment of the present invention provides a design method of an extremely high frequency broadband linearizer, which includes a 3dB directional coupler, a nonlinear load and a matching network, and includes the following steps:
s101, setting gain compensation quantity and phase compensation quantity required by a linearizer at different frequencies;
s102, obtaining impedance values of the nonlinear load at different frequencies under different input powers through measurement, and converting the impedance values of the nonlinear load into admittance values of the nonlinear load;
s103, according to the admittance value of the nonlinear load, obtaining a port impedance value required by the matching network under the condition of meeting the gain compensation quantity and the phase compensation quantity given in the step 1 by an optimization method;
and S104, designing a matching network according to the port impedance value.
Example 2
On the basis of embodiment 1, the embodiment of the present invention further provides a design method of an extremely high frequency broadband linearizer, wherein the linearizer comprises a 3dB directional coupler, a nonlinear load and a matching network, and the design method comprises the following steps:
s201, determining gain compensation quantity and phase compensation quantity of a linearizer at different frequencies according to gain and phase curves of a power amplifier measured at different frequencies and input power;
specifically, when determining the gain compensation amount and the phase compensation amount, it is generally required to satisfy that the gain compression of the power amplifier after linearization by using the linearizer is less than 1dB and the phase change is less than 10 °.
S202, obtaining impedance values of the nonlinear load at different frequencies under different input powers through measurement, and converting the impedance values of the nonlinear load into admittance values of the nonlinear load;
specifically, the formula for converting the impedance value of the nonlinear load into the admittance value of the nonlinear load is shown in formula (1):
Z s ＝1/(G s +jB s ) (1)
wherein, Z s Is the impedance value of the non-linear load, G s 、B s Is the admittance value of the nonlinear load.
S203, setting the transmission matrix of the matching network as
Parameters A, B, C and D of the matching network are solved according to equation (2):
wherein a and b are respectively the gain compensation amount and the phase compensation amount given in step 1, the constraint condition AD-BC =1 is obtained when the matching network is a reciprocal network, IL is the insertion loss of the linearizer, Z is 0 Port impedance value of the coupling end of the 3dB directional coupler, conjugate operation, G s And B s Admittance value, G, for a non-linear load sh And B sh Admittance value, G, for a non-linear load at maximum input power sl And B sl Admittance value, Γ, for a non-linear load at minimum input power h And Γ l The value of the reflection coefficient at maximum input power and the value at minimum input power, phi, respectively Γh And phi Γl Respectively representing the phase value and the sum of the reflection coefficients at maximum input powerThe phase value at minimum input power.
S204, calculating according to the parameters of the matching network and the formula (3) to obtain the port impedance value Z of the matching network opt ：
S205, when designing a matching network, selecting a specific matching network structure, and adopting a formula (4) as an objective function of the matching network:
wherein λ is i Is wave number, Z opt (λ i ) Is the port impedance value, Z, of the matching network obtained in step S204 under different frequencies in (λ i ) N represents the number of frequencies that need to be matched for a port impedance value at a particular matching network configuration at different frequencies.
A matching network satisfying a given gain and phase compensation amount can be obtained from the objective function shown in equation (4), and thus the design parameters of the whole linearizer can be obtained.
Example 3
In this embodiment, taking a linearizer designed for a Q/V band (46-52 GHz), a Rogers5880 substrate with a relative dielectric constant of 2.2 and a thickness of 10mil is used as the circuit substrate. The design method of the very high frequency broadband linearizer provided by the invention is further explained. The circuit structure diagram of the linearizer employed in the embodiment of the present invention is shown in fig. 2.
The design method of the linearizer of the Q/V wave band (46-52 GHz) of the embodiment comprises the following steps:
1) Given the amount of gain compensation and phase compensation required by the linearizer at different frequencies:
determining the gain compensation quantity Δ G and the phase compensation quantity Δ Φ of the required linearizer at different frequencies according to the gain and phase curves of the power amplifier measured at different frequencies and powers, as shown in table 1:
TABLE 1 amount of gain and phase compensation required for power amplifier and port impedance value calculated
2) Obtaining impedance value Z of nonlinear load at different frequencies under different input powers through measurement s Converting the admittance value into an admittance value required by calculation, and storing the admittance value into a computer;
3) According to the related information obtained in the steps 1) and 2), the port impedance values Z of the matching networks required at different frequencies are obtained through an optimization method opt The calculation results are shown in table 1.
4) Designing a matching network according to the port impedance value obtained by calculation:
in this embodiment, a hybrid T-type matching network is selected as the matching network structure, a schematic diagram of which is shown in fig. 3, and a transmission matrix of which can be expressed as formula (5):
its port impedance value can then be expressed as equation (6):
finally, the parameters of the matching network can be obtained according to the objective function shown in formula (7):
the circuit diagram of the linearizer for the finally designed Q/V band (46-52 GHz) is shown in FIG. 4. In fig. 4, parameters before and after "/" are the width and length of the microstrip line, respectively, and for example, "0.84/1.5" indicates that the width of the microstrip line is 0.84mm and the length is 1.5mm. Through actual measurement, the gain compensation quantity of the linearizer is respectively 3.58, 3.67, 4.03 and 4.19dB at 46 GHz, 48 GHz, 50 GHz and 52GHz, the nonlinear performance is good, and the use requirement is met; the phase compensation quantity of the linearizer is respectively 35 degrees, 36.5 degrees, 42.5 degrees and 55 degrees at 46 GHz, 48 GHz, 50 GHz and 52GHz, the nonlinear performance is good, and the using requirement is met. The linearizer gain phase compensation measurements for the Q/V band (46-52 GHz) are attempted as shown in FIGS. 5 and 6, respectively;
finally, it should be noted that: the above examples are only intended to illustrate the technical solution of the present invention, but not to limit it; although the present invention has been described in detail with reference to the foregoing embodiments, it should be understood by those of ordinary skill in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some technical features may be equivalently replaced; and such modifications or substitutions do not depart from the spirit and scope of the corresponding technical solutions of the embodiments of the present invention.
Claims (3)
1. A method of designing a very high frequency broadband linearizer comprising a 3dB directional coupler, a nonlinear load, and a matching network, the method comprising:
step 1, setting gain compensation quantity and phase compensation quantity required by a linearizer at different frequencies;
step 2, obtaining impedance values of the nonlinear load at different frequencies under different input powers through measurement, and converting the impedance values of the nonlinear load into admittance values of the nonlinear load;
step 3, according to the admittance value of the nonlinear load, obtaining a port impedance value required by the matching network under the condition of meeting the gain compensation quantity and the phase compensation quantity given in the step 1 by an optimization method; the method specifically comprises the following steps:
setting the transmission matrix of the matching network as
Solving parameters A, B, C and D of the matching network according to equation (2):
wherein a and b are respectively the gain compensation amount and the phase compensation amount given in step 1, IL is the insertion loss of the linearizer, and Z 0 The port impedance value of the coupling end of the 3dB directional coupler is conjugate operation G s And B s Admittance value, G, for a non-linear load sh And B sh Admittance value, G, for a non-linear load at maximum input power sl And B sl Admittance value, Γ, for a non-linear load at minimum input power h And Γ l Respectively the value of the reflection coefficient at maximum input power and at minimum input power,
and
respectively representing a phase value of the reflection coefficient at the maximum input power and a phase value at the minimum input power;
calculating according to the parameters of the matching network and the formula (3) to obtain the port impedance value Z of the matching network opt ：
And 4, designing a matching network according to the port impedance value.
2. The method according to claim 1, wherein step 1 is specifically:
the amount of gain compensation and the amount of phase compensation of the linearizer at different frequencies are determined from the gain and phase curves of the power amplifier measured at different frequencies and input powers.
3. The method of claim 1, wherein step 4 comprises:
when designing a matching network, selecting a specific matching network structure, and adopting a formula (4) as an objective function of the matching network:
wherein λ is i Is wave number, Z opt (λ i ) Port impedance value, Z, of the matching network obtained in step 3 at different frequencies in (λ i ) N represents the number of frequencies that need to be matched for a port impedance value at a particular matching network configuration at different frequencies.
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Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4772855A (en) * | 1987-02-26 | 1988-09-20 | Siemens Telecommunicazioni, S.P.A. | Linearizer for microwave power amplifiers |
| US5282072A (en) * | 1991-11-19 | 1994-01-25 | Harmonic Lightwaves, Inc. | Shunt-expansive predistortion linearizers for optical analog transmitters |
| US5424680A (en) * | 1993-11-30 | 1995-06-13 | Harmonic Lightwaves, Inc. | Predistorter for high frequency optical communications devices |
| US5966049A (en) * | 1998-12-01 | 1999-10-12 | Space Systems/Loral, Inc. | Broadband linearizer for power amplifiers |
| US6307436B1 (en) * | 1999-06-15 | 2001-10-23 | Nec Corporation | Predistortion type linearizer with a resonant circuit and common gate FET |
| CN102545796A (en) * | 2012-02-15 | 2012-07-04 | 电子科技大学 | Traveling wave tube linearizer |
| CN107276541A (en) * | 2017-06-14 | 2017-10-20 | 电子科技大学 | Variable vector mixes superposing type distortion linearizing method |
| CN107425814A (en) * | 2017-08-07 | 2017-12-01 | 杭州电子科技大学 | A kind of broadband Doherty power amplifier based on compensation parasitic capacitance |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US8848824B2 (en) * | 2008-03-07 | 2014-09-30 | Andrew M. Teetzel | High efficiency RF system linearizer using controlled complex nonlinear distortion generators |
| US20120242405A1 (en) * | 2011-03-25 | 2012-09-27 | Younkyu Chung | Frequency-Desensitizer for Broadband Predistortion Linearizers |
-
2020
- 2020-07-17 CN CN202010692983.5A patent/CN112019181B/en active Active
Patent Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4772855A (en) * | 1987-02-26 | 1988-09-20 | Siemens Telecommunicazioni, S.P.A. | Linearizer for microwave power amplifiers |
| US5282072A (en) * | 1991-11-19 | 1994-01-25 | Harmonic Lightwaves, Inc. | Shunt-expansive predistortion linearizers for optical analog transmitters |
| US5424680A (en) * | 1993-11-30 | 1995-06-13 | Harmonic Lightwaves, Inc. | Predistorter for high frequency optical communications devices |
| US5966049A (en) * | 1998-12-01 | 1999-10-12 | Space Systems/Loral, Inc. | Broadband linearizer for power amplifiers |
| US6307436B1 (en) * | 1999-06-15 | 2001-10-23 | Nec Corporation | Predistortion type linearizer with a resonant circuit and common gate FET |
| CN102545796A (en) * | 2012-02-15 | 2012-07-04 | 电子科技大学 | Traveling wave tube linearizer |
| CN107276541A (en) * | 2017-06-14 | 2017-10-20 | 电子科技大学 | Variable vector mixes superposing type distortion linearizing method |
| CN107425814A (en) * | 2017-08-07 | 2017-12-01 | 杭州电子科技大学 | A kind of broadband Doherty power amplifier based on compensation parasitic capacitance |
Non-Patent Citations (3)
| Title |
|---|
| Ku频段空间行波管形状可调线性化器设计;黄微波等;《空间电子技术》;20121225(第04期);全文 * |
| 一种补偿量可调的反射式预失真线性化器;邓海林等;《真空科学与技术学报》;20180815(第08期);全文 * |
| 超宽带桥T型模拟线性化器设计;周丽等;《电子科技大学学报》;20200130(第01期);全文 * |
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