CN111999725A - Broadband polynomial phase signal deskewing method and device under guidance of narrow-band signal - Google Patents

Broadband polynomial phase signal deskewing method and device under guidance of narrow-band signal Download PDF

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CN111999725A
CN111999725A CN202010904054.6A CN202010904054A CN111999725A CN 111999725 A CN111999725 A CN 111999725A CN 202010904054 A CN202010904054 A CN 202010904054A CN 111999725 A CN111999725 A CN 111999725A
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CN111999725B (en
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陆泽橼
杨广玉
张孟达
徐海洲
于秋野
汪在华
梁华东
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CETC 38 Research Institute
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/0209—Systems with very large relative bandwidth, i.e. larger than 10 %, e.g. baseband, pulse, carrier-free, ultrawideband
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/28—Details of pulse systems
    • G01S7/285—Receivers
    • G01S7/292—Extracting wanted echo-signals
    • G01S7/2923—Extracting wanted echo-signals based on data belonging to a number of consecutive radar periods
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/28—Details of pulse systems
    • G01S7/285—Receivers
    • G01S7/32—Shaping echo pulse signals; Deriving non-pulse signals from echo pulse signals
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Abstract

The invention discloses a broadband polynomial phase signal deskewing method and a broadband polynomial phase signal deskewing device under the guidance of a narrow-band signal, wherein the method comprises the following steps: transmitting a plurality of continuous narrow-band LFM signals; acquiring pulse echoes of a plurality of continuous narrow-band LFM signals; performing delay correlation processing on each pulse echo to obtain a plurality of narrow-band echo delay signals; performing fractional Fourier transform to obtain a quadratic term coefficient and a cubic term coefficient of each narrowband echo delay signal estimation; compensating the pulse echo of each narrowband LFM signal, and performing Fourier transform on the compensated result to obtain a first-order coefficient and a zero-order coefficient of each narrowband echo delay signal estimation; acquiring cubic term coefficients of the broadband signal; acquiring k-1 order item coefficients of the broadband signal, and performing deskew processing on the broadband signal by using a deskew signal; the invention has the advantages that: the method for deskewing the broadband polynomial phase signals is novel and good in deskewing effect.

Description

Broadband polynomial phase signal deskewing method and device under guidance of narrow-band signal
Technical Field
The invention relates to the technical field of microwaves, in particular to a broadband polynomial phase signal deskewing method and device under the guidance of a narrow-band signal.
Background
With the continuous development of microwave technology, the radar can transmit and receive signals with a wider bandwidth than before, and clear imaging processing is carried out by means of the high distance resolution of the signals with the wider bandwidth in cooperation with Doppler generated by space target rotation. The large bandwidth signal meets a space target which moves at high speed and has acceleration, and although the transmitting signal is a linear frequency modulation signal, the receiving signal becomes a polynomial phase signal. Because of the in-band fluctuation of the transceiving response of the antenna with large bandwidth, the possibly generated signal is not an ideal linear frequency modulation signal, the signal needs to be subjected to deskew processing, and the traditional deskew processing adopts an inherent deskew signal loaded on a broadband signal for deskew.
The invention discloses a method for generating broadband deskew echo based on sweep frequency data, which belongs to the technical field of radar signal processing and is disclosed by Chinese invention publication No. CN 110850384B. Firstly, the pulse radar transmits a chirp signal to a detection target containing Q scattering centers. And feeding back each scattering center in the detection target to respective echo signals of the radar to obtain broadband echo signals of Q scattering centers. Setting a reference signal, and performing deskew processing on the broadband echo signal of each scattering center to obtain a frequency response containing the RCS characteristics of a target; carrying out fast Fourier inverse transformation on the frequency response containing the RCS characteristics of the target, carrying out inverse transformation on each scattering center to obtain a complex amplitude, and forming a one-dimensional range profile of the detection target by Q complex amplitudes; and multiplying the one-dimensional range profile of the detection target by the deskew echo signal of each scattering center, and then accumulating and summing to finally obtain the broadband deskew echo of the whole detection target. The invention greatly reduces the operation amount and simultaneously ensures the same precision and accuracy as those of the convolution operation. However, the main focus of the method is not deskew processing, and the wideband polynomial phase signal guided by the narrowband signal cannot be deskewed well.
Disclosure of Invention
The invention aims to solve the technical problem that the deskewing effect of broadband polynomial phase signals guided by narrow-band signals in the prior art is poor.
The invention solves the technical problems through the following technical means: a method of wideband polynomial phase signal deskewing under narrowband signal guidance, the method comprising:
the method comprises the following steps: transmitting a plurality of continuous narrow-band LFM signals;
step two: acquiring pulse echoes of a plurality of continuous narrow-band LFM signals;
step three: performing delay correlation processing on each pulse echo to obtain a plurality of narrow-band echo delay signals;
step four: traversing all the narrow-band echo delay signals, fixing time value taking, and performing fractional Fourier transform to obtain a quadratic term coefficient and a cubic term coefficient estimated by each narrow-band echo delay signal;
step five: compensating the pulse echo of each narrowband LFM signal according to the estimated quadratic term coefficient and the estimated cubic term coefficient of each narrowband echo delay signal, and performing Fourier transform on the compensated result to obtain the estimated primary term coefficient and the zero-order term coefficient of each narrowband echo delay signal;
step six: obtaining a cubic term coefficient of the broadband signal according to the cubic term coefficient and the frequency modulation slope of the ith narrowband echo delay signal and the frequency modulation slope of the broadband signal;
step seven: obtaining a k-1 time term coefficient of the broadband signal according to the k-1 time term coefficient, the frequency modulation slope and the frequency modulation slope of the ith and jth narrow-band echo delay signals, wherein the value of k is 1,2, 3 or 4;
step eight: and obtaining a frequency modulation slope of the deskew signal according to the quadratic term coefficient and the tertiary term coefficient of the broadband signal, and performing deskew processing on the broadband signal by using the deskew signal.
The method is based on the continuous narrow-band LFM signals with different waveforms, realizes the extraction of the waveform parameters of the space target broadband signal, does not need to add extra hardware cost, does not change the existing radar imaging signal processing system, has small calculation load, obtains the frequency modulation slope of a deskew signal through the quadratic term coefficient and the cubic term coefficient of the broadband signal, obtains the deskew signal through the frequency modulation slope of the deskew signal, utilizes the deskew signal to perform deskew processing on the broadband signal, realizes the accurate deskew and real-time deskew aiming at the broadband signal, has good deskew effect, and has important application value for the accurate imaging field of radar and the subsequent target identification.
Further, the ith narrowband LFM signal in the first step is
Figure RE-GDA0002719970750000031
N, where i is 1,2,. N is the total number of narrow-band LFM signals, Si(t) is the ith narrowband LFM signal, j is the imaginary symbol, e()Is an exponential function with e as the base, f0Working frequency point common to all narrow band LFM signals, the narrow band LFM signal and the broadband signal share the same working frequency point, kiFor the chirp rate of the ith narrowband LFM signal, BiThe amplitude of the ith narrowband LFM signal.
Further, the expression of the pulse echo in the second step is
Figure RE-GDA0002719970750000032
Wherein S isr i(t) is the ith pulse echo, α1i、α2i、α3iAnd alpha4iRespectively a zero-order coefficient, a first-order coefficient, a second-order coefficient and a third-order coefficient of the ith narrowband LFM signal, AiThe echo amplitude of the ith narrowband LFM signal.
Further, the third step includes: the ith pulse echo is delayed by tau components to obtain the ith narrow-band echo delay signal
Figure RE-GDA0002719970750000033
Wherein (alpha)3i+3α4it) is the instantaneous frequency of the ith narrow-band echo delayed signal.
Further, the fourth step includes: by the formula
Figure RE-GDA0002719970750000041
Obtaining a first intermediate quantity
Figure RE-GDA0002719970750000042
And a second intermediate amount
Figure RE-GDA0002719970750000043
The time values t1 and t2 can obtain the relation between the instantaneous frequency of the narrow-band echo delay signal and the first intermediate quantity and the second intermediate quantity
Figure RE-GDA0002719970750000044
Obtaining the cubic coefficient estimated by the narrow-band echo delay signal according to the relation between the instantaneous frequency of the narrow-band echo delay signal and the first intermediate quantity and the second intermediate quantity
Figure RE-GDA0002719970750000045
And coefficient of quadratic term
Figure RE-GDA0002719970750000046
Are respectively as
Figure RE-GDA0002719970750000047
Further, the fifth step includes: quadratic estimated from each narrow-band echo delay signalThe pattern coefficient and cubic coefficient compensate the pulse echo of each narrow band LFM signal to obtain the compensated result
Figure RE-GDA0002719970750000048
The compensated result is processed by formula
Figure RE-GDA0002719970750000049
Fourier transform is carried out to obtain the first-order coefficient of each narrow-band echo delay signal estimation
Figure RE-GDA00027199707500000410
And zero degree coefficient
Figure RE-GDA00027199707500000411
Further, the sixth step includes: by the formula
Figure RE-GDA00027199707500000412
Obtaining cubic term coefficient of broadband signal, wherein alpha4bIs the coefficient of the third order term, beta, of the broadband signalbrIs the chirp rate of the wideband signal and,
Figure RE-GDA00027199707500000413
is the coefficient of the cubic term, beta, of the estimated ith narrowband LFM signaliIs the chirp rate of the ith narrowband LFM signal.
Further, the seventh step includes: by the formula
Figure RE-GDA00027199707500000414
Obtaining the linear relation between the FM slope of the narrow band LFM signal and the k-1 order coefficient, wherein, beta1iFor the chirp rate, beta, of the ith narrowband LFM signal2jFor the chirp rate of the jth narrowband LFM signal, pa1 and pa2 are the first parameter and the second parameter, respectively
Figure RE-GDA0002719970750000051
Is the estimated ithThe k-1 order coefficients of the narrowband LFM signal,
Figure RE-GDA0002719970750000052
is the estimated k-1 order coefficient of the jth narrowband LFM signal;
by the formula alphakb＝βbrPa1+ pa2 obtains the k-1 degree term coefficients of the wideband signal, where αkbIs the k-1 degree coefficient of the broadband signal.
Further, the step eight includes:
obtaining an expression Sigmatch of the broadband signal according to the zero-order coefficient, the first-order coefficient, the second-order coefficient and the third-order coefficient of the broadband signalb(t)＝exp[j2π((α1+α2bt+α3bt2+α4bt3))]
Obtaining the FM slope alpha of the declived signal according to the expression of the broadband signal3b+α4bAnd t, obtaining a deskew signal conjugated with the broadband signal according to the frequency modulation slope of the deskew signal, and carrying out deskew processing on the broadband signal by utilizing the deskew signal to offset a secondary term and a tertiary term of the broadband signal.
The invention also provides a wideband polynomial phase signal deskewing apparatus guided by a narrowband signal, the apparatus comprising:
the transmitting module is used for transmitting a plurality of continuous narrow-band LFM signals;
the receiving module is used for acquiring pulse echoes of a plurality of continuous narrow-band LFM signals;
the delay correlation processing module is used for performing delay correlation processing on each pulse echo to obtain a plurality of narrow-band echo delay signals;
the first Fourier transform module is used for traversing all the narrow-band echo delay signals, fixing time value taking, and performing fractional Fourier transform to obtain a quadratic term coefficient and a cubic term coefficient estimated by each narrow-band echo delay signal;
the second Fourier transform module is used for compensating the pulse echo of each narrowband LFM signal according to the quadratic term coefficient and the cubic term coefficient estimated by each narrowband echo delay signal, and carrying out Fourier transform on the compensated result to obtain the estimated quadratic term coefficient and the zero-order term coefficient of each narrowband echo delay signal;
the first broadband signal coefficient acquisition module is used for obtaining a cubic coefficient of a broadband signal according to the cubic coefficient and the frequency modulation slope of the ith narrowband echo delay signal and the frequency modulation slope of the broadband signal;
the second broadband signal coefficient acquisition module is used for acquiring a k-1 time coefficient of the broadband signal according to the k-1 time coefficient, the frequency modulation slope and the frequency modulation slope of the ith and jth narrowband echo delay signals, wherein the value of k is 1,2 or 3;
and the deskew module is used for obtaining a deskew signal frequency modulation slope according to the quadratic term coefficient and the cubic term coefficient of the broadband signal and carrying out deskew processing on the broadband signal by using the deskew signal.
Further, the ith narrowband LFM signal in the transmitting module is
Figure RE-GDA0002719970750000061
N, where i is 1,2,. N is the total number of narrow-band LFM signals, Si(t) is the ith narrowband LFM signal, j is the imaginary symbol, e()Is an exponential function with e as the base, f0Working frequency point common to all narrow band LFM signals, the narrow band LFM signal and the broadband signal share the same working frequency point, kiFor the chirp rate of the ith narrowband LFM signal, BiThe amplitude of the ith narrowband LFM signal.
Further, the expression of the pulse echo in the receiving module is
Figure RE-GDA0002719970750000062
Wherein S isr i(t) is the ith pulse echo, α1i、α2i、α3iAnd alpha4iRespectively a zero-order coefficient, a first-order coefficient, a second-order coefficient and a third-order coefficient of the ith narrowband LFM signal, AiThe echo amplitude of the ith narrowband LFM signal.
Further, the delay correlation processing module is further configured to: the ith pulse echo is delayed by tau components to obtain the ith narrow-band echo delay signal
Figure RE-GDA00027199707500000713
Wherein (alpha)3i+3α4it) is the instantaneous frequency of the ith narrow-band echo delayed signal.
Further, the first fourier transform module is further configured to: by the formula
Figure RE-GDA0002719970750000071
Obtaining a first intermediate quantity
Figure RE-GDA0002719970750000072
And a second intermediate amount
Figure RE-GDA0002719970750000073
The time values t1 and t2 can obtain the relation between the instantaneous frequency of the narrow-band echo delay signal and the first intermediate quantity and the second intermediate quantity
Figure RE-GDA0002719970750000074
Obtaining the cubic coefficient estimated by the narrow-band echo delay signal according to the relation between the instantaneous frequency of the narrow-band echo delay signal and the first intermediate quantity and the second intermediate quantity
Figure RE-GDA0002719970750000075
And coefficient of quadratic term
Figure RE-GDA0002719970750000076
Are respectively as
Figure RE-GDA0002719970750000077
Further, the second fourier transform module is further configured to: according to each narrow-band echo delayThe second order type coefficient and the third order coefficient of the signal estimation compensate the pulse echo of each narrow band LFM signal to obtain the compensated result
Figure RE-GDA0002719970750000078
The compensated result is processed by formula
Figure RE-GDA0002719970750000079
Fourier transform is carried out to obtain the first-order coefficient of each narrow-band echo delay signal estimation
Figure RE-GDA00027199707500000710
And zero degree coefficient
Figure RE-GDA00027199707500000711
Further, the first wideband signal coefficient obtaining module is further configured to: by the formula
Figure RE-GDA00027199707500000712
Obtaining cubic term coefficient of broadband signal, wherein alpha4bIs the coefficient of the third order term, beta, of the broadband signalbrIs the chirp rate of the wideband signal and,
Figure RE-GDA0002719970750000081
is the coefficient of the cubic term, beta, of the estimated ith narrowband LFM signaliIs the chirp rate of the ith narrowband LFM signal.
Further, the second wideband signal coefficient obtaining module is further configured to: by the formula
Figure RE-GDA0002719970750000082
Obtaining the linear relation between the FM slope of the narrow band LFM signal and the k-1 order coefficient, wherein, beta1iFor the chirp rate, beta, of the ith narrowband LFM signal2jFor the chirp rate of the jth narrowband LFM signal, pa1 and pa2 are the first parameter and the second parameter, respectively
Figure RE-GDA0002719970750000083
Figure RE-GDA0002719970750000084
To estimate the k-1 degree coefficients of the ith narrowband LFM signal,
Figure RE-GDA0002719970750000085
is the estimated k-1 order coefficient of the jth narrowband LFM signal;
by the formula alphakb＝βbrPa1+ pa2 obtains the k-1 degree term coefficients of the wideband signal, where αkbIs the k-1 degree coefficient of the broadband signal.
Further, the deskew module is further configured to:
obtaining an expression Sigmatch of the broadband signal according to the zero-order coefficient, the first-order coefficient, the second-order coefficient and the third-order coefficient of the broadband signalb(t)＝exp[j2π((α1+α2bt+α3bt2+α4bt3))]
Obtaining the FM slope alpha of the declived signal according to the expression of the broadband signal3b+α4bAnd t, obtaining a deskew signal conjugated with the broadband signal according to the frequency modulation slope of the deskew signal, and carrying out deskew processing on the broadband signal by utilizing the deskew signal to offset a secondary term and a tertiary term of the broadband signal.
The invention has the advantages that: the method is based on the continuous narrow-band LFM signals with different waveforms, realizes the extraction of the waveform parameters of the space target broadband signal, does not need to add extra hardware cost, does not change the existing radar imaging signal processing system, has small calculation load, obtains the frequency modulation slope of a deskew signal through the quadratic term coefficient and the cubic term coefficient of the broadband signal, obtains the deskew signal through the frequency modulation slope of the deskew signal, utilizes the deskew signal to perform deskew processing on the broadband signal, realizes the accurate deskew and real-time deskew aiming at the broadband signal, has good deskew effect, and has important application value for the accurate imaging field of radar and the subsequent target identification.
Drawings
Fig. 1 is a flowchart of a wideband polynomial phase signal deskewing method under guidance of a narrowband signal according to an embodiment of the present invention;
fig. 2 is a timing diagram of a narrowband LFM signal and a wideband signal in a wideband polynomial phase signal deskewing method under guidance of a narrowband signal according to an embodiment of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the embodiments of the present invention clearer, the technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the embodiments of the present invention, and it is obvious that the described embodiments are some embodiments of the present invention, but not all embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
Example 1
As shown in fig. 1, a wideband polynomial phase signal deskewing method under guidance of a narrowband signal, the method comprising:
step S1: transmitting a plurality of continuous narrow-band LFM signals; specifically, the method comprises the following steps: the ith narrowband LFM signal is
Figure RE-GDA0002719970750000091
N, where i is 1,2,. N is the total number of narrow-band LFM signals, Si(t) is the ith narrowband LFM signal, j is the imaginary symbol, e()Is an exponential function with e as the base, f0Working frequency point common to all narrow band LFM signals, the narrow band LFM signal and the broadband signal share the same working frequency point, kiFor the chirp rate of the ith narrowband LFM signal, BiThe amplitude of the ith narrowband LFM signal.
Step S2: acquiring pulse echoes of a plurality of continuous narrow-band LFM signals; specifically, the method comprises the following steps: the expression of the pulse echo is
Figure RE-GDA0002719970750000101
Wherein S isr i(t) is the ith pulse echo, α1i、α2i、α3iAnd alpha4iRespectively a zero-order coefficient, a first-order coefficient, a second-order coefficient and a third-order coefficient of the ith narrowband LFM signal, AiThe echo amplitude of the ith narrowband LFM signal.
Step S3: performing delay correlation processing on each pulse echo to obtain a plurality of narrow-band echo delay signals; the specific process is as follows: the ith pulse echo is delayed by tau components to obtain the ith narrow-band echo delay signal
Figure RE-GDA0002719970750000108
Wherein (alpha)3i+3α4it) is the instantaneous frequency of the ith narrow-band echo delayed signal.
Step S4: traversing all the narrow-band echo delay signals, fixing time value taking, and performing fractional Fourier transform to obtain a quadratic term coefficient and a cubic term coefficient estimated by each narrow-band echo delay signal; the specific process is as follows: by the formula
Figure RE-GDA0002719970750000102
Obtaining a first intermediate quantity
Figure RE-GDA0002719970750000103
And a second intermediate amount
Figure RE-GDA0002719970750000104
The time values t1 and t2 can obtain the relation between the instantaneous frequency of the narrow-band echo delay signal and the first intermediate quantity and the second intermediate quantity
Figure RE-GDA0002719970750000105
Obtaining the cubic coefficient estimated by the narrow-band echo delay signal according to the relation between the instantaneous frequency of the narrow-band echo delay signal and the first intermediate quantity and the second intermediate quantity
Figure RE-GDA0002719970750000106
And coefficient of quadratic term
Figure RE-GDA0002719970750000107
Are respectively as
Figure RE-GDA0002719970750000111
Step S5: compensating the pulse echo of each narrowband LFM signal according to the estimated quadratic term coefficient and the estimated cubic term coefficient of each narrowband echo delay signal, and performing Fourier transform on the compensated result to obtain the estimated primary term coefficient and the zero-order term coefficient of each narrowband echo delay signal; the specific process is as follows: compensating the pulse echo of each narrow-band LFM signal according to the quadratic form coefficient and the cubic term coefficient estimated by each narrow-band echo delay signal to obtain a compensated result
Figure RE-GDA0002719970750000112
The compensated result is processed by formula
Figure RE-GDA0002719970750000113
Fourier transform is carried out to obtain the first-order coefficient of each narrow-band echo delay signal estimation
Figure RE-GDA0002719970750000114
And zero degree coefficient
Figure RE-GDA0002719970750000115
Step S6: obtaining a cubic term coefficient of the broadband signal according to the cubic term coefficient and the frequency modulation slope of the ith narrowband echo delay signal and the frequency modulation slope of the broadband signal; the specific process is as follows: by the formula
Figure RE-GDA0002719970750000116
Obtaining cubic term coefficient of broadband signal, wherein alpha4bIs the coefficient of the third order term, beta, of the broadband signalbrIs the chirp rate of the wideband signal and,
Figure RE-GDA0002719970750000117
is the coefficient of the cubic term, beta, of the estimated ith narrowband LFM signaliIs the chirp rate of the ith narrowband LFM signal.
Step S7: obtaining a k-1 time term coefficient of the broadband signal according to the k-1 time term coefficient, the frequency modulation slope and the frequency modulation slope of the ith and jth narrow-band echo delay signals, wherein the value of k is 1,2, 3 or 4; the specific process is as follows: by the formula
Figure RE-GDA0002719970750000118
Obtaining the linear relation between the FM slope of the narrow band LFM signal and the k-1 order coefficient, wherein, beta1iFor the chirp rate, beta, of the ith narrowband LFM signal2jFor the chirp rate of the jth narrowband LFM signal, pa1 and pa2 are the first parameter and the second parameter, respectively
Figure RE-GDA0002719970750000121
To estimate the k-1 degree coefficients of the ith narrowband LFM signal,
Figure RE-GDA0002719970750000122
is the estimated k-1 order coefficient of the jth narrowband LFM signal;
by the formula alphakb＝βbrPa1+ pa2 obtains the k-1 degree term coefficients of the wideband signal, where αkbIs the k-1 degree coefficient of the broadband signal.
Step S8: obtaining a deskew signal frequency modulation slope according to a quadratic term coefficient and a cubic term coefficient of the broadband signal, and performing deskew processing on the broadband signal by using the deskew signal, wherein the specific process comprises the following steps:
obtaining an expression Sigmatch of the broadband signal according to the zero-order coefficient, the first-order coefficient, the second-order coefficient and the third-order coefficient of the broadband signalb(t)＝exp[j2π((α1+α2bt+α3bt2+α4bt3))]
Obtaining the FM slope alpha of the declived signal according to the expression of the broadband signal3b+α4bAnd t, obtaining a deskew signal conjugated with the broadband signal according to the frequency modulation slope of the deskew signal, and carrying out deskew processing on the broadband signal by utilizing the deskew signal to offset a secondary term and a tertiary term of the broadband signal.
For intuitively understanding the scheme of the present invention, as shown in fig. 2, a timing diagram of a wideband pulse, that is, a wideband signal of the present invention, and a timing diagram of a narrowband pulse, that is, a narrowband LFM signal of the present invention are shown, where the timing sequence of the wideband pulse and the narrowband pulse is formed by a plurality of wideband-narrowband pulse matching pulse sequences, and each wideband-narrowband pulse matching pulse sequence includes N narrowband LFM signals with different chirp rates and one wideband signal.
According to the technical scheme, the method for deskewing the broadband polynomial phase signals under the guidance of the narrow-band signals, provided by the invention, is used for extracting the waveform parameters of the spatial target broadband signals on the basis of the continuous narrow-band LFM signals with a plurality of different waveforms, does not need to add extra hardware cost, does not change the existing radar imaging signal processing system, is small in calculation load, obtains the frequency modulation slope of the deskew signals through the quadratic coefficient and the cubic coefficient of the broadband signals, obtains the deskew signals through the frequency modulation slope of the deskew signals, carries out deskew processing on the broadband signals by using the deskew signals, realizes accurate deskew and real-time deskew of the broadband signals, is good in deskew effect, and has important application values on the accurate imaging field of radar and the subsequent target identification.
Example 2
Corresponding to embodiment 1 of the present invention, embodiment 2 of the present invention further provides a wideband polynomial phase signal deskewing apparatus guided by a narrowband signal, the apparatus including:
the transmitting module is used for transmitting a plurality of continuous narrow-band LFM signals;
the receiving module is used for acquiring pulse echoes of a plurality of continuous narrow-band LFM signals;
the delay correlation processing module is used for performing delay correlation processing on each pulse echo to obtain a plurality of narrow-band echo delay signals;
the first Fourier transform module is used for traversing all the narrow-band echo delay signals, fixing time value taking, and performing fractional Fourier transform to obtain a quadratic term coefficient and a cubic term coefficient estimated by each narrow-band echo delay signal;
the second Fourier transform module is used for compensating the pulse echo of each narrowband LFM signal according to the quadratic term coefficient and the cubic term coefficient estimated by each narrowband echo delay signal, and carrying out Fourier transform on the compensated result to obtain the estimated quadratic term coefficient and the zero-order term coefficient of each narrowband echo delay signal;
the first broadband signal coefficient acquisition module is used for obtaining a cubic coefficient of a broadband signal according to the cubic coefficient and the frequency modulation slope of the ith narrowband echo delay signal and the frequency modulation slope of the broadband signal;
the second broadband signal coefficient acquisition module is used for acquiring a k-1 time coefficient of the broadband signal according to the k-1 time coefficient, the frequency modulation slope and the frequency modulation slope of the ith and jth narrowband echo delay signals, wherein the value of k is 1,2 or 3;
and the deskew module is used for obtaining a deskew signal frequency modulation slope according to the quadratic term coefficient and the cubic term coefficient of the broadband signal and carrying out deskew processing on the broadband signal by using the deskew signal.
Specifically, the ith narrowband LFM signal in the transmitting module is
Figure RE-GDA0002719970750000141
N, where i is 1,2,. N is the total number of narrow-band LFM signals, Si(t) is the ith narrowband LFM signal, j is the imaginary symbol, e()Is an exponential function with e as the base, f0Working frequency point common to all narrow band LFM signals, the narrow band LFM signal and the broadband signal share the same working frequency point, kiFor the chirp rate of the ith narrowband LFM signal, BiThe amplitude of the ith narrowband LFM signal.
Specifically, the expression of the pulse echo in the receiving module is
Figure RE-GDA0002719970750000142
Wherein S isr i(t) is the ith pulse echo, α1i、α2i、α3iAnd alpha4iRespectively a zero-order coefficient, a first-order coefficient, a second-order coefficient and a third-order coefficient of the ith narrowband LFM signal, AiThe echo amplitude of the ith narrowband LFM signal.
Specifically, the delay correlation processing module is further configured to: the ith pulse echo is delayed by tau components to obtain the ith narrow-band echo delay signal
Figure RE-GDA0002719970750000147
Wherein (alpha)3i+3α4it) is the instantaneous frequency of the ith narrow-band echo delayed signal.
Specifically, the first fourier transform module is further configured to: by the formula
Figure RE-GDA0002719970750000143
Obtaining a first intermediate quantity
Figure RE-GDA0002719970750000144
And a second intermediate amount
Figure RE-GDA0002719970750000145
The time values t1 and t2 can obtain the relation between the instantaneous frequency of the narrow-band echo delay signal and the first intermediate quantity and the second intermediate quantity
Figure RE-GDA0002719970750000146
Obtaining the cubic coefficient estimated by the narrow-band echo delay signal according to the relation between the instantaneous frequency of the narrow-band echo delay signal and the first intermediate quantity and the second intermediate quantity
Figure RE-GDA0002719970750000151
And coefficient of quadratic term
Figure RE-GDA0002719970750000152
Are respectively as
Figure RE-GDA0002719970750000153
Specifically, the second fourier transform module is further configured to: compensating the pulse echo of each narrow-band LFM signal according to the quadratic form coefficient and the cubic term coefficient estimated by each narrow-band echo delay signal to obtain a compensated result
Figure RE-GDA0002719970750000154
The compensated result is processed by formula
Figure RE-GDA0002719970750000155
Fourier transform is carried out to obtain the first-order coefficient of each narrow-band echo delay signal estimation
Figure RE-GDA0002719970750000156
And zero degree coefficient
Figure RE-GDA0002719970750000157
Specifically, the first wideband signal coefficient obtaining module is further configured to: by the formula
Figure RE-GDA0002719970750000158
Obtaining cubic term coefficient of broadband signal, wherein alpha4bIs the coefficient of the third order term, beta, of the broadband signalbrIs the chirp rate of the wideband signal and,
Figure RE-GDA0002719970750000159
is the coefficient of the cubic term, beta, of the estimated ith narrowband LFM signaliIs the chirp rate of the ith narrowband LFM signal.
Specifically, the second wideband signal coefficient obtaining module is further configured to: by the formula
Figure RE-GDA00027199707500001510
Obtaining the linear relation between the FM slope of the narrow band LFM signal and the k-1 order coefficient, wherein, beta1iFor the chirp rate, beta, of the ith narrowband LFM signal2jFor the chirp rate of the jth narrowband LFM signal, pa1 and pa2 are the first parameter and the second parameter, respectively
Figure RE-GDA00027199707500001511
Figure RE-GDA00027199707500001512
To estimate the k-1 degree coefficients of the ith narrowband LFM signal,
Figure RE-GDA00027199707500001513
is the estimated k-1 order coefficient of the jth narrowband LFM signal;
by the formula alphakb＝βbrPa1+ pa2 obtains the k-1 degree term coefficients of the wideband signal, where αkbIs the k-1 degree coefficient of the broadband signal.
Specifically, the deskew module is further configured to:
obtaining an expression Sigmatch of the broadband signal according to the zero-order coefficient, the first-order coefficient, the second-order coefficient and the third-order coefficient of the broadband signalb(t)＝exp[j2π((α1+α2bt+α3bt2+α4bt3))]
Obtaining the FM slope alpha of the declived signal according to the expression of the broadband signal3b+α4bAnd t, obtaining a deskew signal conjugated with the broadband signal according to the frequency modulation slope of the deskew signal, and carrying out deskew processing on the broadband signal by utilizing the deskew signal to offset a secondary term and a tertiary term of the broadband signal.
The above examples are only intended to illustrate the technical solution of the present invention, but not to limit it; although the present invention has been described in detail with reference to the foregoing embodiments, it will be understood by those of ordinary skill in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some technical features may be equivalently replaced; and such modifications or substitutions do not depart from the spirit and scope of the corresponding technical solutions of the embodiments of the present invention.

Claims (10)

1. A method for wideband polynomial phase signal deskewing under guidance of a narrowband signal, the method comprising:
the method comprises the following steps: transmitting a plurality of continuous narrow-band LFM signals;
step two: acquiring pulse echoes of a plurality of continuous narrow-band LFM signals;
step three: performing delay correlation processing on each pulse echo to obtain a plurality of narrow-band echo delay signals;
step four: traversing all the narrow-band echo delay signals, fixing time value taking, and performing fractional Fourier transform to obtain a quadratic term coefficient and a cubic term coefficient estimated by each narrow-band echo delay signal;
step five: compensating the pulse echo of each narrowband LFM signal according to the estimated quadratic term coefficient and the estimated cubic term coefficient of each narrowband echo delay signal, and performing Fourier transform on the compensated result to obtain the estimated primary term coefficient and the zero-order term coefficient of each narrowband echo delay signal;
step six: obtaining a cubic term coefficient of the broadband signal according to the cubic term coefficient and the frequency modulation slope of the ith narrowband echo delay signal and the frequency modulation slope of the broadband signal;
step seven: obtaining a k-1 time term coefficient of the broadband signal according to the k-1 time term coefficient, the frequency modulation slope and the frequency modulation slope of the ith and jth narrow-band echo delay signals, wherein the value of k is 1,2, 3 or 4;
step eight: and obtaining a frequency modulation slope of the deskew signal according to the quadratic term coefficient and the tertiary term coefficient of the broadband signal, and performing deskew processing on the broadband signal by using the deskew signal.
2. The method according to claim 1, wherein the ith narrowband LFM signal in the first step is a narrowband LFM signal
Figure RE-FDA0002719970740000011
N, where i is 1,2,. N is the total number of narrow-band LFM signals, Si(t) is the ith narrowband LFM signal, j is the imaginary symbol, e()Is an exponential function with e as the base, f0Working frequency point common to all narrow band LFM signals, the narrow band LFM signal and the broadband signal share the same working frequency point, kiFor the chirp rate of the ith narrowband LFM signal, BiThe amplitude of the ith narrowband LFM signal.
3. The method according to claim 1, wherein the expression of the pulse echo in the second step is
Figure RE-FDA0002719970740000021
Wherein S isr i(t) is the ith pulse echo, α1i、α2i、α3iAnd alpha4iRespectively a zero-order coefficient, a first-order coefficient, a second-order coefficient and a third-order coefficient of the ith narrowband LFM signal, AiThe echo amplitude of the ith narrowband LFM signal.
4. The narrowband signal guided wideband polynomial phase signal deskewing method of claim 1, wherein the third step comprises: the ith pulse echo is delayed by tau components to obtain the ith narrow-band echo delay signal
Figure RE-FDA0002719970740000022
Wherein (alpha)3i+3α4it) is the instantaneous frequency of the ith narrow-band echo delayed signal.
5. The narrowband signal guided wideband polynomial phase signal deskewing method of claim 1, wherein the fourth step comprises: by the formula
Figure RE-FDA0002719970740000023
Obtaining a first intermediate quantity
Figure RE-FDA0002719970740000024
And a second intermediate amount
Figure RE-FDA0002719970740000025
The time values t1 and t2 can obtain the relation between the instantaneous frequency of the narrow-band echo delay signal and the first intermediate quantity and the second intermediate quantity
Figure RE-FDA0002719970740000026
Obtaining the cubic coefficient estimated by the narrow-band echo delay signal according to the relation between the instantaneous frequency of the narrow-band echo delay signal and the first intermediate quantity and the second intermediate quantity
Figure RE-FDA0002719970740000027
And coefficient of quadratic term
Figure RE-FDA0002719970740000028
Are respectively as
Figure RE-FDA0002719970740000031
6. The narrowband signal guided wideband polynomial phase signal deskewing method of claim 1, wherein the step five comprises: compensating the pulse echo of each narrow-band LFM signal according to the quadratic form coefficient and the cubic term coefficient estimated by each narrow-band echo delay signal to obtain a compensated result
Figure RE-FDA0002719970740000032
The compensated result is processed by formula
Figure RE-FDA0002719970740000033
Fourier transform is carried out to obtain the first-order coefficient of each narrow-band echo delay signal estimation
Figure RE-FDA0002719970740000034
And zero degree coefficient
Figure RE-FDA0002719970740000035
7. The narrowband signal guided wideband polynomial phase signal deskewing method of claim 1, wherein the sixth step comprises: by the formula
Figure RE-FDA0002719970740000036
Obtaining cubic term coefficient of broadband signal, wherein alpha4bIs the coefficient of the third order term, beta, of the broadband signalbrIs the chirp rate of the wideband signal and,
Figure RE-FDA0002719970740000037
is the coefficient of the cubic term, beta, of the estimated ith narrowband LFM signaliIs the chirp rate of the ith narrowband LFM signal.
8. The narrowband signal guided wideband polynomial phase signal deskewing method of claim 1, wherein the seventh step comprises: by the formula
Figure RE-FDA0002719970740000038
Obtaining the linear relation between the FM slope of the narrow band LFM signal and the k-1 order coefficient, wherein, beta1iFor the chirp rate, beta, of the ith narrowband LFM signal2jFor the chirp rate of the jth narrowband LFM signal, pa1 and pa2 are the first parameter and the second parameter, respectively
Figure RE-FDA0002719970740000039
Figure RE-FDA00027199707400000310
To estimate the k-1 degree coefficients of the ith narrowband LFM signal,
Figure RE-FDA00027199707400000311
is the estimated k-1 order coefficient of the jth narrowband LFM signal;
by the formula alphakb＝βbrPa1+ pa2 obtains the k-1 degree term coefficients of the wideband signal, where αkbIs the k-1 degree coefficient of the broadband signal.
9. The narrowband signal guided wideband polynomial phase signal deskewing method of claim 1, wherein the step eight comprises:
obtaining an expression Sigmatch of the broadband signal according to the zero-order coefficient, the first-order coefficient, the second-order coefficient and the third-order coefficient of the broadband signalb(t)＝exp[j2π((α1+α2bt+α3bt2+α4bt3))]
Obtaining the FM slope alpha of the declived signal according to the expression of the broadband signal3b+α4bAnd t, obtaining a deskew signal conjugated with the broadband signal according to the frequency modulation slope of the deskew signal, and carrying out deskew processing on the broadband signal by utilizing the deskew signal to offset a secondary term and a tertiary term of the broadband signal.
10. An apparatus for wideband polynomial phase deskewing under narrowband signal guidance, the apparatus comprising:
the transmitting module is used for transmitting a plurality of continuous narrow-band LFM signals;
the receiving module is used for acquiring pulse echoes of a plurality of continuous narrow-band LFM signals;
the delay correlation processing module is used for performing delay correlation processing on each pulse echo to obtain a plurality of narrow-band echo delay signals;
the first Fourier transform module is used for traversing all the narrow-band echo delay signals, fixing time value taking, and performing fractional Fourier transform to obtain a quadratic term coefficient and a cubic term coefficient estimated by each narrow-band echo delay signal;
the second Fourier transform module is used for compensating the pulse echo of each narrowband LFM signal according to the quadratic term coefficient and the cubic term coefficient estimated by each narrowband echo delay signal, and carrying out Fourier transform on the compensated result to obtain the estimated quadratic term coefficient and the zero-order term coefficient of each narrowband echo delay signal;
the first broadband signal coefficient acquisition module is used for obtaining a cubic coefficient of a broadband signal according to the cubic coefficient and the frequency modulation slope of the ith narrowband echo delay signal and the frequency modulation slope of the broadband signal;
the second broadband signal coefficient acquisition module is used for acquiring a k-1 time coefficient of the broadband signal according to the k-1 time coefficient, the frequency modulation slope and the frequency modulation slope of the ith and jth narrowband echo delay signals, wherein the value of k is 1,2 or 3;
and the deskew module is used for obtaining a deskew signal frequency modulation slope according to the quadratic term coefficient and the cubic term coefficient of the broadband signal and carrying out deskew processing on the broadband signal by using the deskew signal.
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Citations (18)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5418892A (en) * 1993-01-12 1995-05-23 Board Of Trustees Of The Leland Stanford Junior University Subspace-based line detection
US20100195925A1 (en) * 1999-02-25 2010-08-05 Ludwig Lester F Generation of image data with correction for optical misfocus utilizing fractional powers of the fourier transform operator
CN101833082A (en) * 2010-04-20 2010-09-15 中国科学院空间科学与应用研究中心 Wideband frequency-modulation stepping signal processing method based on full deskew
CN101963662A (en) * 2010-09-20 2011-02-02 北京理工大学 Self-focusing preprocessing method based on short-time fractional order Fourier domain filter
CN104391298A (en) * 2014-11-28 2015-03-04 中国电子科技集团公司第三十八研究所 Digital delaying compensation device and method and achieving device and method
CN105301590A (en) * 2015-11-03 2016-02-03 南京信息职业技术学院 Maneuvering object frequency modulation stepping retrosynthesis aperture imaging method
US20160091421A1 (en) * 2013-03-21 2016-03-31 Technical University Of Denmark Refractive index based measurements
CN106597440A (en) * 2016-12-12 2017-04-26 南京信息职业技术学院 Low-SNR imaging method of frequency-modulated stepping radar
CN106872974A (en) * 2017-01-23 2017-06-20 西安电子科技大学 High-precision motion target imaging method based on hypersonic platform Two-channels radar
CN108008369A (en) * 2017-11-30 2018-05-08 中国科学院国家空间科学中心 A kind of NLFM signal lack sampling processing method
CN108107430A (en) * 2017-11-09 2018-06-01 北京理工大学 A kind of Ship Target ISAR imaging methods based on fraction Fourier conversion
CN108152820A (en) * 2017-12-20 2018-06-12 西安电子科技大学 A kind of bistatic radar imaging method based on chromatographic theory
KR20180072972A (en) * 2016-12-22 2018-07-02 한국항공우주연구원 Apparatus and method for digital dechirp processing
CN108318879A (en) * 2017-12-29 2018-07-24 哈尔滨工业大学 ISAR image transverse direction calibrating methods based on IAA Power estimation technologies
CN108919221A (en) * 2018-07-17 2018-11-30 武汉大学 A kind of phase-coherent accumulation detection method for variable accelerated motion target
CN110146889A (en) * 2019-06-17 2019-08-20 中国人民解放军国防科技大学 Large-rotation-angle ISAR imaging method based on optimal echo sub-region selection
CN110988874A (en) * 2019-11-08 2020-04-10 西北大学 ISAR imaging method for complex moving target
CN111505640A (en) * 2020-06-24 2020-08-07 深圳大学 Method and system for deskew one-bit acquisition of broadband radar echo

Patent Citations (18)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5418892A (en) * 1993-01-12 1995-05-23 Board Of Trustees Of The Leland Stanford Junior University Subspace-based line detection
US20100195925A1 (en) * 1999-02-25 2010-08-05 Ludwig Lester F Generation of image data with correction for optical misfocus utilizing fractional powers of the fourier transform operator
CN101833082A (en) * 2010-04-20 2010-09-15 中国科学院空间科学与应用研究中心 Wideband frequency-modulation stepping signal processing method based on full deskew
CN101963662A (en) * 2010-09-20 2011-02-02 北京理工大学 Self-focusing preprocessing method based on short-time fractional order Fourier domain filter
US20160091421A1 (en) * 2013-03-21 2016-03-31 Technical University Of Denmark Refractive index based measurements
CN104391298A (en) * 2014-11-28 2015-03-04 中国电子科技集团公司第三十八研究所 Digital delaying compensation device and method and achieving device and method
CN105301590A (en) * 2015-11-03 2016-02-03 南京信息职业技术学院 Maneuvering object frequency modulation stepping retrosynthesis aperture imaging method
CN106597440A (en) * 2016-12-12 2017-04-26 南京信息职业技术学院 Low-SNR imaging method of frequency-modulated stepping radar
KR20180072972A (en) * 2016-12-22 2018-07-02 한국항공우주연구원 Apparatus and method for digital dechirp processing
CN106872974A (en) * 2017-01-23 2017-06-20 西安电子科技大学 High-precision motion target imaging method based on hypersonic platform Two-channels radar
CN108107430A (en) * 2017-11-09 2018-06-01 北京理工大学 A kind of Ship Target ISAR imaging methods based on fraction Fourier conversion
CN108008369A (en) * 2017-11-30 2018-05-08 中国科学院国家空间科学中心 A kind of NLFM signal lack sampling processing method
CN108152820A (en) * 2017-12-20 2018-06-12 西安电子科技大学 A kind of bistatic radar imaging method based on chromatographic theory
CN108318879A (en) * 2017-12-29 2018-07-24 哈尔滨工业大学 ISAR image transverse direction calibrating methods based on IAA Power estimation technologies
CN108919221A (en) * 2018-07-17 2018-11-30 武汉大学 A kind of phase-coherent accumulation detection method for variable accelerated motion target
CN110146889A (en) * 2019-06-17 2019-08-20 中国人民解放军国防科技大学 Large-rotation-angle ISAR imaging method based on optimal echo sub-region selection
CN110988874A (en) * 2019-11-08 2020-04-10 西北大学 ISAR imaging method for complex moving target
CN111505640A (en) * 2020-06-24 2020-08-07 深圳大学 Method and system for deskew one-bit acquisition of broadband radar echo

Non-Patent Citations (7)

* Cited by examiner, † Cited by third party
Title
D. LI, M. ZHAN, H. LIU, Y. LIAO AND G. LIAO: "A Robust Translational Motion Compensation Method for ISAR Imaging Based on Keystone Transform and Fractional Fourier Transform Under Low SNR Environment", 《IEEE》, pages 2140 - 2156 *
H. ZHAO, L. QIAO, L. DENG AND Y. CHEN: "Construction of chaotic sensing matrix for fractional bandlimited signal associated by fractional fourier transform", 《IEEE》, pages 1 - 7 *
刘小忠,闵威,张孟达,朱子平: "宽带独立信号和相干信号的DOA估计", 《雷达科学与技术》, vol. 12, no. 6, pages 619 - 622 *
罗文茂,崔应留: "一种基于去斜的高速目标ISAR成像新方法", 《系统仿真学报》, pages 851 - 858 *
袁斌;唐鹏飞;徐世友;陈曾平;: "基于FRFT的一维距离像高速运动补偿", 雷达科学与技术, no. 03, pages 84 - 89 *
陈赫: "高速运动目标一维成像研究", 《中国优秀硕士学位论文全文数据库 信息科技辑》, pages 136 - 2322 *
魏耀: "宽带雷达高速运动目标检测与成像处理研究", 《中国优秀博士学位论文全文数据库 信息科技辑》, pages 136 - 303 *

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