CN111865158B - Speed sensorless control method of self-adaptive sliding mode gain permanent magnet synchronous motor - Google Patents

Speed sensorless control method of self-adaptive sliding mode gain permanent magnet synchronous motor Download PDF

Info

Publication number
CN111865158B
CN111865158B CN202010715960.1A CN202010715960A CN111865158B CN 111865158 B CN111865158 B CN 111865158B CN 202010715960 A CN202010715960 A CN 202010715960A CN 111865158 B CN111865158 B CN 111865158B
Authority
CN
China
Prior art keywords
sliding mode
current
adaptive
motor
mode gain
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN202010715960.1A
Other languages
Chinese (zh)
Other versions
CN111865158A (en
Inventor
申永鹏
王延峰
叶晨光
胡智宏
刘普
杨小亮
张志艳
邱洪波
赵俊
杜海明
武洁
郭磊磊
郑竹风
李元丰
王前程
王帅兵
刘迪
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Zhengzhou University of Light Industry
Original Assignee
Zhengzhou University of Light Industry
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Zhengzhou University of Light Industry filed Critical Zhengzhou University of Light Industry
Priority to CN202010715960.1A priority Critical patent/CN111865158B/en
Publication of CN111865158A publication Critical patent/CN111865158A/en
Application granted granted Critical
Publication of CN111865158B publication Critical patent/CN111865158B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/0003—Control strategies in general, e.g. linear type, e.g. P, PI, PID, using robust control
    • H02P21/001—Control strategies in general, e.g. linear type, e.g. P, PI, PID, using robust control using fuzzy control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/13—Observer control, e.g. using Luenberger observers or Kalman filters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/22—Current control, e.g. using a current control loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/34—Modelling or simulation for control purposes
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2205/00—Indexing scheme relating to controlling arrangements characterised by the control loops
    • H02P2205/01—Current loop, i.e. comparison of the motor current with a current reference
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2207/00—Indexing scheme relating to controlling arrangements characterised by the type of motor
    • H02P2207/05—Synchronous machines, e.g. with permanent magnets or DC excitation

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Automation & Control Theory (AREA)
  • Fuzzy Systems (AREA)
  • Control Of Ac Motors In General (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)

Abstract

The invention discloses a speed sensorless control method of a self-adaptive sliding mode gain permanent magnet synchronous motor, which comprises the following steps of: collecting three-phase stator currents of a tested motor respectively
Figure DEST_PATH_IMAGE002
、
Figure DEST_PATH_IMAGE004
、
Figure DEST_PATH_IMAGE006
(ii) a And obtaining the measured current by Clark transformation
Figure DEST_PATH_IMAGE008
、
Figure DEST_PATH_IMAGE010
(ii) a Calculating the observed current value by using a motor mathematical model
Figure DEST_PATH_IMAGE012
、
Figure DEST_PATH_IMAGE014
Calculating a sliding mode gain adaptation rate K, and applying the sliding mode gain adaptation rate to the mathematical model of the motor in S2 for correcting the current error value between the measured current value and the observed current value
Figure DEST_PATH_IMAGE016
Gradually approaching zero. The adaptive sliding mode gain observer adopted by the invention can enable the measured motor to be configured with the adaptive gain factor in real time, and better improve the sliding mode jitterThe vibration phenomenon improves the observation precision; meanwhile, a current curve obtained by the adaptive sliding mode gain observer is smoother, buffeting content is less, and operation is more stable.

Description

Speed sensorless control method of self-adaptive sliding mode gain permanent magnet synchronous motor
Technical Field
The invention belongs to the technical field of motor control, and particularly relates to a speed sensorless control method of a self-adaptive sliding mode gain permanent magnet synchronous motor.
Background
A control method of a permanent magnet synchronous motor self-adaptive sliding mode observer is a very common use method in the control of the existing permanent magnet synchronous motor. The sliding-mode observer is a dynamic system that derives state variable estimates from measured values of external variables (input variables and output variables) of the system, also known as a state reconstructor. The sliding-mode observer not only provides practical possibility for the technical realization of state feedback, but also is practically applied to many aspects of control engineering. The sliding mode observer can obtain an estimated value of the internal state of a given system by measuring the input and the output of the actual system. The sliding-mode observer uses nonlinear high-gain feedback to force the estimated state to approach the hyperplane, so that the estimated output is equal to the measured output. The performance of the control system is tested by building a control experiment platform of the self-adaptive sliding mode observer of the permanent magnet synchronous motor, collecting and analyzing related data according to the operation of the motor under different working conditions. As shown in fig. 1, the conventional control method of the adaptive sliding mode observer is composed of a measured current output link of a motor, an observed current output link estimated by a motor model, and a sliding mode adaptive control part, and an error value is fed back to the motor model in a closed-loop manner. The existing control method of the permanent magnet synchronous motor self-adaptive sliding mode observer has the following defects: 1. the sliding mode buffeting existing in the sliding mode observation control system is large; 2. the phase current output is unstable, and a sawtooth waveform exists around the peak value of the phase current curve; 3. the observation precision of the sliding-mode observer is low; 4. a fixed adaptation factor is employed throughout the system, however, the adaptation factor is not made to vary in accordance with changes in the control system using an adaptive sliding mode gain.
Disclosure of Invention
The invention aims to provide a speed sensorless control method of a self-adaptive sliding mode gain permanent magnet synchronous motor, which can better improve the sliding mode buffeting phenomenon and improve the observation precision.
In order to achieve the purpose, the invention adopts the following technical scheme:
a speed sensorless control method of a self-adaptive sliding mode gain permanent magnet synchronous motor comprises the following steps: s1, collecting three-phase stator currents of the motor to be detected through a current sensor, wherein the three-phase stator currents are ia、ib、ic(ii) a And the three-phase stator current is converted by Clark to obtain the measured current iα、iβ(ii) a Finally, outputting the measured current;
s2, calculating the observed current value i by using a motor mathematical modelα *、iβ *，
S3, calculating a sliding mode gain adaptive rate K, and applying the sliding mode gain adaptive rate to the motor mathematical model in S2 to correct a current error value delta between a measured current value and an observed current value to gradually approach zero.
Further, in S2, the mathematical model formula of the motor is:
Figure BDA0002598154690000021
wherein iα *、iβ *Respectively, are the observed current components of the current,
Figure BDA0002598154690000022
Figure BDA0002598154690000023
respectively, a back electromotive force component, Zα、ZβIs the output correction factor component of the sliding mode controller, R is the stator resistance, L is the stator inductance, u is the output correction factor component of the sliding mode controllerα、uβStator voltages on an alpha coordinate system and a beta coordinate system;
Figure BDA0002598154690000024
estimating the observed current value i by using a motor mathematical modelα *、iβ *Then, the self-adaptive gain factor is fed back to the motor model, the difference value of the measured current and the observed current is judged, and the difference value of the measured current and the observed current is corrected through the self-adaptive gain factor to gradually approach zero, so that the observed current is closer to the measured current.
Further, the sliding mode observer is required to control when the sliding mode gain adaptive rate K is calculated in S3, when the sliding mode observer is adopted to control, it is observed that a large ripple chattering appears in an output waveform of the motor current in a sampling frequency period, the chattering is a real error δ existing between an observed current and a measured current when the permanent magnet synchronous motor operates, and the formula is
Figure BDA0002598154690000031
In order to overcome the current error existing in the control system, a sliding mode gain adaptive factor is introduced, an output error is utilized to drive an adaptive structure, a sliding mode gain adaptive rate K is obtained, and the sliding mode gain adaptive rate K is obtained according to a formula
Figure BDA0002598154690000032
The current output error is made to vary with the adaptation rate. The parameters to be estimated can be continuously corrected under the action of the self-adaptive rate, so that the output error of the sliding mode observation model tends to zero.
Essentially, a constant boundary layer thickness is the root cause for poor performance of the saturation function. Therefore, in order to improve the control performance of the saturation function, a continuously variable adaptive coefficient is required to control the change of the function, so that the thickness of the boundary layer can be narrowed along with the convergence of the system state trajectory, and finally the boundary layer is overlapped with the switching plane, and the aim of converging the system trajectory on the given switching plane is fulfilled. When the control function is continuously changed, an approach angle is formed between the control function and the abscissa axis, the approach angle is an included angle between the system state track and the switching plane and is reduced along with the approach of the state track to the switching plane, so that the approach angle is the most intuitive variable for measuring the convergence degree of the state track, and the approach angle is used as a self-adaptive coefficient of function change to construct a boundary layer thickness function.
The internal relation among the effective value of the current, the current error value and the adaptive factor is found out by calculating the effective value of the measured current, and the sliding mode gain adaptive rate is obtained, so that the error amount of the current in the control system is effectively reduced.
Sliding mode adaptation rate in S3K is calculated by the formula
Figure BDA0002598154690000033
Wherein
Figure BDA0002598154690000034
The effective value of the current in the whole period number. Where r is the adaptive rate coefficient of the functional relation. Using current error value (delta) and current effective value
Figure BDA0002598154690000035
The change relation exists between the sliding mode control system and the sliding mode control system, the value of the coefficient r is determined, and the self-adaptive rate is always controlled within a fixed range, so that the error between the measured current and the observed current is effectively overcome, and the whole sliding mode control system is in a stable and accurate observation state.
Further, the effective value of the current in the whole period number
Figure BDA0002598154690000041
The calculation formula of (2) is as follows:
Figure BDA0002598154690000042
wherein
Figure BDA0002598154690000043
jIs a data sample index; p is the number of periodic cycles; m is the sampling number in the period defined by the filtered synchronous signal; mpThe number of sampling points in the cycle number; m is an initial sampling point index;mpis the index of the initial sampling point of the cycle number; n is the number of cycles (defined by the selected sync source signal);
Figure BDA0002598154690000044
is the effective value of the current in each period.
Effective value of phase current under different working conditions
Figure BDA0002598154690000045
The permanent magnet synchronous motor can be driven in different working conditions according to the formula in the simulation processAnd operating under the condition of the temperature, thus obtaining the temperature.
According to the method, the sliding mode gain self-adaptive factor is introduced by utilizing the current error value between the measured current and the observed current, so that the sliding mode gain self-adaptive rate K is obtained, the self-adaptive gain factor can change along with the magnitude of the current error in the control system, the current error can be better reduced and approaches to zero, the measured current is closer to the actual current, and the sliding mode buffeting phenomenon is better improved.
The method of the invention has the following advantages:
firstly, compare in traditional sliding mode observer control method. The adaptive sliding mode gain observer adopted by the invention can enable the measured motor to be configured with the adaptive gain factor in real time, better improve the phenomenon of sliding mode buffeting and improve the observation precision.
Compared with the traditional sliding mode observer, the self-adaptive sliding mode gain observer has the advantages that the obtained current curve is smoother, the buffeting content is less, and the operation is more stable.
Drawings
FIG. 1 is a schematic diagram of a control structure of a conventional permanent magnet synchronous motor adaptive sliding mode observer;
FIG. 2 is a diagram of a non-speed sensor control design for an adaptive sliding film gain PMSM according to the present invention;
FIG. 3 is a control flow chart of the present invention;
FIG. 4 is a waveform of a stator current at a rotation speed of 1500 r/min;
FIG. 5 shows the waveform changes of the actual rotation speed and the observed rotation speed at the steady state rotation speed of 1500 r/min;
FIG. 6 shows the waveform and error of the rotor position at 1500 r/min.
Detailed Description
In order to make the technical problems solved, technical solutions adopted and technical effects achieved by the present invention clearer, the technical solutions of the embodiments of the present invention will be described in further detail below with reference to the accompanying drawings, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
As shown in fig. 2, a method for controlling a speed sensorless adaptive sliding mode gain permanent magnet synchronous motor. The method comprises the following steps: the motor error correction method comprises a measuring current output link of a motor, an observation current output link estimated by a motor model and a self-adaptive sliding mode gain control part, wherein in order to enable the measuring current to be matched with the observation current, an error value is fed back to the motor model in a closed-loop mode, so that the current error value is corrected. The specific embodiment is implemented as follows:
and S1, outputting the measured current of the motor. The three-phase stator current of the tested motor is acquired through a current sensor and is i respectivelya、ib、ic(ii) a And the three-phase stator current is converted by Clark to obtain the measured current iα、iβ(ii) a Finally, outputting the measured current;
and S2, estimating an observation current output link by the motor model. Calculating an observed current value i by using a motor mathematical modelα *、iβ *，
The mathematical model formula of the motor is as follows:
Figure BDA0002598154690000051
wherein iα *、iβ *Respectively, are the observed current components of the current,
Figure BDA0002598154690000052
Figure BDA0002598154690000053
respectively, a back electromotive force component, Zα、ZβIs the output correction factor component of the sliding mode controller, R is the stator resistance, L is the stator inductance, u is the output correction factor component of the sliding mode controllerα、uβStator voltages on an alpha coordinate system and a beta coordinate system;
Figure BDA0002598154690000061
according to the formula, the self-adaptive gain factor is fed back to the motor model through the sliding mode gain self-adaptive rate K, the difference value of the measured current and the observed current is judged, and the difference value of the measured current and the observed current is corrected through the self-adaptive gain factor to enable the difference value to gradually approach zero.
And S3, adaptive sliding mode gain control. Calculating the self-adaptive rate K of the sliding mode gain, and controlling by using a sliding mode observer during calculation according to the formula
Figure BDA0002598154690000062
Wherein
Figure BDA0002598154690000063
The effective value of the current in the whole period number,
Figure BDA0002598154690000064
where r is the adaptive rate coefficient of the functional relation. Using current error value (delta) and current effective value
Figure BDA0002598154690000065
The change relation exists between the sliding mode control system and the sliding mode control system, the value of the coefficient r is determined, and the self-adaptive rate is always controlled within a fixed range, so that the error between the measured current and the observed current is effectively overcome, and the whole sliding mode control system is in a stable and accurate observation state.
Effective value of current in the whole period
Figure BDA0002598154690000066
The calculation formula of (2) is as follows:
Figure BDA0002598154690000067
wherein
Figure BDA0002598154690000068
j is the data sample index; p is the number of periodic cycles; m is the sampling number in the period defined by the filtered synchronous signal; mpThe number of sampling points in the cycle number; m is an initial sampling point index; m ispIs the index of the initial sampling point of the cycle number; n is the number of cycles (defined by the selected sync source signal);
Figure BDA0002598154690000069
is the effective value of the current in each period.
After calculating the self-adaptive rate K of the sliding mode gain, the formula is used
Figure BDA00025981546900000610
The sliding mode gain adaptation rate is applied to the mathematical model of the motor in S2 to correct the current error value δ between the measured current value and the observed current value to gradually approach zero. At the moment, the sliding mode gain factor can be changed according to the change of the control system, and is not fixed, so that the observation precision of the system is better improved.
Fig. 3 shows a specific control flow chart of the present invention, wherein the stator voltage value of the motor is inputted into the computer input interface before the steps in fig. 2 are implemented, the computer sends the electronic voltage value to the motor controller, and the controller drives the motor to operate and obtains the measured current value through the current sensor.
In order to verify the speed sensorless control system of the permanent magnet synchronous motor based on the self-adaptive sliding mode observer, the method disclosed by the invention is adopted, and a simulation model is built according to the control system, wherein the main specification parameters of the adopted PMSM are shown in table 1.
TABLE 1 PMSM Specification parameters
Figure BDA0002598154690000071
The experimental results are as follows:
the A-phase stator current waveform is obtained by using an adaptive sliding mode gain observer and a traditional sliding mode observer at the rotating speed of 1500r/min as shown in figure 4. According to the simulation result, the buffeting amplitude of the simulation waveform obtained by the adaptive sliding mode gain observer is small under a certain rotating speed, and the buffeting amplitude is effectively weakened.
The motor rotating speed waveform at the steady state is obtained by using an adaptive sliding mode gain observer and a traditional sliding mode observer at the rotating speed of 1500r/min as shown in figure 5. By comparison, the rotating speed error obtained by the traditional sliding mode observer is at least 8r/min, the rotating speed error obtained by the adaptive sliding mode gain observer is 5r/min, and meanwhile, the rotating speed curve obtained by the adaptive sliding mode gain observer has less buffeting content and higher observation precision.
FIG. 6 shows the target rotor position, observed rotor position, and rotor position error waveforms obtained using an adaptive sliding mode gain observer and a conventional sliding mode observer at a rotation speed of 1500 r/min. According to the waveform comparison, the buffeting amplitude and the rotor position error of the observed rotor position of the traditional sliding mode observer are large, the self-adaptive sliding mode gain observer effectively improves the observation precision, weakens the buffeting amplitude, reduces the rotor position error and has good dynamic performance.

Claims (4)

1. A speed sensorless control method of a self-adaptive sliding mode gain permanent magnet synchronous motor is characterized by comprising the following steps:
s1, collecting three-phase stator currents of the tested motor, wherein the three-phase stator currents are ia、ib、ic(ii) a And obtaining the measurement current i through Clark transformationα、iβ；
S2, calculating the observed current value i by using a motor mathematical modelα *、iβ *Wherein the motor mathematical model formula is as follows:
Figure FDA0003348156130000011
wherein iα *、iβ *Respectively, are the observed current components of the current,
Figure FDA0003348156130000012
respectively, a back electromotive force component, Zα、ZβIs the output correction factor component of the sliding mode controller, R is the stator resistance, L is the stator inductance, u is the output correction factor component of the sliding mode controllerα、uβStator voltages on an alpha coordinate system and a beta coordinate system;
Figure FDA0003348156130000013
s3, calculating a sliding mode gain adaptive rate K, and applying the sliding mode gain adaptive rate to the motor mathematical model in S2 to correct a current error value delta between a measured current value and an observed current value to gradually approach zero.
2. The method for controlling the non-speed sensor of the adaptive sliding mode gain permanent magnet synchronous motor according to claim 1, wherein the calculation formula of the sliding mode adaptive rate K in S3 is
Figure FDA0003348156130000014
Wherein
Figure FDA0003348156130000015
The effective value of the current in the whole period number.
3. The method as claimed in claim 1, wherein the current error value δ in S3 is calculated by the following formula:
Figure FDA0003348156130000016
4. the adaptive sliding mode gain PMSM speed sensorless control method of claim 2, wherein the effective value of current over the entire cycle number
Figure FDA0003348156130000021
The calculation formula of (2) is as follows:
Figure FDA0003348156130000022
wherein
Figure FDA0003348156130000023
j is the data sample index; p is the number of cyclesCounting; m is the sampling number in the period defined by the filtered synchronous signal; mpThe number of sampling points in the cycle number; m is an initial sampling point index; m ispIs the index of the initial sampling point of the cycle number; n is the number of cycles;
Figure FDA0003348156130000024
is the effective value of the current in each period.
CN202010715960.1A 2020-07-23 2020-07-23 Speed sensorless control method of self-adaptive sliding mode gain permanent magnet synchronous motor Active CN111865158B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202010715960.1A CN111865158B (en) 2020-07-23 2020-07-23 Speed sensorless control method of self-adaptive sliding mode gain permanent magnet synchronous motor

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202010715960.1A CN111865158B (en) 2020-07-23 2020-07-23 Speed sensorless control method of self-adaptive sliding mode gain permanent magnet synchronous motor

Publications (2)

Publication Number Publication Date
CN111865158A CN111865158A (en) 2020-10-30
CN111865158B true CN111865158B (en) 2022-04-01

Family

ID=72950650

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202010715960.1A Active CN111865158B (en) 2020-07-23 2020-07-23 Speed sensorless control method of self-adaptive sliding mode gain permanent magnet synchronous motor

Country Status (1)

Country Link
CN (1) CN111865158B (en)

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103199788A (en) * 2013-04-19 2013-07-10 哈尔滨工业大学 Permanent magnet synchronous motor rotor position observer
CN103414423A (en) * 2013-08-22 2013-11-27 东南大学 Surface-mounted permanent magnet synchronous motor sensorless direct torque control method
CN104601072A (en) * 2015-02-02 2015-05-06 宁波申菱电梯配件有限公司 Whole-speed range control method of position sensor of elevator door motor
CN108599645A (en) * 2018-04-18 2018-09-28 西安理工大学 Permanent magnet synchronous motor method for controlling position-less sensor based on sliding mode observer

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103199788A (en) * 2013-04-19 2013-07-10 哈尔滨工业大学 Permanent magnet synchronous motor rotor position observer
CN103414423A (en) * 2013-08-22 2013-11-27 东南大学 Surface-mounted permanent magnet synchronous motor sensorless direct torque control method
CN104601072A (en) * 2015-02-02 2015-05-06 宁波申菱电梯配件有限公司 Whole-speed range control method of position sensor of elevator door motor
CN108599645A (en) * 2018-04-18 2018-09-28 西安理工大学 Permanent magnet synchronous motor method for controlling position-less sensor based on sliding mode observer

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
《一种变增益宽速度范围的永磁同步电机无位置传感器控制》;张磊等;《电机与控制学报》;20150831;第19卷(第8期);第37-38页 *

Also Published As

Publication number Publication date
CN111865158A (en) 2020-10-30

Similar Documents

Publication Publication Date Title
CN110572091B (en) Optimized sensorless control method for permanent magnet synchronous motor
CN108092567B (en) Permanent magnet synchronous motor rotating speed control system and method
CN103312244B (en) Based on the brshless DC motor Direct Torque Control of segmented sliding moding structure
CN107070341A (en) Permagnetic synchronous motor method for suppressing torque ripple based on Robust Iterative Learning Control
CN111293947B (en) Improved permanent magnet synchronous motor speed sensorless control method
CN109873582B (en) Limited time position tracking control method of permanent magnet synchronous motor based on dynamic surface
CN113364377B (en) Permanent magnet synchronous motor active disturbance rejection position servo control method
CN112532133B (en) Filtering compensation sliding mode active-disturbance-rejection control method suitable for permanent magnet synchronous motor
CN109713971B (en) Disturbance suppression method for permanent magnet synchronous motor
CN112422002B (en) Robust permanent magnet synchronous motor single current sensor prediction control method
CN110620533A (en) Surface-mounted permanent magnet synchronous motor sensorless control method
CN109510539B (en) Model prediction flux linkage control system and method based on gain matrix
CN108512476B (en) Induction motor rotating speed estimation method based on Longbeige observer
CN111865158B (en) Speed sensorless control method of self-adaptive sliding mode gain permanent magnet synchronous motor
CN113037161A (en) Model reference self-adaptive permanent magnet synchronous motor position-sensorless vector control method based on super-distortion sliding mode algorithm
CN110995094B (en) Permanent magnet synchronous motor position and speed estimation method under low carrier ratio control
CN115459667B (en) Permanent magnet synchronous motor sensorless sliding mode control method based on improved approach law
CN115133828A (en) Permanent magnet synchronous motor control method and system
CN111181462B (en) Surface-mounted permanent magnet synchronous motor parameter identification method based on variable step size neural network
CN112803860A (en) Permanent magnet motor control method based on output feedback sliding mode control and anti-saturation PI
CN112234877A (en) Brushless direct current motor phase commutation error compensation method based on trapezoidal wave back electromotive force
Han et al. Research on PMSM sensor-less system based on ADRC strategy
CN111030543A (en) Zero-speed closed-loop starting method of direct-current variable-frequency air conditioner compressor
CN115360953B (en) Induction motor oscillation suppression method based on rotor flux orientation
CN111900908B (en) Permanent magnet synchronous motor rotor position and speed estimation method based on dead beat back electromotive force predictor

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant