CN110912431A - Inverter circulating current restraining method based on model prediction virtual voltage vector control - Google Patents

Inverter circulating current restraining method based on model prediction virtual voltage vector control Download PDF

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CN110912431A
CN110912431A CN201911270613.6A CN201911270613A CN110912431A CN 110912431 A CN110912431 A CN 110912431A CN 201911270613 A CN201911270613 A CN 201911270613A CN 110912431 A CN110912431 A CN 110912431A
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金涛
黄宇升
张伟锋
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Fuzhou University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/487—Neutral point clamped inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/493—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode the static converters being arranged for operation in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current

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Abstract

The invention relates to a model prediction virtual voltage vector control-based three-level NPC inverter zero sequence circulating current suppression method, which comprises the steps of selecting 7 voltage vectors which contribute to zero sequence circulating current from three-level inverters as basic vectors by analyzing space vectors of the three-level inverters, synthesizing 12 virtual voltage vectors by the basic vectors, effectively suppressing the zero sequence circulating current of a parallel system, simultaneously remarkably reducing the distortion rate of output current of the parallel system, improving the quality of grid-connected current, and being very suitable for a three-level inverter system running in parallel.

Description

Inverter circulating current restraining method based on model prediction virtual voltage vector control
Technical Field
The invention relates to the field of NPC (neutral point clamped) inverters, in particular to an inverter circulating current restraining method based on model prediction virtual voltage vector control.
Background
In recent years, the photovoltaic and wind power of China show explosive growth, and according to the report of energy development in China in 2018, the wind power and the photovoltaic installation of China are respectively 1.84 hundred million kilowatts and 1.7 hundred million kilowatts, and are the first in the world in average. How to deliver the part of the electric energy to the power grid with high efficiency, high quality and low cost has been a research hotspot in recent decades. Neutral-Point Clamped (NPC) three-level inverter has the advantages of small output harmonic, high system efficiency, low switching stress and the like, and is widely applied to the field of new energy power generation. However, a single three-level inverter is difficult to meet the application scenarios of large-scale photovoltaic and wind power, so that the parallel operation of multiple inverters becomes the mainstream trend, and the system reliability and the cost can be improved and reduced while the system output power is improved.
However, due to the problems of hardware parameter difference, dead time, control signal delay and the like, zero-sequence loop current is generated between inverters, so that the operation performance of the system is seriously affected, for example, the system loss is increased, the output current is seriously distorted, the neutral point voltage is deviated and the like, and the system is seriously crashed.
Disclosure of Invention
In view of this, the present invention aims to provide a method for suppressing inverter circulating current based on model prediction virtual voltage vector control, which can effectively suppress zero sequence circulating current in a system and also can significantly reduce distortion rate of inverter output current, thereby reducing system loss, improving output current quality and improving system reliability.
In order to achieve the purpose, the invention adopts the following technical scheme:
a method for restraining the circulating current of an inverter based on model prediction virtual voltage vector control comprises the following steps:
step S1: collection ia1(k)，ib1(k)，ic1(k)，VC1P(k)，VC1N(k) E (k), the value at time k;
wherein ia1，ib1，ic1Three-phase filter inductor current, V, of an upper three-level NPC inverter, respectivelyC1P，VC1NUpper side of three-level NPC inverter respectivelyLower support capacitor voltage, e is grid voltage of grid side;
step S2, the optimal switching vector v found in the last switching period is adoptedopt；
Step S3, calculating the current reference value i at the moment k +2*(k +2), the grid voltage e (k +1) at time k + 1;
step S4, calculating the three-phase output current value i of the inverter at the moment of k +1p(k+1)；
Step S5, predicting the current at the k +2 moment according to the alternative voltage vector;
step S6: according to the alternative voltage vector, predicting the difference value of the capacitor voltages on the upper side and the lower side of the same inverter at the k +2 moment;
step S7, calculating cost function values according to the cost function according to the predicted values obtained in the step S4 and the step S5;
step S8, comparing the values of the cost function obtained in the step S6, taking the smaller value, and recording the smaller value as gopt；
Step S9, judging whether the prediction and optimization of all 19 alternative voltage vectors are finished, if so, entering the step S10; if not, returning to the step S4 to predict the next alternative vector;
step S10, get and goptCorresponding optimal switching state SoptAnd an optimal voltage vector.
Further, the 19 candidate voltage vectors include 7 actual voltage vectors and 12 virtual voltage vectors, and the contribution of the 19 candidate voltage vectors to the zero-sequence circulating current is zero.
Furthermore, the 12 virtual voltage vectors are synthesized pairwise by 7 actual voltage vectors, and the action time of each actual voltage vector is half of the control period.
Further, the step S5 is specifically: substituting the candidate voltage vector into the equation to predict the current at time k +2
Figure BDA0002314060900000031
In the formula: i.e. ipFor current prediction, R is the filter inductance and the equivalent resistance of the line, TsIs the control period of the controller.
Further, the step S6 is specifically: and substituting the candidate voltage vector into the following formula to predict the difference value of the upper side capacitor voltage and the lower side capacitor voltage of the same inverter at the moment k + 2:
Figure BDA0002314060900000032
in the formula: Δ V1 pThe predicted value of the voltage difference of the upper/lower support capacitors of the upper inverter is C, the capacitance value of the DC support capacitor is C, H represents a variable related to the switch state, and the value of H is 0 or 1.
Further, the step S7 is specifically: substituting the predicted values obtained in the steps S4 and S5 into a cost function shown as the following formula;
Figure BDA0002314060900000041
in the formula:
Figure BDA0002314060900000042
respectively α components of the reference current,
Figure BDA0002314060900000043
α components, λ, of the predicted current, respectivelydcThe weight coefficient is the midpoint balance of the direct current side.
Further, the first candidate vector in the candidate vector library is applied in the first period of step S2.
Compared with the prior art, the invention has the following beneficial effects:
according to the invention, through analyzing the equivalent circuit of the zero-sequence circulating current of the three-level NPC inverter running in parallel with the common alternating current-direct current bus, 7 voltage vectors capable of effectively inhibiting the zero-sequence circulating current are selected as basic vectors, and 12 virtual voltage vectors are synthesized according to the 7 basic vectors to enrich the alternative voltage vector library, so that the distortion rate of the output current of the system can be remarkably reduced while the zero-sequence circulating current is effectively inhibited.
Drawings
FIG. 1 is a flow chart of a method in one embodiment of the present invention;
FIG. 2 is a space voltage vector diagram in one embodiment of the present invention;
FIG. 3 is a schematic diagram of the overall system architecture in one embodiment of the present invention;
fig. 4 is a zero sequence circulating current equivalent circuit diagram of the system in an embodiment of the present invention.
Detailed Description
The invention is further explained below with reference to the drawings and the embodiments.
Referring to fig. 1, the present invention provides a method for suppressing inverter circulating current based on model-based virtual voltage vector prediction, including the following steps:
step S1: measurement ia1(k)，ib1(k)，ic1(k)，VC1P(k)，VC1N(k) E (k), the value at time k; wherein ia1，ib1，ic1Three-phase filter inductive current of the upper three-level NPC inverter is acquired by a Hall current transformer, and V isC1P，VC1NThe capacitor voltage is respectively supported by the upper side and the lower side of the upper three-level NPC inverter and acquired through a Hall voltage transformer, and e is the grid voltage of the grid-connected side and acquired through the Hall voltage transformer;
step S2: using the optimum switching vector v found in the last switching cycleopt(the first alternative vector in the alternative vector library is applied in the first period);
step S3: estimating the current reference value i at the time k +2*(k +2), the grid voltage e (k +1) at time k + 1;
step S4: estimating three-phase output current value i of inverter at k +1 momentp(k+1)；
Step S5: substituting the alternative voltage vector into the following formula to predict the current at the k +2 moment;
Figure BDA0002314060900000051
in the formula: i.e. ipFor current prediction, R is the filter inductance and the equivalent resistance of the line, TsIs the control period of the controller.
Step S6: substituting the alternative voltage vector into the following formula to predict the difference value of the capacitor voltages on the upper side and the lower side of the same inverter at the moment of k + 2;
Figure BDA0002314060900000052
in the formula: Δ V1 pThe predicted value of the voltage difference of the upper side and lower side supporting capacitors of the upper side inverter is C, the capacitance value of the direct current side supporting capacitor is C, H represents a variable related to the switching state, the value of H is 0 or 1, a corresponding H value table can be preset according to different switching states, and the H value table can be taken when calculation is to be carried out.
Step S7: substituting the predicted values obtained in step S4 and step S5 into a cost function expressed by the following formula, wherein the smaller the value of the cost function is, the closer the voltage vector is to the demand vector at the next moment;
Figure BDA0002314060900000061
in the formula:
Figure BDA0002314060900000062
respectively α components of the reference current,
Figure BDA0002314060900000063
α components, λ, of the predicted current, respectivelydcThe weight coefficient is the midpoint balance of the direct current side.
Step S8: comparing the values of the cost function obtained in the step S6, taking the smaller value, and recording as gopt；
Step S9: judging whether the prediction and optimization of all 19 alternative voltage vectors are finished, and if so, entering the step S10; if not, returning to the step S4 to predict the next alternative vector;
step S10: storage and goptCorresponding optimal switching state SoptAnd waits for the next sampling instant.
In this embodiment, the 19 candidate voltage vectors include 7 actual voltage vectors and 12 virtual voltage vectors, and the spatial distribution thereof is as shown in fig. 2, and it can be known by substituting the 19 candidate voltage vectors into the following formula, and the contribution to the zero-order circulating current is zero.
Figure BDA0002314060900000064
In the formula, R1，R2Equivalent resistances, L, of filter inductances of the upper and lower inverters, respectively1，L2Filter inductance values, Δ V, of the upper and lower inverters, respectively1，ΔV2The voltage difference i of the upper and lower capacitors on the DC side of the upper and lower inverterszIs a zero-sequence circulating current of uj1O1，uj2O2The output voltages of the upper and lower inverters are provided.
In this embodiment, the 12 virtual voltage vectors are synthesized by combining 7 actual voltage vectors in pairs, and the action time of each actual voltage vector is half of the control period.
In this embodiment, the optimal switching state SoptFor the minimum term of the cost function value g in the process of optimizing the cost function for 19 times in the control period, g being minimum means that the corresponding current vector obtained by applying the voltage vector in the next period will be closest to the reference value i*Repeatedly, the actual output vector in each period is the item which is closest to the reference vector in the alternative vectors, so that the reference current can be tracked in real time. Meanwhile, the newly added 12 virtual voltage vectors expand the alternative vector library, so that the possibility that the alternative vectors are close to the actual demand vector is increased (as can be seen from fig. 2), and the distortion rate of the output current can be obviously reduced.
The above description is only a preferred embodiment of the present invention, and all equivalent changes and modifications made in accordance with the claims of the present invention should be covered by the present invention.

Claims (7)

1. The method for restraining the circulating current of the inverter based on the model prediction virtual voltage vector control is characterized by comprising the following steps of:
step S1: collection ia1(k)，ib1(k)，ic1(k)，VC1P(k)，VC1N(k) E (k), the value at time k;
wherein ia1，ib1，ic1Three-phase filter inductor current, V, of an upper three-level NPC inverter, respectivelyC1P，VC1NThe upper/lower side supporting capacitor voltages of the upper three-level NPC inverter are respectively, and e is the grid voltage of the grid-connected side;
step S2, the optimal switching vector v found in the last switching period is adoptedopt；
Step S3, calculating the current reference value i at the moment k +2*(k +2), the grid voltage e (k +1) at time k + 1;
step S4, calculating the three-phase output current value i of the inverter at the moment of k +1p(k+1)；
Step S5, predicting the current at the k +2 moment according to the alternative voltage vector;
step S6: according to the alternative voltage vector, predicting the difference value of the capacitor voltages on the upper side and the lower side of the same inverter at the k +2 moment;
step S7, calculating cost function values according to the cost function according to the predicted values obtained in the step S4 and the step S5;
step S8, comparing the values of the cost function obtained in the step S6, taking the smaller value, and recording the smaller value as gopt；
Step S9, judging whether the prediction and optimization of all 19 alternative voltage vectors are finished, if so, entering the step S10; if not, returning to the step S4 to predict the next alternative vector;
step S10, get and goptCorresponding optimal switching state SoptAnd an optimal voltage vector.
2. The model prediction virtual voltage vector control-based three-level NPC inverter zero-sequence circulating current suppression method as claimed in claim 1, wherein: the 19 candidate voltage vectors include 7 actual voltage vectors and 12 virtual voltage vectors, and the 19 candidate voltage vectors all contribute zero to the zero-sequence circulating current.
3. The model-based virtual voltage vector control three-level NPC inverter zero-sequence circulating current suppression method as claimed in claim 2, wherein: the 12 virtual voltage vectors are synthesized pairwise by 7 actual voltage vectors, and the action time of each actual voltage vector is half of a control period.
4. The model-based virtual voltage vector control three-level NPC inverter zero-sequence circulating current suppression method according to claim 1, wherein the step S5 specifically comprises: substituting the candidate voltage vector into the equation to predict the current at time k +2
Figure FDA0002314060890000021
In the formula: i.e. ipFor current prediction, R is the filter inductance and the equivalent resistance of the line, TsIs the control period of the controller.
5. The model-based virtual voltage vector control three-level NPC inverter zero-sequence circulating current suppression method according to claim 1, wherein the step S6 specifically comprises: and substituting the candidate voltage vector into the following formula to predict the difference value of the upper side capacitor voltage and the lower side capacitor voltage of the same inverter at the moment k + 2:
Figure FDA0002314060890000022
in the formula: Δ V1 pThe predicted value of the voltage difference of the upper/lower support capacitors of the upper inverter is C, the capacitance value of the DC support capacitor is C, H represents a variable related to the switch state, and the value of H is 0 or 1.
6. The model-based virtual voltage vector control three-level NPC inverter zero-sequence circulating current suppression method according to claim 1, wherein the step S7 specifically comprises: substituting the predicted values obtained in the steps S4 and S5 into a cost function shown as the following formula;
Figure FDA0002314060890000031
in the formula:
Figure FDA0002314060890000032
respectively α components of the reference current,
Figure FDA0002314060890000033
α components, λ, of the predicted current, respectivelydcThe weight coefficient is the midpoint balance of the direct current side.
7. The method for suppressing the zero-sequence circulating current of the model-based predictive virtual voltage vector controlled three-level NPC inverter as claimed in claim 1, wherein the first period of step S2 is to apply the first candidate vector in the candidate vector library.
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