CN110890868A - Resistance circuit and variable gain amplifying circuit - Google Patents
Resistance circuit and variable gain amplifying circuit Download PDFInfo
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- CN110890868A CN110890868A CN201811042171.5A CN201811042171A CN110890868A CN 110890868 A CN110890868 A CN 110890868A CN 201811042171 A CN201811042171 A CN 201811042171A CN 110890868 A CN110890868 A CN 110890868A
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- 239000003990 capacitor Substances 0.000 claims description 44
- 238000007599 discharging Methods 0.000 claims description 30
- 239000004065 semiconductor Substances 0.000 claims description 9
- 229910044991 metal oxide Inorganic materials 0.000 claims description 6
- 150000004706 metal oxides Chemical class 0.000 claims description 6
- 230000005669 field effect Effects 0.000 claims description 5
- 230000000295 complement effect Effects 0.000 claims description 4
- 230000003321 amplification Effects 0.000 claims description 3
- 238000003199 nucleic acid amplification method Methods 0.000 claims description 3
- 238000000034 method Methods 0.000 description 9
- 238000010586 diagram Methods 0.000 description 4
- 230000009471 action Effects 0.000 description 3
- 230000008569 process Effects 0.000 description 3
- 230000005540 biological transmission Effects 0.000 description 2
- 230000003247 decreasing effect Effects 0.000 description 2
- 239000000463 material Substances 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 230000004044 response Effects 0.000 description 2
- 229910021420 polycrystalline silicon Inorganic materials 0.000 description 1
- 229920005591 polysilicon Polymers 0.000 description 1
- 230000000630 rising effect Effects 0.000 description 1
- 239000010409 thin film Substances 0.000 description 1
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/04—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements with semiconductor devices only
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03G—CONTROL OF AMPLIFICATION
- H03G3/00—Gain control in amplifiers or frequency changers
- H03G3/20—Automatic control
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Abstract
The application discloses resistance circuit, its characterized in that includes: the series branch circuit consists of a first resistor and a first switch; a second resistor connected in parallel with the series branch; and the control module is used for providing a control signal for the first switch, wherein the duty ratio of the control signal is continuously changed, and the first switch is switched on or switched off according to the control signal so as to provide continuously changed equivalent resistance at two ends of the second resistor. A highly linear and continuously smoothly varying variable resistance value can be provided. The application also discloses a variable gain amplifying circuit.
Description
Technical Field
The invention relates to the field of integrated circuit design, in particular to a resistance circuit and a variable gain amplifying circuit.
Background
A conventional resistor Circuit (Resistive Circuit) may be implemented by connecting a plurality of resistors with fixed resistance values in parallel or a Metal-Oxide-Semiconductor Field-Effect Transistor (MOSFET) and a PIN Diode (PIN Diode) operating in a linear region. In order to obtain a variable resistance value, the prior art generally adopts a plurality of switch components connected between parallel resistors, and adjusts an equivalent resistance value of a resistance circuit by controlling on/off states of the plurality of switch components. The variable resistance value may also be provided by adjusting the bias to the MOSFET or adjusting the forward bias of the PIN diode to control the resistance of the sandwich portion.
However, the conventional resistance circuit has the following problems: the equivalent variable resistance obtained by the method of adjusting the bias of the MOSFET or PIN diode has nonlinear error; the variable resistance value formed using a plurality of parallel resistors is not continuously variable.
Disclosure of Invention
In view of the above, it is an object of the present invention to provide a resistance circuit and a variable gain amplifier circuit that can provide a variable resistance value that changes continuously and smoothly with high linearity.
According to an aspect of the present invention, there is provided a resistor circuit, comprising: the series branch circuit consists of a first resistor and a first switch; a second resistor connected in parallel with the series branch; and the control module is used for providing a control signal for the first switch, wherein the duty ratio of the control signal is continuously changed, and the first switch is switched on or switched off according to the control signal so as to provide continuously changed equivalent resistance at two ends of the second resistor.
Preferably, the control module comprises: a charging unit and a discharging unit connected in series between a power supply voltage and ground; a capacitor, a first end of which is connected to a middle node between the charging unit and the discharging unit, and a second end of which is grounded, wherein the charging unit is used for charging the capacitor in a first period, and the discharging unit is used for discharging the capacitor in a second period; and the comparator comprises a first input end, a second input end, a third input end and an output end, wherein the first input end of the comparator is connected with the first end of the capacitor to receive the voltage of the capacitor, the second input end is used for receiving the first threshold voltage, the third input end is used for receiving the second threshold voltage, and the output end is used for providing the control signal.
Preferably, the comparator is arranged to: when the capacitor voltage is the first threshold voltage, the comparator outputs a control signal of a first level; when the capacitor voltage is the second threshold voltage, the comparator outputs a control signal of a second level, wherein when the control signal is the first level, the first switch is turned off; when the control signal is at the second level, the first switch is turned on.
Preferably, the first threshold voltage is a continuously varying analog signal.
Preferably, the charging unit includes a first current source and a second switch, the discharging switch includes a second current source, wherein the first current source, the second switch, and the second current source are connected in series between the power supply voltage and ground, an intermediate node of the second switch and the second current source is connected to the first terminal of the capacitor, the second switch is turned on and off according to the control signal, the second switch is turned on during the first period, and the second switch is turned off during the second period.
Preferably, the charging unit includes a first transistor, and the discharging unit includes a third resistor and a second transistor, wherein the first transistor, the third resistor and the second transistor are connected in series between the power supply voltage and ground, an intermediate node of the first transistor and the third resistor is connected to the first terminal of the capacitor, and a control terminal of the first transistor and a control terminal of the second transistor are connected to each other to receive the control signal.
Preferably, the first transistor is an NMOS transistor, and the second transistor is a PMOS transistor.
Preferably, the comparator is a window comparator.
Preferably, the first period and the second period do not overlap each other.
Preferably, the first switch is selected from one of an electromechanical switch, a metal oxide semiconductor field effect transistor, a complementary metal oxide semiconductor or a bipolar transistor.
According to another aspect of the present invention, there is provided a variable gain amplifier circuit for amplifying an input voltage signal to generate an output voltage signal, comprising: an amplifier comprising a first input terminal, a second input terminal and an output terminal; and the resistor circuit, wherein the first input terminal of the amplifier is configured to receive the input voltage signal, the output terminal is configured to provide the output voltage signal, and the resistor circuit is coupled between the output terminal and the second input terminal of the amplifier and configured to provide a continuously variable equivalent resistance.
The resistance circuit comprises a control module and a resistance network comprising a switching tube, wherein the control module obtains a control signal with continuously changing duty ratio by providing a first threshold voltage of an analog signal with continuously changing duty ratio. And then the switching tube is controlled to be switched on or switched off according to the control signal with the continuously-changed duty ratio so as to provide continuously-changed equivalent resistance at an output node of the resistance network. The resistance circuit of the invention can obtain the equivalent resistance which is continuously changed only by adopting the resistance and the switch control, thereby reducing the circuit cost.
When the resistor network is used in a circuit with low switching frequency, the equivalent variable resistor with continuity and high linearity can be obtained. And the frequency response of a circuit which adopts the resistance circuit of the invention as a feedback element or an attenuation element to carry out transmission gain control can be improved.
Drawings
The above and other objects, features and advantages of the present invention will become more apparent from the following description of the embodiments of the present invention with reference to the accompanying drawings.
Fig. 1 shows a schematic configuration diagram of a resistor circuit according to a first embodiment of the present invention.
Fig. 2 shows a circuit schematic of a resistor circuit according to a first embodiment of the invention.
Fig. 3 shows an operation timing chart of the resistance circuit according to the first embodiment of the present invention.
Fig. 4 shows a circuit schematic of a resistor circuit according to a second embodiment of the invention.
Fig. 5 shows a schematic configuration diagram of a variable gain amplification circuit according to a third embodiment of the present invention.
Detailed Description
The invention will be described in more detail below with reference to the accompanying drawings. Like elements in the various figures are denoted by like reference numerals. For purposes of clarity, the various features in the drawings are not necessarily drawn to scale. Moreover, certain well-known elements may not be shown in the figures.
In the following description, numerous specific details of the invention, such as structure, materials, dimensions, processing techniques and techniques of components, are set forth in order to provide a more thorough understanding of the invention. However, as will be understood by those skilled in the art, the present invention may be practiced without these specific details.
It should be understood that in the following description, a "circuit" refers to a conductive loop formed by at least one element or sub-circuit through an electrical or electromagnetic connection. When an element or circuit is referred to as being "connected to" another element or element/circuit is referred to as being "connected between" two nodes, it may be directly coupled or connected to the other element or intervening elements may be present, and the connection between the elements may be physical, logical, or a combination thereof. In contrast, when an element is referred to as being "directly coupled" or "directly connected" to another element, it is intended that there are no intervening elements present.
Fig. 1 shows a schematic configuration diagram of a resistor circuit according to a first embodiment of the present invention.
As shown in fig. 1, the resistor circuit 100 includes a resistor R1, a resistor R2, a switch 110, and a control module 120. The control module 120 is configured to provide a control signal Ctrl to the switch 110, and the control signal Ctrl is configured to control the switch 110 to turn on and off to provide a variable resistance value between the node a and the node B.
In this embodiment, the control signal Ctrl is a square wave signal with a duty ratio D, and the equivalent resistance value between the node a and the node B can be calculated by using the average current:
Re＝R2*R1/(R1+D*R2)
where Re is the equivalent resistance between node a and node B, R1 and R2 are the resistances of resistor R1 and resistor R2, respectively, and D is the duty cycle of control signal Ctrl.
As can be seen from the above equation, in the present embodiment, a continuously varying equivalent resistance can be obtained between the node a and the node B by providing the control signal Ctrl with a continuously varying duty ratio.
In the embodiment, the switch 110 is selected from one or more structures of an electromechanical switch, a Metal-Oxide-Semiconductor Field-Effect Transistor (MOSFET), a Complementary Metal Oxide Semiconductor (CMOS), a Bipolar Junction Transistor (BJT), or the like.
In the following embodiments, the switch 110 is an N-type metal-Oxide-Semiconductor Field-Effect Transistor (NMOSFET) as an example.
Fig. 2 shows a circuit schematic of a resistor circuit according to a first embodiment of the invention. As shown in fig. 2, the resistor circuit 100 includes a switch tube 110, a resistor R1, a resistor R2, and a control module 120. The control end of the switching tube 110 is configured to receive a control signal Ctrl, the first path end is connected to the first end of the resistor R1, the first end of the resistor R2 is connected to the second path end of the switching tube 110, and the second end is connected to the second end of the resistor R1. The switch tube 110 is used for switching on or off according to the control signal Ctrl with continuously varying duty ratio to provide a continuously varying equivalent resistance between the node a and the node B at both ends of the resistor R2.
The control module 120 includes a charging unit 121 and a discharging unit 122 connected in series between a power supply voltage and ground. The capacitor C1 has a first terminal connected to the intermediate node between the charging unit 121 and the discharging unit 122, and a second terminal connected to ground.
The control module 120 further includes a comparator 124, the comparator 124 is, for example, a window comparator, a first input terminal of the comparator 124 is connected to the first terminal of the capacitor C1, a second input terminal is configured to receive the first threshold voltage Vc, a third input terminal is configured to receive the second threshold voltage Vref, and an output terminal is configured to provide a control signal Ctrl, and the control signal Ctrl is configured to control the on and off of the switch tube 110 and the switch 123.
The charging unit 121 and the discharging unit 122 are used to charge and discharge the capacitor C1. A Switch (Switch)123 is connected between the charging unit 121 and the node 130. When the switch 123 is closed, the charging unit 121 charges the capacitor C1; conversely, when the switch 123 is opened, the discharge unit 122 discharges the capacitor C1. The charging period and the discharging period of the capacitor C1 do not overlap each other. However, in other embodiments, the charging unit 121 and the discharging unit 122 may be simultaneously turned on and off as long as the rising and falling of the voltage of the node 130 may be continuously controlled.
The comparator 124 is configured to compare the voltage of the first end of the capacitor C1 with the first threshold voltage Vc and the second threshold voltage Vref, and provide the control signal Ctrl at the output end according to the comparison result.
In addition, the charging unit 121 and the discharging unit 122 may be a Current Source (Current Source) or other forms of power sources to realize the charging and discharging operations.
Specifically, the charging unit 121 includes a current source I1 and a Switch (Switch)123, and the discharging unit 122 includes a current source I2. The current source I1, the switch 123 and the current source I2 are connected in series between the supply voltage and ground, and the intermediate node of the switch 123 and the current source I2 is connected to the first terminal of the capacitor C1.
Fig. 3 shows an operation timing chart of the resistance circuit according to the first embodiment of the present invention. The operation principle of the resistor circuit according to the first embodiment of the present invention will be described in detail with reference to fig. 2 and 3.
As shown in fig. 2, when the switch 123 is closed, the charging unit 121 charges the capacitor C1, the voltage of the capacitor C1 rises, and the voltage V1 of the capacitor C1 is (I1-I2) × t1/C, where I1 and I2 respectively represent current values provided by the charging unit 121 and the discharging unit 122, t1 represents charging time, and C represents a capacitance value of the capacitor C1. When the voltage of the capacitor C1 rises to the first threshold voltage Vc, the comparator 124 flips and the output control signal Ctrl is at a low level, as shown in fig. 3.
When the control signal Ctrl goes low, the switch 123 is turned off, the discharging unit 122 discharges the capacitor C1, the voltage of the capacitor C1 drops, and the voltage V2 of the capacitor C1 is equal to V1-I2 t2/C, where V1 represents the maximum voltage value of the capacitor C1 in the charging stage, I2 represents the current value provided by the discharging unit 122, t2 represents the discharging time, and C represents the capacitance value of the capacitor C1. When the voltage of the capacitor C1 drops to the second threshold voltage Vref, the comparator 124 flips, the output control signal Ctrl is at a high level, and the charging and discharging of one cycle is completed, as shown in fig. 3.
In addition, the control signal having the continuously varying duty ratio may be obtained by supplying the first threshold voltage Vc of the analog signal having the continuously varying duty ratio. As shown in fig. 3, by providing gradually increasing first threshold voltages Vc1, Vc2, and Vc3, a control signal Ctrl with gradually increasing duty cycle is obtained. Of course, in other embodiments, the control signal Ctrl with gradually decreasing duty cycle is obtained by providing gradually decreasing first threshold voltages Vc1, Vc2, and Vc 3.
In this embodiment, the control signal having the continuously varying duty ratio may be obtained by supplying the first threshold voltage Vc of the continuously varying analog signal. The switching tube 110 is then controlled to be turned on or off according to the control signal with the duty ratio continuously varying, so as to provide a continuously varying equivalent resistance between the node a and the node B at both ends of the resistor R2.
Fig. 4 shows a circuit schematic of a resistor circuit according to a second embodiment of the invention. As shown in fig. 4, the resistor circuit 200 includes a switch tube 210, a resistor R1, a resistor R2, and a control module 220. The control module 220 includes a charging unit 221, a discharging unit 222, a resistor R3, a comparator 224, and a capacitor C1. The circuit structure and principle of the resistor circuit 200 are similar to those of the resistor circuit 100 according to the first embodiment of the present invention, except that the charging unit 221 and the discharging unit 222 in the resistor circuit 200 are implemented in the form of transistors.
The charging unit 221 and the discharging unit 222 are used to charge and discharge the capacitor C1, respectively. The charging unit 221 includes a transistor M1, the transistor M1 is an nmos fet, and the discharging unit 222 includes a transistor M2 and a resistor R3, the transistor M2 is a pmos fet. The transistor M1, the resistor R3 and the transistor M2 are connected in series between the power voltage and ground, the intermediate node of the transistor M1 and the resistor R3 is connected to the first terminal of the capacitor C1, and the control terminals of the transistor M1 and the transistor M2 are both connected to the output terminal of the comparator 224 to receive the control signal Ctrl. The transistor M1 and the transistor M2 constitute a Complementary Metal Oxide Semiconductor (CMOS) Inverter (Inverter). When the control signal Ctrl is at a high level (logic 1), the transistor M1 is turned on, the transistor M2 is turned off, the charging unit 221 charges the capacitor C1, and when the voltage of the capacitor C1 rises to the first threshold voltage Vc, the comparator 124 inverts and the output control signal Ctrl is at a low level; when the control signal Ctrl changes to a low level (logic 0), the transistor M2 is turned on, the transistor M1 is turned off, the discharging unit 222 discharges the capacitor C1, and when the voltage of the capacitor C1 drops to the second threshold voltage Vref, the comparator 124 inverts, and the output control signal Ctrl is at a high level, thereby completing charging and discharging of one cycle.
Fig. 5 shows a schematic configuration diagram of a variable gain amplification circuit according to a third embodiment of the present invention. As shown in fig. 5, the variable gain amplifier 300 is used for amplifying an input voltage signal Vin to generate an output voltage signal Vout. The variable gain amplifier 300 includes an amplifier 310 and a resistance circuit 320. The amplifier 310 has a first input terminal for receiving an input voltage signal Vin and an output terminal for providing the output voltage signal Vout. The resistor circuit 320 is coupled between the output terminal and the second input terminal of the amplifier 310 for providing a continuously variable resistance. The resistor circuit 320 is any one of the resistor circuits disclosed in the first and second embodiments.
The "resistance" mentioned in the above embodiments may be a single physical resistor or a resistance element, or may be a combination of a plurality of physical resistors or resistance elements. In other words, the resistance type digital-to-analog converter shown in the present invention is applicable to various types of impedance elements, each impedance element having an impedance corresponding to a required resistance. Thus, reference herein to "resistance" is further to any number of different types of resistive elements according to circuit layout, such as precision thin film resistors formed of SiCr or other material, or in the case of integrated circuits, polysilicon (doped p-or n-). It will also be appreciated that a "resistor" as described herein may include any circuit element that can generate a voltage across its terminals that is proportional to the current passing through it.
In summary, the resistor circuit of the present invention includes a control module and a resistor network including a switching tube, wherein the control module obtains a control signal with a continuously varying duty ratio by providing a first threshold voltage of an analog signal with a continuously varying duty ratio. And then the switching tube is controlled to be switched on or switched off according to the control signal with the continuously-changed duty ratio so as to provide continuously-changed equivalent resistance at an output node of the resistance network. The resistance circuit of the invention can obtain the equivalent resistance which is continuously changed only by adopting the resistance and the switch control, thereby reducing the circuit cost.
When the resistor network is used in a circuit with low switching frequency, the equivalent variable resistor with continuity and high linearity can be obtained. And the frequency response of a circuit which adopts the resistance circuit of the invention as a feedback element or an attenuation element to carry out transmission gain control can be improved.
It is noted that, herein, relational terms such as first and second, and the like may be used solely to distinguish one entity or action from another entity or action without necessarily requiring or implying any actual such relationship or order between such entities or actions. Also, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.
While embodiments in accordance with the invention have been described above, these embodiments are not intended to be exhaustive or to limit the invention to the precise embodiments described. Obviously, many modifications and variations are possible in light of the above teaching. The embodiments were chosen and described in order to best explain the principles of the invention and the practical application, to thereby enable others skilled in the art to best utilize the invention and various embodiments with various modifications as are suited to the particular use contemplated. The invention is limited only by the claims and their full scope and equivalents.
Claims (10)
1. A resistor circuit, comprising:
the series branch circuit consists of a first resistor and a first switch;
a second resistor connected in parallel with the series branch; and
a control module for providing a control signal to the first switch,
the duty ratio of the control signal is continuously changed, and the first switch is switched on or switched off according to the control signal so as to provide continuously changed equivalent resistance at two ends of the second resistor.
2. The resistor circuit of claim 1, wherein the control module comprises:
a charging unit and a discharging unit connected in series between a power supply voltage and ground;
a capacitor having a first terminal connected to a middle node of the charging unit and the discharging unit and a second terminal connected to ground,
the charging unit is used for charging the capacitor in a first period,
the discharge unit is used for discharging the capacitor in a second period; and
a comparator including a first input terminal, a second input terminal, a third input terminal, and an output terminal,
the first input end of the comparator is connected with the first end of the capacitor to receive the capacitor voltage, the second input end of the comparator is used for receiving the first threshold voltage, the third input end of the comparator is used for receiving the second threshold voltage, and the output end of the comparator is used for providing the control signal.
3. The resistor circuit of claim 2, wherein the comparator is configured to:
when the capacitor voltage is the first threshold voltage, the comparator outputs a control signal of a first level;
when the capacitor voltage is the second threshold voltage, the comparator outputs a control signal of a second level,
when the control signal is at the first level, the first switch is turned off; when the control signal is at the second level, the first switch is turned on.
4. The resistor circuit of claim 3, wherein the first threshold voltage is a continuously varying analog signal.
5. The resistance circuit of claim 2, wherein the charging unit comprises a first current source and a second switch, wherein the discharging switch comprises a second current source,
wherein the first current source, second switch and second current source are connected in series between the supply voltage and ground,
an intermediate node of the second switch and the second current source is connected to a first terminal of the capacitor,
the second switch is turned on and off according to the control signal, the second switch is turned on during the first period, and the second switch is turned off during the second period.
6. The resistor circuit according to claim 2, wherein the charging unit comprises a first transistor, the discharging unit comprises a third resistor and a second transistor,
wherein the first transistor, the third resistor, and the second transistor are connected in series between the power supply voltage and ground,
an intermediate node of the first transistor and the third resistor is connected to a first terminal of the capacitor,
a control terminal of the first transistor and a control terminal of the second transistor are connected to each other to receive the control signal.
7. The resistor circuit according to claim 6, wherein the first transistor is an NMOS transistor and the second transistor is a PMOS transistor.
8. The resistor circuit of claim 2, wherein the comparator is a window comparator.
9. The resistor circuit of claim 1, wherein the first switch is selected from one of an electromechanical switch, a metal oxide semiconductor field effect transistor, a complementary metal oxide semiconductor, or a bipolar transistor.
10. A variable gain amplification circuit for amplifying an input voltage signal to produce an output voltage signal, comprising:
an amplifier comprising a first input terminal, a second input terminal and an output terminal; and
the resistance circuit of any one of claims 1-9,
the amplifier has a first input terminal for receiving the input voltage signal, an output terminal for providing the output voltage signal, and a resistance circuit coupled between the output terminal and the second input terminal for providing a continuously variable equivalent resistance.
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| Application Number | Priority Date | Filing Date | Title |
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| CN201811042171.5A CN110890868B (en) | 2018-09-07 | 2018-09-07 | Resistor circuit and variable gain amplifier circuit |
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| Application Number | Priority Date | Filing Date | Title |
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| CN201811042171.5A CN110890868B (en) | 2018-09-07 | 2018-09-07 | Resistor circuit and variable gain amplifier circuit |
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| CN110890868A true CN110890868A (en) | 2020-03-17 |
| CN110890868B CN110890868B (en) | 2023-09-12 |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN113484697A (en) * | 2021-05-19 | 2021-10-08 | 北京宏优科技发展有限公司 | Insulator leakage analysis system and method |
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| US5534819A (en) * | 1995-04-13 | 1996-07-09 | Motorola, Inc. | Circuit and method for reducing voltage error when charging and discharging a variable capacitor through a switch |
| CN101166021A (en) * | 2006-10-17 | 2008-04-23 | 联发科技股份有限公司 | Controllable resistive circuit for providing a continuous variable resistance and filter circuit |
| CN201805351U (en) * | 2010-08-12 | 2011-04-20 | 美凌微电子(上海)有限公司 | Control circuit for altering frequency of switching power supply |
| CN105141114A (en) * | 2015-09-07 | 2015-12-09 | 成都芯源系统有限公司 | Switch converter with constant on-time control and control circuit thereof |
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2018
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Patent Citations (4)
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|---|---|---|---|---|
| US5534819A (en) * | 1995-04-13 | 1996-07-09 | Motorola, Inc. | Circuit and method for reducing voltage error when charging and discharging a variable capacitor through a switch |
| CN101166021A (en) * | 2006-10-17 | 2008-04-23 | 联发科技股份有限公司 | Controllable resistive circuit for providing a continuous variable resistance and filter circuit |
| CN201805351U (en) * | 2010-08-12 | 2011-04-20 | 美凌微电子(上海)有限公司 | Control circuit for altering frequency of switching power supply |
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| CN113484697A (en) * | 2021-05-19 | 2021-10-08 | 北京宏优科技发展有限公司 | Insulator leakage analysis system and method |
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