CN110572042B - A double-sided asymmetric voltage control method for a two-way wireless power transmission system - Google Patents

A double-sided asymmetric voltage control method for a two-way wireless power transmission system Download PDF

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CN110572042B
CN110572042B CN201910941898.5A CN201910941898A CN110572042B CN 110572042 B CN110572042 B CN 110572042B CN 201910941898 A CN201910941898 A CN 201910941898A CN 110572042 B CN110572042 B CN 110572042B
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CN110572042A (en
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陈昌松
贾舒然
朝泽云
刘朋
段善旭
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Huazhong University of Science and Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter

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Abstract

本发明公开了一种双向无线电能传输系统的双侧不对称电压控制方法，包括：获取第一全桥变换器的交流侧端口电流的相位、第一全桥变换器的直流侧电压和直流侧电流；根据稳压或恒流要求确定第一全桥变换器的激励电压总脉冲宽度角；确定第一全桥变换器的开关管的导通和关断的时刻，并据此对开关管进行驱动；将所需参数发送至原边控制器；确定为实现零电压开通，第二全桥变换器的激励电压总脉冲宽度角的取值范围，并在该取值范围内选取最优的原边激励电压总脉冲宽度角的取值；确定第二全桥变换器开关管的导通和关断的时刻。本发明可以实现原边全桥变换器和副边全桥变换器的开关管的零电压开通，并且实现电能传输效率的优化。

Figure 201910941898

The invention discloses a double-side asymmetric voltage control method for a two-way wireless power transmission system. current; determine the total pulse width angle of the excitation voltage of the first full-bridge converter according to the requirements of voltage regulation or constant current; determine the turn-on and turn-off times of the switch tube of the first full-bridge converter, and conduct the switch tube accordingly. drive; send the required parameters to the primary side controller; determine the value range of the total pulse width angle of the excitation voltage of the second full-bridge converter in order to achieve zero-voltage turn-on, and select the optimal original value within the value range The value of the total pulse width angle of the side excitation voltage; determine the turn-on and turn-off moments of the switch tube of the second full-bridge converter. The invention can realize the zero-voltage turn-on of the switching tubes of the primary-side full-bridge converter and the secondary-side full-bridge converter, and realize the optimization of the power transmission efficiency.

Figure 201910941898

Description

一种双向无线电能传输系统的双侧不对称电压控制方法A double-sided asymmetric voltage control method for a two-way wireless power transmission system

技术领域technical field

本发明属于DC/DC变换器领域，更具体地，涉及一种双向无线电能传输系统的双侧不对称电压控制方法。The invention belongs to the field of DC/DC converters, and more particularly, relates to a double-sided asymmetrical voltage control method of a two-way wireless power transmission system.

背景技术Background technique

随着能源互联网概念的提出以及智能配电网相关技术的发展，电动汽车双向无线电能传输系统逐渐开始展现出其独特的优势。对于电网而言，双向无线电能传输系统允许了电网电能与车载电池电能之间双向流动，因此若经过智能调控，可实现电动汽车有序充电、电网削峰填谷等优化运行功能。而对于用户而言，无线电能传输的方式省去了连接或断开充电线缆的步骤，不存在接口磨损、接触不良或漏电等问题，其操作极为便捷，因此用户更乐于参与将电动汽车挂载于电网上。由此，双向无线电能传输的技术发展，对提升未来能源互联网的稳定性和智能性起到重要作用。With the proposal of the concept of energy Internet and the development of related technologies of intelligent distribution network, the two-way wireless energy transmission system of electric vehicles has gradually begun to show its unique advantages. For the power grid, the two-way wireless power transmission system allows two-way flow between power grid power and on-board battery power. Therefore, if it is intelligently controlled, it can realize optimal operation functions such as orderly charging of electric vehicles and grid peak shaving and valley filling. For users, the wireless power transmission method saves the steps of connecting or disconnecting the charging cable, and there are no problems such as interface wear, poor contact or leakage, and the operation is extremely convenient, so users are more willing to participate in connecting the electric vehicle loaded on the grid. As a result, the technological development of two-way wireless energy transmission plays an important role in improving the stability and intelligence of the future energy Internet.

在双向无线电能传输系统中，实现传输功率的调节，并且在宽传输功率(负载)范围内实现较高的效率是很有必要的。在双向无线电能传输系统中，原边变换器与副边变换器是相对的概念。目前，在双向无线电能传输系统中，实现功率的调节主要有以下几种方法：1、单级单侧控制方法。在双向无线电能传输电路部分，除了双全桥变换器这一级DC/DC变换器外，不增加其它的变换器。通过改变原边或副边侧全桥变换器的内移相角实现功率的调节。该方法虽然较为简单，容易实现，但是存在的问题是：未实现原副边激励电压的匹配，因此未能实现中间环节的传输效率优化，同时部分开关管处于硬开关状态，导致系统传输效率低下。In a two-way wireless power transmission system, it is necessary to realize the regulation of transmission power and achieve high efficiency in a wide transmission power (load) range. In the two-way wireless power transmission system, the primary side converter and the secondary side converter are relative concepts. At present, in the two-way wireless power transmission system, there are mainly the following methods for realizing power regulation: 1. Single-stage and single-side control method. In the part of the two-way wireless power transmission circuit, no other converters are added except the DC/DC converter of the double full-bridge converter. The power regulation is realized by changing the internal phase shift angle of the primary side or secondary side full-bridge converter. Although this method is relatively simple and easy to implement, the problem is that the excitation voltage of the primary and secondary sides is not matched, so the transmission efficiency optimization of the intermediate link cannot be achieved, and some switches are in a hard switching state, resulting in low transmission efficiency of the system. .

2、多级单侧控制方法：在双向无线电能传输电路部分，除了双全桥变换器这一级DC/DC变换器外，在某一侧另加入一级DC/DC变换器，通过DC/DC变换器改变该侧的全桥变换器的直流侧电压，从而调节该侧的激励电压，实现传输功率的调节。该方法可以使双向无线电能传输电路部分的所有开关管均实现软开关，但是存在的问题是：未实现原副边激励电压的匹配，因此未能实现中间环节的传输效率优化，导致系统传输效率低下。新增的一级DC/DC变换器使得整个系统的控制较为复杂，且也会增加一定的损耗。2. Multi-stage single-side control method: In the part of the two-way wireless power transmission circuit, in addition to the double full-bridge converter this level of DC/DC converter, another level of DC/DC converter is added on one side, through the DC/DC The converter changes the DC side voltage of the full-bridge converter on the side, so as to adjust the excitation voltage on the side and realize the adjustment of the transmission power. This method can make all switches in the two-way wireless power transmission circuit part realize soft switching, but the problem is that the excitation voltages of the primary and secondary sides are not matched, so the transmission efficiency optimization of the intermediate links cannot be achieved, resulting in the transmission efficiency of the system. low. The newly added one-stage DC/DC converter makes the control of the whole system more complicated, and also increases a certain loss.

3、多级双侧控制方法：在双向无线电能传输电路部分，除了双全桥变换器这一级DC/DC变换器外，在原副边两侧各加入一级DC/DC变换器，通过DC/DC变换器改变双侧的全桥变换器的直流侧电压，实现传输功率的调节，同时能实现激励电压的匹配，从而实现中间环节的传输效率优化，达到较高的效率。但是，该方法存在的问题是：加入的额外的DC/DC变换器使得整个系统的控制较为复杂，也会增加一定的损耗。3. Multi-level double-side control method: In the part of the two-way wireless power transmission circuit, in addition to the double full-bridge converter, a level of DC/DC converter, a level of DC/DC converter is added on both sides of the primary and secondary sides. The DC converter changes the DC side voltage of the full-bridge converter on both sides, realizes the adjustment of the transmission power, and at the same time can realize the matching of the excitation voltage, so as to realize the optimization of the transmission efficiency of the intermediate link and achieve a higher efficiency. However, the problem of this method is that the added additional DC/DC converter makes the control of the whole system more complicated, and also increases a certain loss.

4、单级双侧对称激励电压双移相控制方法：在双向无线电能传输电路部分，除了双全桥变换器这一级DC/DC变换器外，不增加其它的变换器。通过改变原边和副边侧全桥变换器的内移相角实现功率的调节，同时使得激励电压比接近最优激励电压比，从而实现中间环节的传输效率优化，提高系统效率。但是，该方法存在的问题是：开关管工作在硬开关状态，损耗较高。4. Single-stage double-sided symmetrical excitation voltage double-phase-shift control method: In the part of the two-way wireless power transmission circuit, no other converters are added except the double full-bridge converter. By changing the internal phase shift angle of the primary side and secondary side full-bridge converters, the power is adjusted, and the excitation voltage ratio is close to the optimal excitation voltage ratio, so as to optimize the transmission efficiency of the intermediate links and improve the system efficiency. However, the problem of this method is that the switch tube works in a hard switching state, and the loss is relatively high.

5、单级双侧对称激励电压三移相控制方法：在单级双侧对称激励电压双移相控制方法的基础上，对原副边激励电压的基波相位差(称之为外移相角)进行控制，从而实现所有开关管的零电压开通(Zero Voltage Switch，ZVS)，进一步减小开关损耗，从而使得效率有进一步的提升。但是，该方法存在的问题是：当传输功率处于中载功率或轻载功率等级时，为实现ZVS，外移相角将接近零度，使得传输效率严重下降。5. Single-stage double-sided symmetrical excitation voltage three-phase-shift control method: On the basis of the single-stage double-sided symmetrical excitation voltage double-phase-shift control method, the fundamental phase difference of the primary and secondary excitation voltages (called external phase-shift Angle) to control, so as to realize the zero voltage turn-on (Zero Voltage Switch, ZVS) of all switches, further reduce the switching loss, and thus further improve the efficiency. However, the problem with this method is: when the transmission power is at the level of medium load power or light load power, in order to achieve ZVS, the external phase shift angle will be close to zero degrees, which will seriously reduce the transmission efficiency.

因此，有必要研究一种新的控制方法，既能实现激励电压比接近最优激励电压比，同时在较高的外移相角下实现ZVS，从而实现较高的效率。Therefore, it is necessary to study a new control method, which can not only achieve the excitation voltage ratio close to the optimal excitation voltage ratio, but also realize ZVS at a higher external phase shift angle, thereby achieving higher efficiency.

发明内容SUMMARY OF THE INVENTION

针对现有技术的缺陷和改进需求，本发明提供了一种双向无线电能传输系统的双侧不对称电压控制方法，旨在解决现有的双向无线电能传输系统的无法在宽传输功率范围内实现较高效率的问题。In view of the defects and improvement requirements of the prior art, the present invention provides a bilateral asymmetric voltage control method for a two-way wireless power transmission system, aiming to solve the problem that the existing two-way wireless power transmission system cannot be realized in a wide transmission power range. higher efficiency issues.

为实现上述目的，本发明提供了一种双向无线电能传输系统的双侧不对称电压控制方法，包括：In order to achieve the above object, the present invention provides a bilateral asymmetric voltage control method for a two-way wireless power transmission system, including:

(1)获取第一全桥变换器的交流侧端口电流i2的相位，以及第一全桥变换器的直流侧电压Vdc2和直流侧电流Idc2；其中，所述第一全桥变换器为副边全桥变换器且所述第二全桥变换器为原边全桥变换器，或者所述第一全桥变换器为原边全桥变换器且所述第二全桥变换器为副边全桥变换器；(1) Obtain the phase of the AC-side port current i 2 of the first full-bridge converter, as well as the DC-side voltage V dc2 and the DC-side current I dc2 of the first full-bridge converter; wherein, the first full-bridge converter is a secondary-side full-bridge converter and the second full-bridge converter is a primary-side full-bridge converter, or the first full-bridge converter is a primary-side full-bridge converter and the second full-bridge converter is Secondary side full bridge converter;

(2)根据对Vdc2或Idc2的控制要求，计算第一全桥变换器的激励电压的总脉冲宽度角的指令值β2t，确定电能传输方向；(2) According to the control requirements for V dc2 or I dc2 , calculate the command value β 2t of the total pulse width angle of the excitation voltage of the first full-bridge converter, and determine the power transmission direction;

(3)结合(1)中获取到的第一全桥变换器的交流侧端口电流i2的相位，以及(2)中得到的第一全桥变换器的激励电压的总脉冲宽度角的指令值β2t，计算出第一全桥变换器的各个开关管的导通和关断时刻，根据各个开关管的导通和关断时刻，产生对第一全桥变换器的开关管的驱动信号；(3) Combining the phase of the AC side port current i 2 of the first full-bridge converter obtained in (1) and the command of the total pulse width angle of the excitation voltage of the first full-bridge converter obtained in (2) value β 2t , calculate the turn-on and turn-off time of each switch tube of the first full-bridge converter, and generate the drive signal to the switch tube of the first full-bridge converter according to the turn-on and turn-off time of each switch tube ;

(4)将第一全桥变换器的直流侧电压值Vdc2、第一全桥变换器的激励电压的总脉冲宽度角β2t和所需的电能传输方向通过通信通道发送至第二全桥变换器所对应的控制器，同时获取第二全桥变换器的直流侧电压Vdc1，根据给定的裕量角α，计算可使第二全桥变换器所有开关管实现ZVS的第二全桥变换器的激励电压的总脉冲宽度角β1t；(4) Send the DC side voltage value V dc2 of the first full-bridge converter, the total pulse width angle β 2t of the excitation voltage of the first full-bridge converter, and the required power transmission direction to the second full-bridge through the communication channel The controller corresponding to the converter obtains the DC side voltage V dc1 of the second full-bridge converter at the same time, and according to the given margin angle α, calculates that all switches of the second full-bridge converter can realize the second full-bridge of ZVS. the total pulse width angle β 1t of the excitation voltage of the bridge converter;

(5)根据第二全桥变换器的激励电压的总脉冲宽度角β1t，计算第二全桥变换器的各个开关管的导通和关断时刻，根据各个开关管的导通和关断时刻，产生对第二全桥变换器的开关管的驱动信号。(5) According to the total pulse width angle β 1t of the excitation voltage of the second full-bridge converter, calculate the turn-on and turn-off time of each switch tube of the second full-bridge converter, and according to the turn-on and turn-off time of each switch tube At a moment, a drive signal to the switch tube of the second full-bridge converter is generated.

进一步地，步骤(2)中，可以使用常规的比例-积分(PI)控制算法，得到第一全桥变换器的激励电压的总脉冲宽度角的指令值β2t。Further, in step (2), a conventional proportional-integral (PI) control algorithm can be used to obtain the command value β 2t of the total pulse width angle of the excitation voltage of the first full-bridge converter.

进一步地，步骤(3)中，可以采用以下步骤确定第一全桥变换器的各个开关管的导通和关断时刻：Further, in step (3), the following steps can be used to determine the turn-on and turn-off moments of each switch tube of the first full-bridge converter:

(31)根据如下方法确定正脉冲宽度角β2+和负脉冲宽度角β2-：(31) Determine the positive pulse width angle β 2+ and the negative pulse width angle β 2- according to the following method:

Figure GDA0002508580750000041
Figure GDA0002508580750000041

Figure GDA0002508580750000042
Figure GDA0002508580750000042

(32)根据β2t值所处的范围确定第一全桥变换器应工作于半桥模式或是全桥模式：若0≤β2t≤180°，则第一全桥变换器应工作于半桥模式；若180°＜β2t≤360°，则第一全桥变换器应工作于全桥模式；(32) Determine whether the first full-bridge converter should work in half-bridge mode or full-bridge mode according to the range of β 2t value: if 0≤β 2t ≤180°, then the first full-bridge converter should work in half-bridge mode Bridge mode; if 180°＜β 2t ≤360°, the first full-bridge converter should work in full-bridge mode;

(33)根据所需的电能传输方向确定第一全桥变换器应工作于整流模式或是逆变模式：若所需的电能传输方向为从第二全桥变换器传输至第一全桥变换器，则第一全桥变换器工作于整流模式；若所需的电能传输方向为从第一全桥变换器传输至第二全桥变换器，则第一全桥变换器工作于逆变模式；(33) Determine whether the first full-bridge converter should work in rectification mode or inverter mode according to the required power transmission direction: if the required power transmission direction is from the second full-bridge converter to the first full-bridge converter If the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, the first full-bridge converter works in the inverter mode ;

(34)根据(32)-(33)中所确定的第一全桥变换器的工作模式，确定各个开关管的导通和关断时刻：(34) According to the working mode of the first full-bridge converter determined in (32)-(33), determine the turn-on and turn-off moments of each switch:

若第一全桥变换器工作于整流全桥模式，则：If the first full-bridge converter works in the rectified full-bridge mode, then:

Figure GDA0002508580750000043
Figure GDA0002508580750000043

若第一全桥变换器工作于整流半桥模式，则：If the first full-bridge converter works in the rectifier half-bridge mode, then:

Figure GDA0002508580750000044
Figure GDA0002508580750000044

同时保持第二桥臂的靠近直流侧正极的开关管始终处于关断状态，而第二桥臂的靠近直流侧负极的开关管始终处于导通状态；At the same time, the switch tube of the second bridge arm close to the positive pole of the DC side is always in an off state, and the switch tube of the second bridge arm close to the negative pole of the DC side is always in an on state;

若第一全桥变换器工作于逆变全桥模式，则：If the first full-bridge converter works in the inverter full-bridge mode, then:

Figure GDA0002508580750000051
Figure GDA0002508580750000051

若第一全桥变换器工作于逆变半桥模式，则：If the first full-bridge converter works in the inverter half-bridge mode, then:

Figure GDA0002508580750000052
Figure GDA0002508580750000052

同时保持第二桥臂的靠近直流侧正极的开关管始终处于关断状态，而第二桥臂的靠近直流侧负极的开关管始终处于导通状态；At the same time, the switch tube of the second bridge arm close to the positive pole of the DC side is always in an off state, and the switch tube of the second bridge arm close to the negative pole of the DC side is always in an on state;

其中，αon5和αoff5分别为第一全桥变换器的第一桥臂的靠近直流侧正极的开关管的开通和关断时刻相对于i2的基波分量由负到正过零时刻之间的相位角，以前者超前后者为正，前者滞后后者为负；αon7和αoff7分别为第一全桥变换器的第二桥臂的靠近直流侧正极的开关管的开通和关断时刻相对于i2的基波分量由负到正过零时刻之间的相位角，以前者超前后者为正，前者滞后后者为负；α为裕量角；max为最大值函数。Among them, α on5 and α off5 are respectively the time between the turn-on and turn-off time of the switch tube of the first bridge arm of the first full-bridge converter close to the positive pole of the DC side relative to the fundamental wave component of i 2 from negative to positive zero-crossing time The phase angle between α and α, the former is ahead and the latter is positive, the former lags the latter and is negative; α on7 and α off7 are the turn-on and turn-off of the switch tube of the second bridge arm of the first full-bridge converter, which is close to the positive electrode of the DC side, respectively. The phase angle from negative to positive zero-crossing moment relative to the fundamental wave component of i 2 , the former is ahead of the latter and the latter is positive, and the former lags behind the latter is negative; α is the margin angle; max is the maximum value function.

进一步地，步骤(4)中，可以采用以下步骤确定第二全桥变换器的激励电压总脉冲宽度角β1t的取值范围：Further, in step (4), the following steps can be used to determine the value range of the total pulse width angle β 1t of the excitation voltage of the second full-bridge converter:

(41)根据如下方法确定正脉冲宽度角β1+和负脉冲宽度角β1-：(41) Determine the positive pulse width angle β 1+ and the negative pulse width angle β 1- according to the following method:

Figure GDA0002508580750000053
Figure GDA0002508580750000053

Figure GDA0002508580750000054
Figure GDA0002508580750000054

(42)根据所需的电能传输方向确定第二全桥变换器应工作于逆变模式或是整流模式：若所需的电能传输方向为从第二全桥变换器传输至第一全桥变换器，则第一全桥变换器工作于逆变模式；若所需的电能传输方向为从第一全桥变换器传输至第二全桥变换器，则第一全桥变换器工作于整流模式；(42) Determine whether the second full-bridge converter should work in the inverter mode or the rectifier mode according to the required power transmission direction: if the required power transmission direction is from the second full-bridge converter to the first full-bridge converter If the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, the first full-bridge converter works in the rectifier mode ;

(43)根据所需的电能传输方向，根据下式计算：第一全桥变换器产生的激励电压的基波分量由负到正过零点时刻与第一全桥变换器产生的激励电压的正脉冲上升沿所对应的时刻之间的相位差θ2,rec或θ2,inv、第二全桥变换器产生的激励电压的基波分量由负到正过零点时刻与第二全桥变换器产生的激励电压的正脉冲上升沿所对应的时刻之间的相位差θ1,rec或θ1,inv。若所需的电能传输方向为从第二全桥变换器至第一全桥变换器，则计算θ2,rec与θ1,inv；若所需的电能传输方向为从第一全桥变换器至第二全桥变换器，则计算θ2,inv与θ1,rec，rec代表整流模式，inv代表逆变模式。(43) According to the required power transmission direction, calculate according to the following formula: the fundamental wave component of the excitation voltage generated by the first full-bridge converter changes from negative to positive zero-crossing time and the positive value of the excitation voltage generated by the first full-bridge converter. The phase difference θ 2,rec or θ 2,inv between the times corresponding to the rising edge of the pulse, the fundamental wave component of the excitation voltage generated by the second full-bridge converter changes from negative to positive zero-crossing time and the second full-bridge converter. The phase difference θ 1,rec or θ 1,inv between the times corresponding to the rising edge of the positive pulse of the generated excitation voltage. If the required power transfer direction is from the second full-bridge converter to the first full-bridge converter, calculate θ 2,rec and θ 1,inv ; if the required power transfer direction is from the first full-bridge converter To the second full-bridge converter, θ 2,inv and θ 1,rec are calculated, where rec represents the rectification mode, and inv represents the inverter mode.

Figure GDA0002508580750000061
Figure GDA0002508580750000061

Figure GDA0002508580750000062
Figure GDA0002508580750000062

Figure GDA0002508580750000063
Figure GDA0002508580750000063

Figure GDA0002508580750000064
Figure GDA0002508580750000064

其中atan2为四象限反正切函数。where atan2 is the four-quadrant arctangent function.

进一步地，可以采用以下方法确定可使第二全桥变换器所有开关管实现ZVS的激励电压总脉冲宽度角β1t的取值范围。α为裕量角，用于保证ZVS的实现。该取值范围为满足以下条件的所有β1t值组成的集合。Further, the following method can be used to determine the value range of the total pulse width angle β 1t of the excitation voltage that enables all switches of the second full-bridge converter to realize ZVS. α is the margin angle, which is used to ensure the realization of ZVS. The value range is the set of all β 1t values that satisfy the following conditions.

当所需的电能传输方向为从第二全桥变换器至第一全桥变换器，且0≤β1t≤180°，所需满足的条件为：When the required power transmission direction is from the second full-bridge converter to the first full-bridge converter, and 0≤β 1t ≤180°, the required conditions are:

Figure GDA0002508580750000071
Figure GDA0002508580750000071

当所需的电能传输方向为从第二全桥变换器至第一全桥变换器，且180°＜β1t≤360°，所需满足的条件为：When the required power transmission direction is from the second full-bridge converter to the first full-bridge converter, and 180°<β 1t ≤ 360°, the required conditions are:

Figure GDA0002508580750000072
Figure GDA0002508580750000072

当所需的电能传输方向为从第一全桥变换器至第二全桥变换器，且0≤β1t≤180°，所需满足的条件为：When the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, and 0≤β 1t ≤180°, the required conditions are:

Figure GDA0002508580750000073
Figure GDA0002508580750000073

当所需的电能传输方向为从第一全桥变换器至第二全桥变换器，且180°＜β1t≤360°，所需满足的条件为：When the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, and 180°<β 1t ≤ 360°, the required conditions are:

Figure GDA0002508580750000074
Figure GDA0002508580750000074

进一步地，在计算出的β1t的取值范围内，选取最优β1t的值，使得激励电压比κ与最优激励电压比κopt最接近。Further, within the calculated value range of β 1t , the optimal value of β 1t is selected so that the excitation voltage ratio κ is the closest to the optimal excitation voltage ratio κ opt .

Figure GDA0002508580750000081
Figure GDA0002508580750000081

Figure GDA0002508580750000082
Figure GDA0002508580750000082

Figure GDA0002508580750000083
Figure GDA0002508580750000083

其中，U1m为第二全桥变换器产生的激励电压的基波幅值，U2m为第一全桥变换器产生的激励电压的基波幅值。Wherein, U 1m is the fundamental wave amplitude of the excitation voltage generated by the second full-bridge converter, and U 2m is the fundamental wave amplitude of the excitation voltage generated by the first full-bridge converter.

进一步地，可以采用以下步骤确定第二全桥变换器的各个开关管的导通和关断时刻。Further, the following steps may be used to determine the turn-on and turn-off moments of each switch tube of the second full-bridge converter.

(51)根据如下方法确定正脉冲宽度角β1+和负脉冲宽度角β1-：(51) Determine the positive pulse width angle β 1+ and the negative pulse width angle β 1- according to the following method:

Figure GDA0002508580750000084
Figure GDA0002508580750000084

Figure GDA0002508580750000085
Figure GDA0002508580750000085

(52)根据β1t值所处的范围确定第二全桥变换器的工作模式：若0≤β1t≤180°，则第二全桥变换器应工作于半桥模式；若180°＜β1t≤360°，则第二全桥变换器应工作于全桥模式。(52) Determine the working mode of the second full-bridge converter according to the range of the value of β 1t : if 0≤β 1t ≤180°, the second full-bridge converter should work in the half-bridge mode; if 180°<β 1t ≤360°, the second full-bridge converter should work in full-bridge mode.

(53)根据所需的电能传输方向确定第二全桥变换器应工作于逆变模式或是整流模式：若所需的电能传输方向为从第二全桥变换器传输至第一全桥变换器，则第二全桥变换器工作于逆变模式；若所需的电能传输方向为从第一全桥变换器传输至第二全桥变换器，则第二全桥变换器工作于整流模式。(53) Determine whether the second full-bridge converter should work in the inverter mode or the rectifier mode according to the required power transmission direction: if the required power transmission direction is from the second full-bridge converter to the first full-bridge converter If the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, the second full-bridge converter works in the rectifier mode .

(54)根据(52)-(53)中所确定的第二全桥变换器的工作模式，确定各个开关管的导通和关断时刻：(54) According to the working mode of the second full-bridge converter determined in (52)-(53), determine the turn-on and turn-off moments of each switch:

若第二全桥变换器工作于逆变全桥模式，则：If the second full-bridge converter works in the inverter full-bridge mode, then:

Figure GDA0002508580750000091
Figure GDA0002508580750000091

其中，

Figure GDA0002508580750000092
和
Figure GDA0002508580750000093
分别为第二全桥变换器的第一桥臂的靠近直流侧正极的开关管的开通和关断时刻相对于第二全桥变换器所产生的激励电压的基波分量由负到正过零时刻之间的相位角，以前者超前后者为正，前者滞后后者为负；
Figure GDA0002508580750000094
和
Figure GDA0002508580750000095
分别为第二全桥变换器的第二桥臂的靠近直流侧正极的开关管的开通和关断时刻相对于第二全桥变换器所产生的激励电压的基波分量由负到正过零时刻之间的相位角，以前者超前后者为正，前者滞后后者为负；in,
Figure GDA0002508580750000092
and
Figure GDA0002508580750000093
are respectively the turn-on and turn-off times of the switch tube of the first bridge arm of the second full-bridge converter close to the positive pole of the DC side, relative to the fundamental wave component of the excitation voltage generated by the second full-bridge converter from negative to positive zero-crossing The phase angle between moments, the former is ahead and the latter is positive, and the former lags behind the latter is negative;
Figure GDA0002508580750000094
and
Figure GDA0002508580750000095
are respectively the turn-on and turn-off times of the switch tube of the second bridge arm of the second full-bridge converter close to the positive pole of the DC side relative to the fundamental component of the excitation voltage generated by the second full-bridge converter from negative to positive zero-crossing The phase angle between moments, the former is ahead and the latter is positive, and the former lags behind the latter is negative;

若第二全桥变换器工作于逆变半桥模式，则：If the second full-bridge converter works in the inverter half-bridge mode, then:

Figure GDA0002508580750000096
Figure GDA0002508580750000096

同时保持第二桥臂的靠近直流侧正极的开关管始终处于关断状态，而第二桥臂的靠近直流侧负极的开关管始终处于导通状态；At the same time, the switch tube of the second bridge arm close to the positive pole of the DC side is always in an off state, and the switch tube of the second bridge arm close to the negative pole of the DC side is always in an on state;

若第二全桥变换器工作于整流全桥模式，则：If the second full-bridge converter works in the rectified full-bridge mode, then:

Figure GDA0002508580750000097
Figure GDA0002508580750000097

若第二全桥变换器工作于整流半桥模式，则：If the second full-bridge converter works in the rectifier half-bridge mode, then:

Figure GDA0002508580750000098
Figure GDA0002508580750000098

同时保持第二桥臂的靠近直流侧正极的开关管始终处于关断状态，而第二桥臂的靠近直流侧负极的开关管始终处于导通状态。At the same time, the switch tube of the second bridge arm close to the positive pole of the DC side is always in an off state, and the switch tube of the second bridge arm close to the negative pole of the DC side is always in an on state.

进一步地，最优激励电压比κopt可以采用如下方法计算：Further, the optimal excitation voltage ratio κ opt can be calculated by the following method:

Figure GDA0002508580750000101
Figure GDA0002508580750000101

其中，r1为第二全桥变换器一侧的等效损耗电阻，r2为第一全桥变换器一侧的等效损耗电阻。Wherein, r 1 is the equivalent loss resistance on the side of the second full-bridge converter, and r 2 is the equivalent loss resistance on the side of the first full-bridge converter.

总体而言，通过本发明所构思的以上技术方案，与现有技术相比，由于采用本发明的方法提高了发送侧、接收侧的功率因数，同时又可以通过使激励电压比等于最优激励电压比从而实现传输效率的优化，从而，本发明所提供的双向无线电能传输系统的双侧不对称电压控制方法，能在宽传输功率范围内实现较高的传输效率，同时使得所有开关器件实现ZVS。In general, through the above technical solutions conceived by the present invention, compared with the prior art, the power factor of the transmitting side and the receiving side can be improved by using the method of the present invention, and at the same time, the excitation voltage ratio can be equal to the optimal excitation voltage. Therefore, the double-sided asymmetric voltage control method of the two-way wireless power transmission system provided by the present invention can achieve high transmission efficiency in a wide transmission power range, and at the same time make all switching devices realize ZVS.

附图说明Description of drawings

图1是本发明实施例的双向无线电能传输系统的主电路示意图；1 is a schematic diagram of a main circuit of a two-way wireless power transmission system according to an embodiment of the present invention;

图2是本发明实施例的双向无线电能传输系统的系统框图；2 is a system block diagram of a two-way wireless power transmission system according to an embodiment of the present invention;

图3是本发明实施例的副边控制器及原边控制器的程序流程图；3 is a program flow diagram of a secondary side controller and a primary side controller according to an embodiment of the present invention;

图4是本发明实施例裕量角为10°时实现ZVS所需的β1t与β2t范围；4 is the range of β 1t and β 2t required to realize ZVS when the margin angle is 10° according to the embodiment of the present invention;

图5是本发明实施例在不同功率下的传输效率与DPS、TPS方法的对比。FIG. 5 is a comparison of the transmission efficiency of the embodiment of the present invention with DPS and TPS methods under different powers.

具体实施方式Detailed ways

为了使本发明的目的、技术方案及优点更加清楚明白，以下结合附图及实施例，对本发明进行进一步详细说明。应当理解，此处所描述的具体实施例仅仅用以解释本发明，并不用于限定本发明。此外，下面所描述的本发明各个实施方式中所涉及到的技术特征只要彼此之间未构成冲突就可以相互组合。In order to make the objectives, technical solutions and advantages of the present invention clearer, the present invention will be further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are only used to explain the present invention, but not to limit the present invention. In addition, the technical features involved in the various embodiments of the present invention described below can be combined with each other as long as they do not conflict with each other.

双向无线电能传输系统包括主电路和控制电路；如图1所示，主电路包括依此级联的原边全桥变换电路，原边谐振补偿网络，耦合机构，副边谐振补偿网络，副边全桥变换电路和滤波电路，原边谐振补偿网络、副边谐振补偿网络为单电容串联。The two-way wireless power transmission system includes a main circuit and a control circuit; as shown in Figure 1, the main circuit includes a primary side full-bridge conversion circuit, a primary side resonance compensation network, a coupling mechanism, a secondary side resonance compensation network, and a secondary side resonance compensation network. The full-bridge conversion circuit and filter circuit, the primary side resonance compensation network and the secondary side resonance compensation network are connected in series with a single capacitor.

在图1所示的主电路中，SS补偿网络各参数满足如下条件：

Figure GDA0002508580750000111
Figure GDA0002508580750000112
其中，ωs为谐振角频率，ωs＝2πfs，fs为谐振频率，开关频率与谐振频率相等，C1为原边补偿电容，C2为副边补偿电容，L1为耦合机构原边线圈自感，L2为耦合机构副边线圈自感。In the main circuit shown in Figure 1, the parameters of the SS compensation network meet the following conditions:
Figure GDA0002508580750000111
Figure GDA0002508580750000112
Among them, ω s is the resonant angular frequency, ω s =2πf s , f s is the resonant frequency, the switching frequency is equal to the resonant frequency, C 1 is the primary side compensation capacitor, C 2 is the secondary side compensation capacitor, L 1 is the original coupling mechanism The self-inductance of the side coil, L 2 is the self-inductance of the secondary side coil of the coupling mechanism.

本发明提供了一种双向无线电能传输系统的双侧不对称电压控制方法，用于在宽传输功率范围内实现较高的传输效率，同时使得所有开关器件实现ZVS。图2所示为一种用于实现本发明所提供的双侧不对称电压控制方法的系统结构示意图，本发明提供的一种双向无线电能传输系统的双侧不对称电压控制方法包括：The invention provides a bilateral asymmetric voltage control method of a two-way wireless power transmission system, which is used for realizing high transmission efficiency in a wide transmission power range, and at the same time enabling all switching devices to realize ZVS. FIG. 2 shows a schematic diagram of a system structure for realizing the double-sided asymmetrical voltage control method provided by the present invention. The double-sided asymmetrical voltage control method of a two-way wireless power transmission system provided by the present invention includes:

(1)获取第一全桥变换器的交流侧端口电流i2的相位，以及第一全桥变换器的直流侧电压Vdc2和直流侧电流Idc2；其中，所述第一全桥变换器为副边全桥变换器且所述第二全桥变换器为原边全桥变换器，或者所述第一全桥变换器为原边全桥变换器且所述第二全桥变换器为副边全桥变换器；(1) Obtain the phase of the AC-side port current i 2 of the first full-bridge converter, as well as the DC-side voltage V dc2 and the DC-side current I dc2 of the first full-bridge converter; wherein, the first full-bridge converter is a secondary-side full-bridge converter and the second full-bridge converter is a primary-side full-bridge converter, or the first full-bridge converter is a primary-side full-bridge converter and the second full-bridge converter is Secondary side full bridge converter;

(2)根据对Vdc2或Idc2的控制要求，计算第一全桥变换器的激励电压的总脉冲宽度角的指令值β2t，确定电能传输方向；(2) According to the control requirements for V dc2 or I dc2 , calculate the command value β 2t of the total pulse width angle of the excitation voltage of the first full-bridge converter, and determine the power transmission direction;

(3)结合(1)中获取到的第一全桥变换器的交流侧端口电流i2的相位，以及(2)中得到的第一全桥变换器的激励电压的总脉冲宽度角的指令值β2t，计算出第一全桥变换器的各个开关管的导通和关断时刻，根据各个开关管的导通和关断时刻，产生对第一全桥变换器的开关管的驱动信号；(3) Combining the phase of the AC side port current i 2 of the first full-bridge converter obtained in (1) and the command of the total pulse width angle of the excitation voltage of the first full-bridge converter obtained in (2) value β 2t , calculate the turn-on and turn-off time of each switch tube of the first full-bridge converter, and generate the drive signal to the switch tube of the first full-bridge converter according to the turn-on and turn-off time of each switch tube ;

(4)将第一全桥变换器的直流侧电压值Vdc2、第一全桥变换器的激励电压的总脉冲宽度角β2t和所需的电能传输方向通过通信通道发送至第二全桥变换器所对应的控制器，同时获取第二全桥变换器的直流侧电压Vdc1，根据给定的裕量角α，计算可使第二全桥变换器所有开关管实现ZVS的第二全桥变换器的激励电压的总脉冲宽度角β1t；(4) Send the DC side voltage value V dc2 of the first full-bridge converter, the total pulse width angle β 2t of the excitation voltage of the first full-bridge converter, and the required power transmission direction to the second full-bridge through the communication channel The controller corresponding to the converter obtains the DC side voltage V dc1 of the second full-bridge converter at the same time, and according to the given margin angle α, calculates that all switches of the second full-bridge converter can realize the second full-bridge of ZVS. the total pulse width angle β 1t of the excitation voltage of the bridge converter;

(5)根据第二全桥变换器的激励电压的总脉冲宽度角β1t，计算第二全桥变换器的各个开关管的导通和关断时刻，根据各个开关管的导通和关断时刻，产生对第二全桥变换器的开关管的驱动信号。(5) According to the total pulse width angle β 1t of the excitation voltage of the second full-bridge converter, calculate the turn-on and turn-off time of each switch tube of the second full-bridge converter, and according to the turn-on and turn-off time of each switch tube At a moment, a drive signal to the switch tube of the second full-bridge converter is generated.

具体地，步骤(2)中，可以使用常规的比例-积分(PI)控制算法，得到第一全桥变换器的激励电压的总脉冲宽度角的指令值β2t。Specifically, in step (2), a conventional proportional-integral (PI) control algorithm can be used to obtain the command value β 2t of the total pulse width angle of the excitation voltage of the first full-bridge converter.

具体地，步骤(3)中，可以采用以下步骤确定第一全桥变换器的各个开关管的导通和关断时刻：Specifically, in step (3), the following steps can be used to determine the turn-on and turn-off moments of each switch tube of the first full-bridge converter:

(31)根据如下方法确定正脉冲宽度角β2+和负脉冲宽度角β2-：(31) Determine the positive pulse width angle β 2+ and the negative pulse width angle β 2- according to the following method:

Figure GDA0002508580750000121
Figure GDA0002508580750000121

Figure GDA0002508580750000122
Figure GDA0002508580750000122

(32)根据β2t值所处的范围确定第一全桥变换器应工作于半桥模式或是全桥模式：若0≤β2t≤180°，则第一全桥变换器应工作于半桥模式；若180°＜β2t≤360°，则第一全桥变换器应工作于全桥模式；(32) Determine whether the first full-bridge converter should work in half-bridge mode or full-bridge mode according to the range of β 2t value: if 0≤β 2t ≤180°, then the first full-bridge converter should work in half-bridge mode Bridge mode; if 180°＜β 2t ≤360°, the first full-bridge converter should work in full-bridge mode;

(33)根据所需的电能传输方向确定第一全桥变换器应工作于整流模式或是逆变模式：若所需的电能传输方向为从第二全桥变换器传输至第一全桥变换器，则第一全桥变换器工作于整流模式；若所需的电能传输方向为从第一全桥变换器传输至第二全桥变换器，则第一全桥变换器工作于逆变模式；(33) Determine whether the first full-bridge converter should work in rectification mode or inverter mode according to the required power transmission direction: if the required power transmission direction is from the second full-bridge converter to the first full-bridge converter If the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, the first full-bridge converter works in the inverter mode ;

(34)根据(32)-(33)中所确定的第一全桥变换器的工作模式，确定各个开关管的导通和关断时刻：(34) According to the working mode of the first full-bridge converter determined in (32)-(33), determine the turn-on and turn-off moments of each switch:

若第一全桥变换器工作于整流全桥模式，则：If the first full-bridge converter works in the rectified full-bridge mode, then:

Figure GDA0002508580750000131
Figure GDA0002508580750000131

若第一全桥变换器工作于整流半桥模式，则：If the first full-bridge converter works in the rectifier half-bridge mode, then:

Figure GDA0002508580750000132
Figure GDA0002508580750000132

同时保持第二桥臂的靠近直流侧正极的开关管始终处于关断状态，而第二桥臂的靠近直流侧负极的开关管始终处于导通状态；At the same time, the switch tube of the second bridge arm close to the positive pole of the DC side is always in an off state, and the switch tube of the second bridge arm close to the negative pole of the DC side is always in an on state;

若第一全桥变换器工作于逆变全桥模式，则：If the first full-bridge converter works in the inverter full-bridge mode, then:

Figure GDA0002508580750000133
Figure GDA0002508580750000133

若第一全桥变换器工作于逆变半桥模式，则：If the first full-bridge converter works in the inverter half-bridge mode, then:

Figure GDA0002508580750000134
Figure GDA0002508580750000134

同时保持第二桥臂的靠近直流侧正极的开关管始终处于关断状态，而第二桥臂的靠近直流侧负极的开关管始终处于导通状态；At the same time, the switch tube of the second bridge arm close to the positive pole of the DC side is always in an off state, and the switch tube of the second bridge arm close to the negative pole of the DC side is always in an on state;

其中，αon5和αoff5分别为第一全桥变换器的第一桥臂的靠近直流侧正极的开关管的开通和关断时刻相对于i2的基波分量由负到正过零时刻之间的相位角，以前者超前后者为正，前者滞后后者为负；αon7和αoff7分别为第一全桥变换器的第二桥臂的靠近直流侧正极的开关管的开通和关断时刻相对于i2的基波分量由负到正过零时刻之间的相位角，以前者超前后者为正，前者滞后后者为负；α为裕量角；max为最大值函数。Among them, α on5 and α off5 are respectively the time between the turn-on and turn-off time of the switch tube of the first bridge arm of the first full-bridge converter close to the positive pole of the DC side relative to the fundamental wave component of i 2 from negative to positive zero-crossing time The phase angle between α and α, the former is ahead and the latter is positive, the former lags the latter and is negative; α on7 and α off7 are the turn-on and turn-off of the switch tube of the second bridge arm of the first full-bridge converter, which is close to the positive electrode of the DC side, respectively. The phase angle from negative to positive zero-crossing moment relative to the fundamental wave component of i 2 , the former is ahead of the latter and the latter is positive, and the former lags behind the latter is negative; α is the margin angle; max is the maximum value function.

进一步地，步骤(4)中，可以采用以下步骤确定第二全桥变换器的激励电压总脉冲宽度角β1t的取值范围：Further, in step (4), the following steps can be used to determine the value range of the total pulse width angle β 1t of the excitation voltage of the second full-bridge converter:

(41)根据如下方法确定正脉冲宽度角β1+和负脉冲宽度角β1-：(41) Determine the positive pulse width angle β 1+ and the negative pulse width angle β 1- according to the following method:

Figure GDA0002508580750000141
Figure GDA0002508580750000141

Figure GDA0002508580750000142
Figure GDA0002508580750000142

(42)根据所需的电能传输方向确定第二全桥变换器应工作于逆变模式或是整流模式：若所需的电能传输方向为从第二全桥变换器传输至第一全桥变换器，则第一全桥变换器工作于逆变模式；若所需的电能传输方向为从第一全桥变换器传输至第二全桥变换器，则第一全桥变换器工作于整流模式；(42) Determine whether the second full-bridge converter should work in the inverter mode or the rectifier mode according to the required power transmission direction: if the required power transmission direction is from the second full-bridge converter to the first full-bridge converter If the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, the first full-bridge converter works in the rectifier mode ;

(43)根据所需的电能传输方向，根据下式计算：第一全桥变换器产生的激励电压的基波分量由负到正过零点时刻与第一全桥变换器产生的激励电压的正脉冲上升沿所对应的时刻之间的相位差θ2,rec或θ2,inv、第二全桥变换器产生的激励电压的基波分量由负到正过零点时刻与第二全桥变换器产生的激励电压的正脉冲上升沿所对应的时刻之间的相位差θ1,rec或θ1,inv。若所需的电能传输方向为从第二全桥变换器至第一全桥变换器，则计算θ2,rec与θ1,inv；若所需的电能传输方向为从第一全桥变换器至第二全桥变换器，则计算θ2,inv与θ1,rec，rec代表整流模式，inv代表逆变模式。(43) According to the required power transmission direction, calculate according to the following formula: the fundamental wave component of the excitation voltage generated by the first full-bridge converter changes from negative to positive zero-crossing time and the positive value of the excitation voltage generated by the first full-bridge converter. The phase difference θ 2,rec or θ 2,inv between the times corresponding to the rising edge of the pulse, the fundamental wave component of the excitation voltage generated by the second full-bridge converter changes from negative to positive zero-crossing time and the second full-bridge converter. The phase difference θ 1,rec or θ 1,inv between the times corresponding to the rising edge of the positive pulse of the generated excitation voltage. If the required power transfer direction is from the second full-bridge converter to the first full-bridge converter, calculate θ 2,rec and θ 1,inv ; if the required power transfer direction is from the first full-bridge converter To the second full-bridge converter, θ 2,inv and θ 1,rec are calculated, where rec represents the rectification mode, and inv represents the inverter mode.

Figure GDA0002508580750000143
Figure GDA0002508580750000143

Figure GDA0002508580750000144
Figure GDA0002508580750000144

Figure GDA0002508580750000151
Figure GDA0002508580750000151

Figure GDA0002508580750000152
Figure GDA0002508580750000152

其中atan2为四象限反正切函数。where atan2 is the four-quadrant arctangent function.

进一步地，可以采用以下方法确定可使第二全桥变换器所有开关管实现ZVS的激励电压总脉冲宽度角β1t的取值范围。α为裕量角，用于保证ZVS的实现。Further, the following method can be used to determine the value range of the total pulse width angle β 1t of the excitation voltage that enables all switches of the second full-bridge converter to realize ZVS. α is the margin angle, which is used to ensure the realization of ZVS.

该取值范围为满足以下条件的所有β1t值组成的集合。The value range is the set of all β 1t values that satisfy the following conditions.

当所需的电能传输方向为从第二全桥变换器至第一全桥变换器，且0≤β1t≤180°，所需满足的条件为：When the required power transmission direction is from the second full-bridge converter to the first full-bridge converter, and 0≤β 1t ≤180°, the required conditions are:

Figure GDA0002508580750000153
Figure GDA0002508580750000153

当所需的电能传输方向为从第二全桥变换器至第一全桥变换器，且180°＜β1t≤360°，所需满足的条件为：When the required power transmission direction is from the second full-bridge converter to the first full-bridge converter, and 180°<β 1t ≤ 360°, the required conditions are:

Figure GDA0002508580750000154
Figure GDA0002508580750000154

当所需的电能传输方向为从第一全桥变换器至第二全桥变换器，且0≤β1t≤180°，所需满足的条件为：When the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, and 0≤β 1t ≤180°, the required conditions are:

Figure GDA0002508580750000155
Figure GDA0002508580750000155

当所需的电能传输方向为从第一全桥变换器至第二全桥变换器，且180°＜β1t≤360°，所需满足的条件为：When the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, and 180°<β 1t ≤ 360°, the required conditions are:

Figure GDA0002508580750000161
Figure GDA0002508580750000161

进一步地，在计算出的β1t的取值范围内，选取最优β1t的值，使得激励电压比κ与最优激励电压比κopt最接近。Further, within the calculated value range of β 1t , the optimal value of β 1t is selected so that the excitation voltage ratio κ is the closest to the optimal excitation voltage ratio κ opt .

κ＝U1m κ=U 1m

U2m U 2m

Figure GDA0002508580750000162
Figure GDA0002508580750000162

Figure GDA0002508580750000163
Figure GDA0002508580750000163

其中，U1m为第二全桥变换器产生的激励电压的基波幅值，U2m为第一全桥变换器产生的激励电压的基波幅值。Wherein, U 1m is the fundamental wave amplitude of the excitation voltage generated by the second full-bridge converter, and U 2m is the fundamental wave amplitude of the excitation voltage generated by the first full-bridge converter.

进一步地，可以采用以下步骤确定第二全桥变换器的各个开关管的导通和关断时刻。Further, the following steps may be used to determine the turn-on and turn-off moments of each switch tube of the second full-bridge converter.

(51)根据如下方法确定正脉冲宽度角β1+和负脉冲宽度角β1-：(51) Determine the positive pulse width angle β 1+ and the negative pulse width angle β 1- according to the following method:

Figure GDA0002508580750000164
Figure GDA0002508580750000164

Figure GDA0002508580750000165
Figure GDA0002508580750000165

(52)根据β1t值所处的范围确定第二全桥变换器的工作模式：若0≤β1t≤180°，则第二全桥变换器应工作于半桥模式；若180°＜β1t≤360°，则第二全桥变换器应工作于全桥模式。(52) Determine the working mode of the second full-bridge converter according to the range of the value of β 1t : if 0≤β 1t ≤180°, the second full-bridge converter should work in the half-bridge mode; if 180°<β 1t ≤360°, the second full-bridge converter should work in full-bridge mode.

(53)根据所需的电能传输方向确定第二全桥变换器应工作于逆变模式或是整流模式：若所需的电能传输方向为从第二全桥变换器传输至第一全桥变换器，则第二全桥变换器工作于逆变模式；若所需的电能传输方向为从第一全桥变换器传输至第二全桥变换器，则第二全桥变换器工作于整流模式。(53) Determine whether the second full-bridge converter should work in the inverter mode or the rectifier mode according to the required power transmission direction: if the required power transmission direction is from the second full-bridge converter to the first full-bridge converter If the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, the second full-bridge converter works in the rectifier mode .

(54)根据(52)-(53)中所确定的第二全桥变换器的工作模式，确定各个开关管的导通和关断时刻：(54) According to the working mode of the second full-bridge converter determined in (52)-(53), determine the turn-on and turn-off moments of each switch:

若第二全桥变换器工作于逆变全桥模式，则：If the second full-bridge converter works in the inverter full-bridge mode, then:

Figure GDA0002508580750000171
Figure GDA0002508580750000171

其中，

Figure GDA0002508580750000172
和
Figure GDA0002508580750000173
分别为第二全桥变换器的第一桥臂的靠近直流侧正极的开关管的开通和关断时刻相对于第二全桥变换器所产生的激励电压的基波分量由负到正过零时刻之间的相位角，以前者超前后者为正，前者滞后后者为负；
Figure GDA0002508580750000174
和
Figure GDA0002508580750000175
分别为第二全桥变换器的第二桥臂的靠近直流侧正极的开关管的开通和关断时刻相对于第二全桥变换器所产生的激励电压的基波分量由负到正过零时刻之间的相位角，以前者超前后者为正，前者滞后后者为负；in,
Figure GDA0002508580750000172
and
Figure GDA0002508580750000173
are respectively the turn-on and turn-off times of the switch tube of the first bridge arm of the second full-bridge converter close to the positive pole of the DC side, relative to the fundamental wave component of the excitation voltage generated by the second full-bridge converter from negative to positive zero-crossing The phase angle between moments, the former is ahead and the latter is positive, and the former lags behind the latter is negative;
Figure GDA0002508580750000174
and
Figure GDA0002508580750000175
are respectively the turn-on and turn-off times of the switch tube of the second bridge arm of the second full-bridge converter close to the positive pole of the DC side relative to the fundamental component of the excitation voltage generated by the second full-bridge converter from negative to positive zero-crossing The phase angle between moments, the former is ahead and the latter is positive, and the former lags behind the latter is negative;

若第二全桥变换器工作于逆变半桥模式，则：If the second full-bridge converter works in the inverter half-bridge mode, then:

Figure GDA0002508580750000176
Figure GDA0002508580750000176

同时保持第二桥臂的靠近直流侧正极的开关管始终处于关断状态，而第二桥臂的靠近直流侧负极的开关管始终处于导通状态；At the same time, the switch tube of the second bridge arm close to the positive pole of the DC side is always in an off state, and the switch tube of the second bridge arm close to the negative pole of the DC side is always in an on state;

若第二全桥变换器工作于整流全桥模式，则：If the second full-bridge converter works in the rectified full-bridge mode, then:

Figure GDA0002508580750000181
Figure GDA0002508580750000181

若第二全桥变换器工作于整流半桥模式，则：If the second full-bridge converter works in the rectifier half-bridge mode, then:

Figure GDA0002508580750000182
Figure GDA0002508580750000182

同时保持第二桥臂的靠近直流侧正极的开关管始终处于关断状态，而第二桥臂的靠近直流侧负极的开关管始终处于导通状态。At the same time, the switch tube of the second bridge arm close to the positive pole of the DC side is always in an off state, and the switch tube of the second bridge arm close to the negative pole of the DC side is always in an on state.

进一步地，最优激励电压比κopt可以采用如下方法计算：Further, the optimal excitation voltage ratio κ opt can be calculated by the following method:

Figure GDA0002508580750000183
Figure GDA0002508580750000183

其中，r1为第二全桥变换器一侧的等效损耗电阻，r2为第一全桥变换器一侧的等效损耗电阻。Wherein, r 1 is the equivalent loss resistance on the side of the second full-bridge converter, and r 2 is the equivalent loss resistance on the side of the first full-bridge converter.

在图1所示的主电路中，设置各元件参数如下：L1＝183.25μH，L2＝180.45μH，M＝35.46μH，C1＝19.11nF，C2＝19.42nF，r1＝0.34Ω，r2＝0.35Ω，Vdc1＝288V，Vdc2＝288V，α＝10°，开关频率等于谐振频率，为85kHz。采用上述双侧不对称电压控制方法的系统结构图如图2所示，程序流程图如图3所示，按照步骤(6)计算出的实现ZVS的β1t，β2t取值范围如图4所示。实验所得本实施例与单级双侧对称激励电压三移相控制和单级双侧对称激励电压三移相控制在相同副边接收功率下的系统传输效率如图5所示。由图5可见，在相同的功率下，本发明实施例所能达到的效率高于单级双侧对称激励电压三移相控制和单级双侧对称激励电压三移相控制所能达到的效率。In the main circuit shown in Fig. 1, the parameters of each element are set as follows: L 1 =183.25μH, L 2 =180.45μH, M=35.46μH, C 1 =19.11nF, C 2 =19.42nF, r 1 =0.34Ω , r 2 =0.35Ω, V dc1 =288V, V dc2 =288V, α=10°, the switching frequency is equal to the resonant frequency, which is 85kHz. The system structure diagram of the above-mentioned double-sided asymmetric voltage control method is shown in Figure 2, and the program flow chart is shown in Figure 3. The value ranges of β 1t and β 2t for realizing ZVS calculated according to step (6) are shown in Figure 4 shown. Figure 5 shows the system transmission efficiency of this embodiment, the single-stage double-sided symmetrical excitation voltage three-phase-shift control and the single-stage double-sided symmetrical excitation voltage three-phase-shift control under the same secondary side received power. It can be seen from FIG. 5 that, under the same power, the efficiency that the embodiment of the present invention can achieve is higher than the efficiency that can be achieved by the single-stage double-sided symmetrical excitation voltage three-phase-shift control and the single-stage double-sided symmetrical excitation voltage three-phase-shift control. .

本领域的技术人员容易理解，以上所述仅为本发明的较佳实施例而已，并不用以限制本发明，凡在本发明的精神和原则之内所作的任何修改、等同替换和改进等，均应包含在本发明的保护范围之内。Those skilled in the art can easily understand that the above are only preferred embodiments of the present invention, and are not intended to limit the present invention. Any modifications, equivalent replacements and improvements made within the spirit and principles of the present invention, etc., All should be included within the protection scope of the present invention.

Claims (4)

1. A bilateral asymmetric voltage control method of a bidirectional wireless power transmission system is characterized by comprising the following steps:
(1) obtaining an AC side port current i of a first full bridge converter2Phase of the first full-bridge inverter, the DC-side voltage V of the first full-bridge inverterdc2And a direct side current Idc2；
(2) According to pair Vdc2Or Idc2The command value β of the total pulse width angle of the excitation voltage of the first full-bridge inverter is calculated by the PI control algorithm2tDetermining the electric energy transmission direction;
(3) combining the alternating current port current i of the first full-bridge converter obtained in the step (1)2And the command value β of the total pulse width angle of the excitation voltage of the first full-bridge inverter obtained in step (2)2tCalculating the on and off time of each switching tube of the first full-bridge converter, and generating a driving signal for the switching tube of the first full-bridge converter; the method specifically comprises the following steps:
(31) determining positive pulse width angle β2+And negative pulse width angle β2-：
Figure FDA0002508580740000011
Figure FDA0002508580740000012
(32) According to β2tThe value range determines whether the first full-bridge inverter should operate in half-bridge mode or full-bridge mode if 0 ≦ β2tLess than 180 deg., the first full-bridge converter should be operated in half-bridge mode, and less than β deg2tThe angle is less than or equal to 360 degrees, and the first full-bridge converter is required to work in a full-bridge mode;
(33) determining whether the first full-bridge converter should work in a rectification mode or an inversion mode according to the required electric energy transmission direction: if the required electric energy transmission direction is from the second full-bridge converter to the first full-bridge converter, the first full-bridge converter works in a rectification mode; if the required electric energy transmission direction is from the first full-bridge converter to the second full-bridge converter, the first full-bridge converter works in an inversion mode;
(34) if the first full-bridge converter operates in the rectified full-bridge mode, then:
Figure FDA0002508580740000021
if the first full-bridge converter operates in the rectifying half-bridge mode, then:
Figure FDA0002508580740000022
meanwhile, the switching tube of the second bridge arm close to the positive pole of the direct current side is kept in an off state all the time, and the switching tube of the second bridge arm close to the negative pole of the direct current side is kept in an on state all the time;
if the first full-bridge converter operates in the inverted full-bridge mode, then:
Figure FDA0002508580740000023
if the first full-bridge converter operates in the inverter half-bridge mode, then:
Figure FDA0002508580740000024
meanwhile, the switching tube of the second bridge arm close to the positive pole of the direct current side is kept in an off state all the time, and the switching tube of the second bridge arm close to the negative pole of the direct current side is kept in an on state all the time;
wherein, αon5And αoff5The on and off time of a switching tube close to the positive electrode of the direct current side of a first bridge arm of the first full-bridge converter is relative to i2α that the fundamental component of (A) leads the latter to be positive and lags the latter to be negativeon7And αoff7The on and off time of a switching tube close to the positive electrode of the direct current side of the second bridge arm of the first full-bridge converter is relative to i2The phase angle between the zero crossing time from negative to positive of the fundamental component of (c) is positive when the former leads the latter and negative when the former lags the latter, α is a margin angle, max is a maximum function;
(4) the DC side voltage value V of the first full-bridge converterdc2Command value β for total pulse width angle of excitation voltage of first full-bridge converter2tThe required electric energy transmission direction is sent to the controller corresponding to the second full-bridge converter through the communication channel, and the direct-current side voltage V of the second full-bridge converter is obtained at the same timedc1Calculating the total pulse width angle β of the excitation voltage of the second full-bridge converter which can make all the switch tubes of the second full-bridge converter realize zero-voltage turn-on according to the preset margin angle α1t(ii) a The method specifically comprises the following steps:
(41) the positive pulse width angle β is determined according to the following method1+And negative pulse width angle β1-：
Figure FDA0002508580740000031
Figure FDA0002508580740000032
(42) Determining whether the second full-bridge converter should work in an inversion mode or a rectification mode according to the required electric energy transmission direction: if the required electric energy transmission direction is from the second full-bridge converter to the first full-bridge converter, the first full-bridge converter works in an inversion mode; if the required electric energy transmission direction is from the first full-bridge converter to the second full-bridge converter, the first full-bridge converter works in a rectification mode;
(43)β1tis that all β satisfying the following conditions1tSet of values:
when the required electric energy transmission direction is from the second full-bridge converter to the first full-bridge converter and is not less than 0 and not more than β1tLess than or equal to 180 degrees, and the required conditions are as follows:
Figure FDA0002508580740000033
when the required power transmission direction is from the second full-bridge inverter to the first full-bridge inverter, and 180 DEG < β1tLess than or equal to 360 degrees, and the required conditions are as follows:
Figure FDA0002508580740000041
when the required electric energy transmission direction is from the first full-bridge converter to the second full-bridge converter and is not less than 0 and not more than β1tLess than or equal to 180 degrees, and the required conditions are as follows:
Figure FDA0002508580740000042
when the required power transmission direction is from the first full-bridge converter to the second full-bridge converter, and 180 DEG < β1tLess than or equal to 360 degrees, and the required conditions are as follows:
Figure FDA0002508580740000043
wherein, the fundamental component of the excitation voltage generated by the first full-bridge converter is from negative to positive zero crossing point timeThe phase difference theta between the moments corresponding to the rising edges of the positive pulses of the excitation voltage generated by the first full-bridge inverter2,recOr theta2,invA phase difference theta between the moment when the fundamental wave component of the excitation voltage generated by the second full-bridge inverter crosses zero from negative to positive and the moment corresponding to the rising edge of the positive pulse of the excitation voltage generated by the second full-bridge inverter1,recOr theta1,inv，β2+Rec represents a rectification mode and inv represents an inversion mode for a positive pulse width angle;
(5) from the total pulse width angle β of the excitation voltage of the second full-bridge converter1tCalculating the on and off time of each switching tube of the second full-bridge converter, and generating a driving signal for the switching tube of the second full-bridge converter; the method specifically comprises the following steps:
(51) determining positive pulse width angle β1+And negative pulse width angle β1-：
Figure FDA0002508580740000051
Figure FDA0002508580740000052
(52) According to β1tThe range of the value determines the working mode of the second full-bridge converter, if 0 is less than or equal to β1tLess than 180 deg., the second full-bridge converter should be operated in half-bridge mode, and less than β deg1tThe angle is less than or equal to 360 degrees, the second full-bridge converter should work in a full-bridge mode;
(53) determining whether the second full-bridge converter should work in an inversion mode or a rectification mode according to the required electric energy transmission direction: if the required electric energy transmission direction is from the second full-bridge converter to the first full-bridge converter, the second full-bridge converter works in an inversion mode; if the required electric energy transmission direction is from the first full-bridge converter to the second full-bridge converter, the second full-bridge converter works in a rectification mode;
(54) if the second full-bridge converter operates in the inverted full-bridge mode, then:
Figure FDA0002508580740000053
wherein,
Figure FDA0002508580740000054
and
Figure FDA0002508580740000055
the on and off time of a switching tube close to the positive pole of the direct current side of a first bridge arm of a second full-bridge converter is respectively relative to a phase angle between the negative and positive zero-crossing time of a fundamental component of excitation voltage generated by the second full-bridge converter, the former leads the latter to be positive, and the former lags the latter to be negative;
Figure FDA0002508580740000056
and
Figure FDA0002508580740000057
the on and off time of a switching tube close to the positive pole of the direct current side of a second bridge arm of the second full-bridge converter is respectively relative to a phase angle between the negative and positive zero-crossing time of a fundamental component of excitation voltage generated by the second full-bridge converter, wherein the former is in advance of the latter and the former is in lag behind the latter;
if the second full-bridge converter operates in the inverter half-bridge mode, then:
Figure FDA0002508580740000058
meanwhile, the switching tube of the second bridge arm close to the positive pole of the direct current side is always kept in an off state, and the switching tube of the second bridge arm close to the negative pole of the direct current side is always kept in an on state;
if the second full-bridge converter operates in the rectified full-bridge mode, then:
Figure FDA0002508580740000061
if the second full-bridge converter operates in the rectifying half-bridge mode, then:
Figure FDA0002508580740000062
meanwhile, the switching tube of the second bridge arm close to the positive pole of the direct current side is always kept in an off state, and the switching tube of the second bridge arm close to the negative pole of the direct current side is always kept in an on state.
2. The bilateral asymmetric voltage control method of claim 1, wherein the first full-bridge inverter is a secondary full-bridge inverter and the second full-bridge inverter is a primary full-bridge inverter, or the first full-bridge inverter is a primary full-bridge inverter and the second full-bridge inverter is a secondary full-bridge inverter.
3. The bilateral asymmetric voltage control method of claim 1 wherein if the desired power transfer direction is from the second full-bridge inverter to the first full-bridge inverter, then θ is calculated2,recAnd theta1,inv(ii) a If the required power transfer direction is from the first full-bridge inverter to the second full-bridge inverter, then θ is calculated2,invAnd theta1,recAre respectively expressed by the following formulas:
Figure FDA0002508580740000063
Figure FDA0002508580740000064
Figure FDA0002508580740000071
Figure FDA0002508580740000072
wherein atan2 is a four quadrant arctangent function, β2+Is a positive pulse width angle, β2-For a negative pulse width angle, rec represents the rectification mode and inv represents the inversion mode.
4. The method of bilateral asymmetric voltage control for a two-way wireless power transfer system of claim 1 wherein at calculated β1tWithin the value range of (A), selecting the optimal β1tSuch that the excitation voltage ratio k is equal to the optimum excitation voltage ratio koptMost closely, it is formulated as:
Figure FDA0002508580740000073
Figure FDA0002508580740000074
Figure FDA0002508580740000075
Figure FDA0002508580740000076
wherein, U1mFundamental amplitude, U, of the excitation voltage generated for the second full-bridge inverter2mFundamental amplitude, r, of the excitation voltage generated for the first full-bridge inverter1Is an equivalent loss resistance on the side of the second full-bridge inverter, r2Is the equivalent loss resistance on one side of the first full-bridge inverter.
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