CN110426670B - Super-resolution DOA estimation method for external radiation source radar based on TLS-CS - Google Patents
Super-resolution DOA estimation method for external radiation source radar based on TLS-CS Download PDFInfo
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Abstract
The invention discloses a TLS-CS-based super-resolution DOA estimation method for an external radiation source radar. The method mainly solves the problem that compressed sensing super-resolution DOA estimation angle measurement precision and target resolution are reduced due to array amplitude-phase errors in the prior art. It includes: obtaining echo received by an array antenna and direct wave received by a reference antenna; utilizing the direct wave and the multipath interference signal in the delay suppression echo of the direct wave to perform distance-Doppler two-dimensional correlation processing on the echo signal after clutter suppression to obtain a complex vector signal S; then adding amplitude-phase disturbance to S to obtain complex vector signal with amplitude-phase error
Constructing a guide vector D of the whole observation space, and solving the guide vector D to obtain a guide vector after correcting the amplitude-phase error
By using
And
and carrying out sparse reconstruction on the azimuth information of the plurality of targets to obtain the azimuth of the targets. The invention reduces the influence of array amplitude-phase errors on the steering vectors, improves the angle measurement precision and the resolution performance of the target, and can be used for positioning the target.
Description
Technical Field
The invention belongs to the technical field of radar signal processing, and particularly relates to a super-resolution DOA estimation method for an external radiation source radar, which can be used for target positioning.
Background
The external radiation source radar refers to a radar system which does not actively emit electromagnetic waves and is implemented by relying on existing third-party non-cooperative radiation source signals in a target reflection environment, such as frequency modulation broadcast FM, television signals and mobile phone signals, for detecting, positioning and tracking a target. The radiation source signal frequency band used by the system radar is low, the system radar irradiates towards the ground, and the system radar has the capabilities of hiding and detecting low-altitude targets, so that the system radar is widely concerned.
In an external radiation source radar system, DOA estimation of the direction of arrival of array signals is a very important link in a target positioning process. Generally, the energy of echo signals reflected by a target received by an array antenna is far lower than that of strong direct waves from a radiation source and multipath clutter and noise signals reflected by the ground and buildings, and direct direction finding of the target is difficult to achieve. In order to estimate DOA of a target in an external radiation source radar, firstly, a clutter cancellation algorithm is utilized to suppress strong direct waves and multipath clutter signals in echo signals received by an array antenna; then, the signal-to-noise ratio of the received target echo signal is improved by using range-Doppler two-dimensional correlation processing; and finally, performing compressed sensing sparse reconstruction on the azimuth information of the plurality of targets on the range-Doppler unit where the targets are located, and realizing super-resolution DOA estimation. However, good performance can only be achieved with compressed sensing without errors in the array. In an actual external radiation source radar system, amplitude and phase gains of all channels of an array are usually inconsistent, namely, amplitude and phase errors exist in the array, and therefore mismatching of a steering vector can be caused.
In summary, when amplitude and phase errors exist in the array, the angle measurement precision and the target resolution performance of the existing method are sharply reduced, and the target super-resolution DOA estimation cannot be effectively realized.
Disclosure of Invention
The invention aims to provide an external radiation source radar super-resolution DOA estimation method based on total least square-compressive sensing TLS-CS (total least squares-compressive sensing) aiming at the defects of the prior art, so that the angle measurement precision and the target resolution performance of target super-resolution DOA estimation are improved, and the target super-resolution DOA estimation is effectively realized.
The idea for achieving the purpose of the invention is to solve a total least square TLS signal model with amplitude-phase errors through a singular value decomposition method to obtain a guide vector after the amplitude-phase errors are corrected, the corrected guide vector is used as a sensing matrix, and a greedy iterative tracking matching algorithm is used for carrying out compressed sensing sparse reconstruction on the azimuth information of a target to achieve super-resolution DOA estimation.
According to the above thought, the implementation scheme of the invention comprises the following steps:
(1) respectively acquiring echo signals S received by array antennas ech And a reference antenna for receiving the direct wave signal S in the radiation source direction ref ；
(2) Utilizing a reference antenna to receive a direct wave signal in the radiation source direction, and adopting an extended cancellation algorithm to suppress the direct wave and multipath interference in an echo signal to obtain an echo signal S after clutter suppression sur ；
(3) Echo signal S after clutter suppression sur Performing distance-Doppler two-dimensional correlation processing to obtain a complex vector signal S;
S＝A*S tar +Z <1>
S tar representing a target echo signal, A representing a steering vector corresponding to a target, and Z representing a noise signal;
(4) adding amplitude-phase disturbance parameter delta A to the complex vector signal S to obtain a TLS signal model with amplitude-phase errors,
for complex vector signals with amplitude and phase errors:
(5) setting the number of rows of a guide vector of the whole observation space as the number M of array elements and the number of columns as the number N of division of the observation space, and constructing an MxN dimensional matrix as a guide vector D of an observation interval;
(6) taking the guide vector D of the whole observation interval as a guide vector with amplitude-phase disturbance, and substituting the guide vector D into the complex vector signal
Solving the error by using a singular value decomposition method to obtain a guide vector with corrected amplitude-phase error
(7) Will complex vector signal
As a measurement vector, a guide vector after correcting an amplitude-phase error
And as a sensing matrix, carrying out compressed sensing sparse reconstruction on the orientation information of a plurality of targets in the same range-Doppler unit by using a greedy iterative tracking algorithm to obtain the orientation information of the plurality of targets.
Compared with the prior art, the invention has the following advantages:
1. according to the method, the influence of the amplitude-phase error on the echo signal is considered, the amplitude-phase error is added into the echo signal model, the corrected amplitude-phase error is solved by using a singular value decomposition method, sparse reconstruction is carried out on orientation information of a plurality of targets by using a greedy iterative matching tracking algorithm, the orientation of the targets is obtained, and the angle measurement precision and the resolution performance of the targets are improved.
2. The invention only needs the array antenna for receiving echo signals and the reference antenna for receiving direct wave signals, does not need additional calibration antennas and is simple to realize.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to these drawings without creative efforts.
FIG. 1 is a schematic diagram of an application scenario of an external radiation source radar;
FIG. 2 is a flow chart of an implementation of the present invention;
FIG. 3 is a graph of simulation results for a conventional method and the method of the present invention in the absence of amplitude and phase errors;
FIG. 4 is a graph of simulation results of a conventional method and the method of the present invention in the presence of amplitude and phase errors.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
First, for the sake of understanding, the following will be based on the application scenario of the external radiation source radar shown in fig. 1, which is described as follows:
as shown in fig. 1, a third-party non-cooperative external radiation source is placed in a far field of a radar receiving station of the external radiation source to serve as a transmitting station, so as to transmit an electromagnetic wave signal, a signal reflected by a target in a coverage space of the array antenna irradiated by the electromagnetic wave signal is called a target echo signal, and an electromagnetic wave directly irradiated on a reference antenna without reflection is called a direct wave signal, which is also called a reference signal. The external radiation source radar receives a target echo signal through the array antenna, receives a direct wave signal through the reference antenna, and then processes the target echo signal and the direct wave signal by using a radar signal processing algorithm so as to obtain distance, speed and azimuth information of a target. As can be seen from fig. 1, the external radiation source radar array antenna inevitably receives a strong direct wave signal from the direction of the transmitting station and a multipath interference signal reflected by different obstacles, in addition to the target echo signal, and in general, the energy of the target echo signal is much lower than that of the direct wave and the multipath interference signal, so that the direct wave and the multipath interference signal received by the array antenna need to be eliminated by using the direct wave received by the reference antenna, and the energy of the target echo is improved by distance-doppler processing.
Referring to fig. 2, an embodiment of the present invention provides an external radiation source radar super-resolution DOA estimation method based on total least square-compressive sensing, which includes the following implementation steps:
step 1: respectively acquiring echo signals S received by array antennas ech And a reference antenna for receiving the direct wave signal S in the radiation source direction ref ；
The array antenna is composed of uniform linear arrays with array element spacing of half wavelength, the number of the array elements is M, M is more than or equal to 11, and M echo signals S are received ech Wherein each echo signal S ech The method comprises the steps of (1) including a strong direct wave from the direction of a transmitting station, a multipath interference signal reflected by a multipath and a noise signal;
the reference antenna is composed of a narrow beam antenna which is independently pointed to the direction of the transmitting station and receives a direct wave signal S from the direction of the radiation source ref 。
Step 2: receiving direct wave signal S of radiation source direction by using reference antenna ref Echo signal S is processed by using an extended cancellation algorithm ech Suppressing the direct wave and the multi-path interference signal to obtain an echo signal S after clutter suppression sur 。
Echo signal S received by array antenna ref Not only includes echo signal reflected by target, but also includes direct wave signal from radiation source and multipath reflected by building and roadThe clutter signals, which have much larger energy than the target echo signal, cause the target echo to be submerged in the clutter signal, and the target cannot be detected, so the clutter signal must be suppressed. By projecting the echo signal onto the direct wave signal S ref And the clutter signals have a group of projection coefficients which are not completely zero in the orthogonal subspace V and represent the intensity of various clutter signals, and the clutter existing in the echo signals can be eliminated by solving the group of projection coefficients which are not completely zero to obtain echo signals S after clutter suppression sur 。
The specific implementation of this step is as follows:
(2a) using direct waves S ref And constructing a clutter orthogonal subspace V by time delay:
wherein G is the data length of the direct wave signal, C is the clutter cancellation order, the first column of the matrix represents the direct wave signal, the second column represents the multipath signal with the time delay unit of one, and the Nth column represents the multipath signal with the time delay unit of C;
(2b) echo signal S ech Projecting into a clutter orthogonal subspace V, solving the set of projection coefficients W which are not all zero on the subspace:
W＝(V H *V) -1 V H S ech ， <3>wherein V H Represents the conjugate transpose of the matrix V, (V) H *V) -1 Expressing the inversion of the matrix product result;
(2c) based on the echo signal S ech Obtaining a clutter suppressed residual echo signal S by using a clutter orthogonal subspace V and a projection coefficient W which is not completely zero sur ：
S sur ＝S ech -V*W。 <4>
And step 3: for residual echo signal S sur And performing distance-Doppler two-dimensional correlation processing to obtain a complex vector signal S.
By clutter suppressionAfter, echo signal S ech The clutter signal contained in has been eliminated, however, the residual echo signal S sur The energy of the target echo signal in the S-Doppler signal is still lower than that of the noise signal, so that the energy of the target echo signal is improved by performing range-Doppler two-dimensional correlation processing to obtain a signal model under an ideal condition, and the S is a complex vector signal obtained after the range-Doppler two-dimensional correlation processing.
The specific implementation of this step is as follows:
(3a) the residual echo signal S after clutter suppression sur With time-delayed conjugate reference signal S ref * [g-τ]Point multiplication to obtain complex vector signal S after distance dimension correlation processing m ：
Wherein tau represents the distance of the moving object and G is the residual echo signal S sur The length of (d);
(3b) the complex vector signal S after the distance dimension correlation processing m After Doppler dimension correlation accumulation is carried out, a target signal S after Doppler dimension correlation accumulation is obtained tar ：
(3c) For the target signal S tar Adding a guide vector A and a noise Z to obtain a distance-Doppler two-dimensional correlation processing complex vector signal S:
S＝A*S tar +Z。 <7>
and 4, step 4: adding amplitude-phase disturbance parameter delta A to the complex vector signal S to obtain a TLS signal model with amplitude-phase errors,
for complex vector signals with amplitude and phase errors: .
The complex vector signal S in the step 3 is derived under the ideal condition, but the actual working of the radar at the external radiation sourceIn operation, the complex vector signal S is inevitably affected by amplitude-phase errors and is therefore in<7>Adding the amplitude-phase error delta A into the formula to obtain a TLS model,
for complex vector signals with amplitude and phase errors:
and 5: and constructing a guide vector D of the whole observation space.
And (3) establishing an M multiplied by N dimensional matrix as a guide vector D of an observation interval by setting the row number of the guide vector of the whole observation space as an array element number M and the column number as a division number N of the observation space:
wherein, theta 1 To the starting position of the observation interval, θ N D is the distance between the antenna elements, and lambda is the wavelength of the emitted electromagnetic wave.
Step 6: taking the guide vector D of the whole observation interval as a guide vector with amplitude-phase disturbance instead of the guide vector D<6>A + delta A of the formula is solved by using a singular value decomposition method to obtain the guide vector after correcting the amplitude-phase error
The specific implementation of this step is as follows:
(6a) construction of M × (N +1) -dimensional extended matrix
Wherein
Complex vector signal with amplitude-phase error for Mx 1 dimension, and D is director after maintaining positive amplitude-phase error for Mx NAn amount;
(6b) calculating the singular value decomposition of the expansion matrix B:
B＝UΣV H ,
wherein Σ is M × MM × M dimensional diagonal matrix ═ i (diag (σ) 1 ,σ 2 ,…,σ M ) 0), 0 is an M × (N-M +1) -dimensional matrix, the elements of which are all 0; diag (sigma) 1 ,σ 2 ,…,σ M ) Is that the main diagonal element is sigma 1 ,σ 2 ,…,σ M M × M dimensional matrix of (V) H Represents the conjugate transpose of matrix V;
(6c) from the principal diagonal element σ 1 ,σ 2 ,…,σ M Search for a mutant element σ p When σ is p Satisfy sigma p ＞σ M +ξ≥σ p+1 ≥…≥σ M When xi is max [ (sigma) 1 -σ 2 ),(σ 2 -σ 3 ),…,(σ M-1 -σ M )]Constructing a (N +1) × (N +1) -dimensional correction matrix with the subscript P as an effective rank order: e ═ I p ,0] T ,I p Is a p multiplied by p dimensional identity matrix, 0 is a zero matrix;
(6d) adding the correction matrix E to the equation<7>Left-hand multiplication of the diagonal matrix sigma to obtain the optimal approximation matrix of the augmented matrix B
(6e) For the best approximation matrix
Carrying out the resolution of
The 2 nd column to the N +1 th column of the vector are used as guide vectors after correcting amplitude-phase errors
Is an M × N dimensional matrix.
And 7: will complex vector signal
As a measurement vector, a guide vector after correcting an amplitude-phase error
And as a sensing matrix, carrying out compressed sensing sparse reconstruction on the orientation information of a plurality of targets in the same range-Doppler unit by using a greedy iterative tracking algorithm to obtain the orientation information of the plurality of targets.
The specific implementation of this step is as follows:
(7a) will measure the vector
As an initial input, note e 0 ；
(7b) Slave sensing matrix
Screening with e 0 One column with the largest absolute value of inner product is shown as
(7c) Calculating residual value e according to the results of (7a) and (7b) 1 ：
Wherein
Denotes e 0 And
inner product of (d);
(7d) taking the residual value obtained by the calculation of (7c) as a new input of (7a), and repeatedly executing (7b) and (7c) for K times to obtain a perception matrix
Neutralization measurement vector
Most relevant K vectors
The range of K is less than or equal to 7, and the value of the example is 7;
(7e) when the vector is correlated
Is located in the sensing matrix
Column n in (d), the azimuth θ of the target is:
θ＝(n-N/2)*(θ N -θ 1 )/N，n∈1,2,…,N
where N is the total number of columns in the entire space, θ 1 To the starting position of the observation interval, θ N Is the cut-off orientation of the observation interval.
The effect of the invention can be further illustrated by the following simulation experiment:
1. the experimental conditions are as follows:
in the test of the invention, a frequency modulation broadcast signal FM is taken as a radiation source, the frequency is 93.1MHz, the bandwidth is 200kHz, the sampling rate is 200kHz, and the accumulation time is 1 s; the array antenna is composed of uniform linear arrays with the interval of half wavelength, the number of array elements is 15, and simultaneously the array antenna receives 2 target echo signals located in the same distance-Doppler unit. The performance of the method of the present invention is illustrated by two sets of simulation experiments, and the simulation parameters of the target are shown in table one.
Table-simulation parameters of a target
2. Simulation content and results
Simulation I, under the condition that the array has no amplitude-phase error, compressed sensing sparse reconstruction simulation is carried out on the azimuth information of two targets by using a traditional method and the method of the invention to obtain the azimuth of the two targets, and the result is shown in FIG. 3, wherein:
FIG. 3(a) is a diagram of azimuth information obtained using a conventional compressed sensing super-resolution DOA estimation method;
FIG. 3(b) is the orientation information obtained by the method of the present invention;
as can be seen from fig. 3, both the conventional method and the method of the present invention can effectively distinguish two targets, and the detected target orientation is [5 °,14 ° ], which is consistent with the assumed target orientation.
Simulation II, under the condition that the array has an amplitude-phase error of-30 dB, performing compressed sensing sparse reconstruction simulation on the azimuth information of the two targets by using a traditional method and the method of the invention to obtain the azimuths of the two targets, wherein the result is shown in figure 4, and the method comprises the following steps:
FIG. 4(a) is a diagram of azimuth information obtained by using a conventional compressed sensing super-resolution DOA estimation method when the array amplitude-phase error is-30 dB;
FIG. 4(b) is the azimuth information obtained by the method of the present invention when the array amplitude-phase error is-30 dB;
it can be seen from fig. 4 that when the amplitude-phase error of the array is-30 dB, the directions of the two targets detected by the method of the present invention are 5 ° and 14 °, respectively, which illustrates that the method can suppress the influence of the amplitude-phase error on the steering vector and effectively resolve the two targets, and the two targets are consistent with the assumed target direction when the amplitude-phase error exists in the array, whereas the detection by the conventional method can suppress a plurality of false direction information, and both of them are inconsistent with the assumed target direction information, and cannot effectively resolve the two targets.
The above description is only for the specific embodiments of the present invention, but the scope of the present invention is not limited thereto, and any person skilled in the art can easily conceive of the changes or substitutions within the technical scope of the present invention, and the changes or substitutions should be covered within the scope of the present invention. Therefore, the protection scope of the present invention shall be subject to the protection scope of the claims.
Claims (5)
1. A TLS-CS-based super-resolution DOA estimation method for an external radiation source radar is characterized by comprising the following steps:
(1) respectively acquiring echo signals S received by array antennas ech And a reference antenna for receiving the direct wave signal S in the radiation source direction ref ；
(2) Utilizing a reference antenna to receive a direct wave signal in the radiation source direction, and adopting an extended cancellation algorithm to suppress the direct wave and multipath interference in an echo signal to obtain an echo signal S after clutter suppression sur ；
(3) Echo signal S after clutter suppression sur Performing distance-Doppler two-dimensional correlation processing to obtain a complex vector signal S;
S＝A*S tar +Z <1>
S tar representing a target echo signal, A representing a steering vector corresponding to a target, and Z representing a noise signal;
(4) adding the complex vector signal S into the amplitude-phase disturbance parameter delta A to obtain a TLS signal model with amplitude-phase errors,
for complex vector signals with amplitude and phase errors:
(5) setting the number of rows of a guide vector of the whole observation space as the number M of array elements and the number of columns as the number N of division of the observation space, and constructing an MxN dimensional matrix as a guide vector D of an observation interval;
(6) taking the guide vector D of the whole observation interval as a guide vector with amplitude-phase disturbance instead of the guide vector D<2>A + delta A of the formula, and solving by using a singular value decomposition method<2>After obtaining the corrected amplitude-phase errorGuide vector of
(7) Will complex vector signal
As a measurement vector, a guide vector after correcting an amplitude-phase error
As a sensing matrix, compressed sensing sparse reconstruction is performed on the orientation information of a plurality of targets in the same range-Doppler unit by using a greedy iterative tracking algorithm to obtain the orientation information of the plurality of targets, and the implementation is as follows:
(7a) will measure the vector
As an initial input, note e 0 ；
(7b) From the perception matrix
Middle screening with e 0 One column with the largest absolute value of inner product is shown as
(7c) Calculating residual value e according to the results of (7a) and (7b) 1 ：
Wherein
Denotes e 0 And
inner product of (d);
(7d) taking the residual value obtained by the calculation of (7c) as a new input of (7a), and repeatedly executing (7b) and (7c) for K times to obtain a perception matrix
Neutralization measurement vector
Most relevant K vectors
(7e) When the vector is correlated
Is located in the sensing matrix
Column n in (d), the azimuth θ of the target is:
θ＝(n-N/2)*(θ N -θ 1 )/N，n∈1,2,…,N
where N is the total number of columns in the entire space, θ 1 To the starting position of the observation interval, θ N Is the cut-off orientation of the observation interval.
2. The method of claim 1, wherein the step (2) is implemented as follows:
(2a) using direct waves S ref And constructing a clutter orthogonal subspace V by time delay:
wherein G is the data length of the direct wave signal, C is the clutter cancellation order, the first column of the matrix represents the direct wave signal, the second column represents the multipath signal with the time delay unit of one, and the Nth column represents the multipath signal with the time delay unit of C;
(2b) echo signal S ech Projecting into a clutter orthogonal subspace V, solving the set of projection coefficients W which are not all zero on the subspace:
W＝(V H *V) -1 V H S ech ， <3>
wherein V H Represents a conjugate transpose of the matrix V; (V) H *V) -1 Expressing the inversion of the matrix product result;
(2c) according to the echo signal S ech Obtaining a clutter suppressed residual echo signal S by using a clutter orthogonal subspace V and a projection coefficient W which is not completely zero sur ：
S sur ＝S ech -V*W <4>。
3. The method of claim 1 wherein step (3) is practiced with respect to clutter suppressed echo signal S sur And (3) performing distance-Doppler two-dimensional correlation processing, which is realized as follows:
(3a) the residual echo signal S after clutter suppression sur With time-delayed conjugate reference signal S ref * [g-τ]Point multiplication to obtain complex vector signal S after distance dimension correlation processing m ：
Wherein τ represents the distance of the moving object, f d Representing the Doppler induced by relative motion between the moving object and the array antenna, G being the residual echo signal S sur Length of (d);
(3b) the complex vector signal S after the distance dimension correlation processing m After Doppler dimension correlation accumulation is carried out, a target signal S after Doppler dimension correlation accumulation is obtained tar ：
(3c) For the target signal S tar Adding a guide vector A and a noise Z to obtain a distance-Doppler two-dimensional correlation processing complex vector signal S:
S＝A*S tar +Z <7>。
4. the method of claim 1, wherein the observation space steering vector D in step (5),
is represented as follows:
wherein M is the number of array elements, N is the total column number of the whole space, and theta 1 To the starting position of the observation interval, θ N D is the distance between the antenna elements, and lambda is the wavelength of the emitted electromagnetic wave.
5. The method according to claim 1, characterized in that said step (6) is implemented as follows:
(6a) construction of M × (N +1) -dimensional extended matrix
Complex vector signals with amplitude-phase errors exist in MxN 1 dimensions, and D is a guide vector after the M xN maintenance of positive amplitude-phase errors;
(6b) calculating the singular value decomposition of the expansion matrix B:
B＝UΣV H ， <8>
wherein Σ is M × MM × M dimensional diagonal matrix ═ i (diag (σ) 1 ,σ 2 ,…,σ M ) 0), 0 is an M × (N-M +1) -dimensional matrix, the elements of which are all 0; diag (sigma) 1 ,σ 2 ,…,σ M ) Is that the main diagonal element is sigma 1 ,σ 2 ,…,σ M M × M dimensional matrix of (a); v H Conjugate transitions of the representation matrix VPlacing;
(6c) from the principal diagonal element σ 1 ,σ 2 ,…,σ M Search for a mutant element sigma p When σ is p Satisfy sigma p ＞σ M +ξ≥σ p+1 ≥…≥σ M When xi is max [ (sigma) 1 -σ 2 ),(σ 2 -σ 3 ),…,(σ M-1 -σ M )]Taking P as an effective rank order, constructing a (N +1) × (N +1) -dimensional correction matrix: e ═ I p ,0] T ,I p The matrix is a p multiplied by p dimension unit matrix, 0 is a zero matrix, and the elements of the zero matrix are 0;
(6d) adding the correction matrix E to the equation<8>Left-hand multiplication of the diagonal matrix sigma to obtain the optimal approximation matrix of the augmented matrix B
(6e) For the best approximation matrix
Carrying out the resolution of
As a guide vector after correcting the amplitude-phase error
Is an M × N dimensional matrix.
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