CN110380208B - Variable-thickness double-arc millimeter wave radome and design method - Google Patents
Variable-thickness double-arc millimeter wave radome and design method Download PDFInfo
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- CN110380208B CN110380208B CN201910593528.7A CN201910593528A CN110380208B CN 110380208 B CN110380208 B CN 110380208B CN 201910593528 A CN201910593528 A CN 201910593528A CN 110380208 B CN110380208 B CN 110380208B
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/27—Adaptation for use in or on movable bodies
- H01Q1/32—Adaptation for use in or on road or rail vehicles
- H01Q1/3208—Adaptation for use in or on road or rail vehicles characterised by the application wherein the antenna is used
- H01Q1/3233—Adaptation for use in or on road or rail vehicles characterised by the application wherein the antenna is used particular used as part of a sensor or in a security system, e.g. for automotive radar, navigation systems
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/42—Housings not intimately mechanically associated with radiating elements, e.g. radome
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Abstract
The invention relates to a design method of a variable-thickness double-arc millimeter wave radar antenna housing, which comprises the following steps of: (1) establishing an appearance curved surface equation of the radome; (2) establishing a ray equation of the antenna; (3) solving the coordinates of the intersection point of the antenna ray and the curved surface of the radome; (4) calculating an incident angle formed by an antenna ray and a radar curved surface incident surface; (5) calculating a polarization angle formed by an antenna ray and a radar cover surface; (6) calculating the electrical parameters of the projection of the antenna rays onto the shield wall; (7) and obtaining the wall thickness of the antenna housing through optimization iteration according to the obtained electrical parameters. The invention also provides a variable-thickness double-arc millimeter wave radome, wherein the cover surface of the radome is provided with a first arc-shaped structure and a second arc-shaped structure. The antenna cover can improve the electrical performance index of the antenna cover, so that the problem that the radar antenna is passive and has a depression with an active directional diagram at a large angle after the planar antenna cover is loaded is solved.
Description
Technical Field
The invention relates to the technical field of radar antennas, in particular to a variable-thickness double-arc millimeter wave radar antenna housing and a design method.
Background
As one of important sensors of Advanced Driving Assistance System (ADAS), the vehicle-mounted millimeter-wave radar has become an indispensable part of the ADAS system, and with the continuous development of the automatic driving technology, the millimeter-wave radar will have great market demand. In the development of vehicle-mounted radar products, the development design of the radome is an important part of the radome, the detection sensing performance of radar waves is influenced, and an important protection effect is also played on the core component radar antenna. The design goal is primarily to have little or no effect on the radar's view angle (FOV) range.
At present, the research on the forward radar of the automobile tends to be mature, and the research on the vehicle-mounted millimeter-wave angle radar is just started. The vehicle-mounted millimeter wave angle radar not only needs to take account of the antenna gain, but also needs to have a large-angle detection range (140-150 degrees). The antenna has high requirement on the beam width of the antenna, and the development and design difficulty of the antenna is greatly increased after the influence of the antenna housing on the performance of the antenna is considered. The vehicle-mounted millimeter wave angle radar plays a vital role in the application of scenes such as blind spot monitoring (BSD), Lane Change Assistance (LCA), Parking Assistance (PA), Cross Traffic Alarm (CTA) and the like. At present, due to the limitation of the PCB processing technology, most manufacturers still adopt microstrip array antennas. The vehicle-mounted millimeter wave radar is mostly a radar product or a plane antenna housing, and the radar product is mostly a medium-distance radar. When the simple plane cover is applied to an angle radar, a radar antenna directional diagram can be sunken at a large angle, and the performance requirement is difficult to meet. Therefore, how to improve the antenna housing and further improve the detection performance of the millimeter wave angle radar is still an important technical difficulty in the design of the present millimeter wave radar.
Disclosure of Invention
The invention aims to provide a variable-thickness double-arc millimeter wave radome and a design method, which can improve the electrical performance index of the radome, thereby solving the problems that a radar antenna is passive and has a depression with an active directional diagram at a large angle after a planar radome is loaded.
A design method of a variable-thickness double-arc millimeter wave radome comprises the following steps:
(1) the method comprises the following steps of establishing a coordinate system by taking the center of the bottom surface of the antenna housing as an original point, defining the bottom surface as an xy plane, and establishing an appearance curved surface equation of the antenna housing by taking the height direction of the antenna housing as a z direction:
wherein a, b, c, d and f are shape parameters of the antenna housing, and x, y and z are directions of a coordinate system respectively;
(2) defining the ray emitted by the antenna to be vertical to the antenna aperture surface, obtaining the direction vector (l, m, n) of the antenna ray in the coordinate system of the radome, defining that the radar has one point P (xp, yp, zp), and obtaining the ray equation of the ray emitted by any point on the antenna aperture surface as follows:
(3) jointly solving according to the outline curved surface equation and the ray equation in the step (1) and the step (2), obtaining real number solutions in the obtained multiple groups of solutions, and obtaining intersection point coordinates (xr, yr and zr) of the antenna rays and the radome curved surface;
(4) according to the intersection point coordinates (xr, yr, zr), a direction vector of the radome curved surface is defined as (u, v, w), and an incident angle θ i between an antenna ray and an incident plane of the radome curved surface is obtained as:
(5) defining the plane determined by the normal line at the intersection point of the antenna ray and the antenna cover surface as an incident plane, and defining the included angle between the electric field vector and the incident plane as the polarization angle of the electric wave, wherein the polarization angle xi formed by the antenna ray and the antenna cover surface is as follows:
wherein, the direction vector of the incident normal is (S1, S2, S3), and the antenna electric field vector is (E1, E2, E3);
(6) assuming that the radar is composed of multiple layers of media, the transmission matrix of the radar can be obtained according to the microwave transmission theory as follows:
wherein [ An]Is a transmission matrix of a multi-layer model, and
、
、
...
respectively is a transmission matrix of each layer of medium; for the Nth layer medium, the transmission matrix is as follows:
wherein:
；
combining a multilayer medium flat plate cascade matrix transmission calculation formula to obtain electrical parameters of the antenna ray projected on the antenna shield wall, wherein the electrical parameters comprise impedance Zcn, voltage transmission coefficient T, voltage reflection coefficient R and insertion phase delay IPD;
(7) and obtaining the wall thickness distribution of the antenna housing through optimization iteration according to the obtained electrical parameters of the antenna housing wall.
Further, the specific implementation steps of the step (6) are as follows:
(6a) the impedance Zcn is calculated as follows:
wherein, is
The incident angle of the electromagnetic wave is,
for the wavelength of the operating frequency of the radar,
is the thickness of the n-th layer of medium,
is the relative dielectric constant of the nth layer of dielectric,
is the loss tangent of the nth layer dielectric;
(6b) when n =0, epsilon o =1, Zco is expressed as a free-space normalized impedance, the voltage transmission coefficient T of the antenna ray through the antenna shield wall can be obtained according to the theory of the microwave transmission network:
wherein the content of the first and second substances,
，
；
(6c) the voltage reflection factor R of the antenna radiation incident on the shield wall is determined as follows:
(6d) the insertion phase delay IPD of the antenna radiation through the radome wall at this time is:
furthermore, the shape parameter is obtained by performing inverse extrapolation according to the voltage transmission coefficient T, the voltage reflection coefficient R and the specific requirements of the insertion phase delay IPD when the electromagnetic wave is incident to the radome wall at different incidence angles and according to the calculation formulas of the voltage transmission coefficient T, the voltage reflection coefficient R and the insertion phase delay IPD.
Further, the specific implementation steps of the optimization iteration of step (7) are as follows:
(7a) taking a voltage transmission coefficient T, a voltage reflection coefficient R and an insertion phase delay IPD of the antenna housing as output results;
(7b) taking the shape parameters as input parameters, and calculating the voltage transmission coefficient, the voltage reflection coefficient and the insertion phase delay of the antenna housing according to the input of the shape parameters each time by using a simulation algorithm;
(7c) if at least one of the voltage transmission coefficient, the voltage reflection coefficient and the insertion phase delay does not meet the requirement, repeating the step (7 a) and the step (7 b); if the voltage transmission coefficient, the voltage reflection coefficient and the insertion phase delay all meet the requirements, iteration is completed.
The utility model provides a two arc millimeter wave radar antenna cover of thickness, the thickness of antenna house is through design as above-mentioned design method, the antenna house includes the top facing and locates the peripheral cover wall of top facing, the top facing is equipped with adjacent first arc structure and second arc structure, the internal surface and the surface of first arc structure and second arc structure all are the arc.
Furthermore, a groove is formed between the outer surfaces of the first arc-shaped structure and the second arc-shaped structure.
Further, an isolation bulge is formed between the inner surfaces of the first arc-shaped structure and the second arc-shaped structure, and the isolation bulge vertically extends downwards along the inner surface of the cover surface.
Furthermore, the cross section of the isolation bulge is rectangular or inverted trapezoid.
Compared with the prior art, the invention has the following beneficial effects: 1. by utilizing the double-arc-shaped antenna housing, the transmitting part and the receiving part are separately processed when the antenna housing is designed, so that the design difficulty is greatly reduced. 2. There is trapezoidal isolation arch at antenna house main part intermediate wall, can make the antenna house be symmetrical structure for the structure of antenna, further reduced the degree of difficulty of the design of antenna house. 3. The antenna cover is designed into a double-arc shape, so that the included angle between the antenna radiation and the antenna cover tangent plane tends to be consistent, the loss of electromagnetic waves incident to the antenna cover tangent plane at a large angle is effectively reduced, and the transmission amount of the electromagnetic waves in the antenna cover when the angle is increased can be further increased. 4. The design method of the antenna housing is scientific and reasonable, the design difficulty of the antenna housing is reduced, and the electrical performance index of the antenna housing is improved. 5. The thickness of the antenna housing is changed along with the actual distribution of the antenna, so that the wave path of the electromagnetic wave passing through the antenna housing tends to be consistent when the electromagnetic wave enters the antenna housing at a large angle. In conclusion, the invention can reduce the design difficulty, improve the design efficiency and enable the radar to meet the requirements of speed measurement and angle measurement in different environments and scenes.
Drawings
Fig. 1 is a flowchart of a design method of a variable-thickness double-arc millimeter wave radome of the present invention.
Fig. 2 is a flowchart of an optimization iteration process of the design method of the variable-thickness double-arc millimeter wave radome of the present invention.
Fig. 3 is a schematic structural diagram of the variable-thickness double-arc millimeter wave radome of the present invention.
Fig. 4 is a schematic cross-sectional structure view of the variable-thickness double-arc millimeter wave radome of the present invention.
Fig. 5 is a schematic view of an antenna structure used in an embodiment of the variable-thickness double-arc millimeter wave radar radome of the present invention.
Fig. 6 is a graph comparing the reflection coefficients of the antenna TX1 before loading the variable-thickness double-arc millimeter wave radome and after loading the variable-thickness double-arc millimeter wave radome.
Fig. 7 is a graph comparing the reflection coefficients of the antenna TX2 before loading the variable-thickness double-arc millimeter wave radome and after loading the variable-thickness double-arc millimeter wave radome.
Fig. 8 is a graph comparing the reflection coefficients of the antenna RX1 before loading the variable-thickness double-arc-shaped millimeter wave radome and after loading the variable-thickness double-arc-shaped millimeter wave radome.
Fig. 9 is a graph comparing the reflection coefficients of the antenna RX2 before loading the variable-thickness double-arc millimeter wave radome and after loading the variable-thickness double-arc millimeter wave radome.
Fig. 10 is a graph comparing the reflection coefficients of the antenna RX3 before loading the variable-thickness double-arc millimeter wave radome and after loading the variable-thickness double-arc millimeter wave radome.
Fig. 11 is a graph comparing the reflection coefficients of the antenna RX4 before loading the variable-thickness double-arc millimeter wave radome and after loading the variable-thickness double-arc millimeter wave radome.
Fig. 12 is a comparison graph of H-plane patterns of the antenna TX1 before loading the variable-thickness double-arc millimeter wave radome and after loading the variable-thickness double-arc millimeter wave radome.
Fig. 13 is a comparison graph of H-plane patterns of the antenna TX2 before loading the variable-thickness double-arc millimeter wave radome and after loading the variable-thickness double-arc millimeter wave radome.
Fig. 14 is a graph comparing H-plane patterns of antenna RX1 before loading the variable thickness dual-arc millimeter wave radome and after loading the variable thickness dual-arc millimeter wave radome.
Fig. 15 is a graph comparing H-plane patterns of antenna RX2 before loading the variable thickness dual-arc millimeter wave radome and after loading the variable thickness dual-arc millimeter wave radome.
Fig. 16 is a comparison graph of H-plane patterns of the antenna RX3 before loading the variable-thickness double-arc millimeter wave radome and after loading the variable-thickness double-arc millimeter wave radome.
Fig. 17 is a comparison graph of H-plane patterns of antenna RX4 before loading the variable-thickness double-arc millimeter wave radome and after loading the variable-thickness double-arc millimeter wave radome.
Fig. 18 is a graph comparing H-plane patterns of another frequency before the variable thickness double arc millimeter wave radome is loaded on the antenna RX4 and after the variable thickness double arc millimeter wave radome is loaded on the antenna RX 4.
Detailed Description
The present invention will be described in further detail below with reference to specific embodiments and the attached drawings.
As shown in fig. 1 and 2, the method for designing a variable-thickness double-arc millimeter wave radome of the present invention includes the following steps:
(1) the method comprises the following steps of establishing a coordinate system by taking the center of the bottom surface of the antenna housing as an original point, defining the bottom surface as an xy plane, and establishing an appearance curved surface equation of the antenna housing by taking the height direction of the antenna housing as a z direction:
wherein a, b, c, d and f are shape parameters related to the antenna housing, and x, y and z are directions of a coordinate system respectively;
(2) defining the ray emitted by the antenna to be vertical to the antenna aperture surface, obtaining the direction vector (l, m, n) of the antenna ray in the coordinate system of the radome, defining that the radar has one point P (xp, yp, zp), and obtaining the ray equation of the ray emitted by any point on the antenna aperture surface as follows:
(3) jointly solving according to the outline curved surface equation and the ray equation in the step (1) and the step (2), obtaining real number solutions in the obtained multiple groups of solutions, and obtaining intersection point coordinates (xr, yr and zr) of the antenna rays and the radome curved surface;
(4) according to the intersection point coordinates (xr, yr, zr), a direction vector of the radome curved surface is defined as (u, v, w), and an incident angle θ i between an antenna ray and an incident plane of the radome curved surface is obtained as:
(6) defining the plane determined by the normal line at the intersection point of the antenna ray and the antenna cover surface as an incident plane, and defining the included angle between the electric field vector and the incident plane as the polarization angle of the electric wave, wherein the polarization angle xi formed by the antenna ray and the antenna cover surface is as follows:
wherein, the direction vector of the incident normal is (S1, S2, S3), and the antenna electric field vector is (E1, E2, E3);
(6) assuming that the radar is composed of multiple layers of media, the transmission matrix of the radar can be obtained according to the microwave transmission theory as follows:
wherein [ An]Is a transmission matrix of a multi-layer model,
、
、
...
respectively is a transmission matrix of each layer of medium; for the Nth layer medium, the transmission matrix is as follows:
wherein:
；
combining a multilayer medium flat plate cascade matrix transmission calculation formula to obtain electrical parameters of the antenna ray projected on the antenna shield wall, wherein the electrical parameters comprise impedance Zcn, voltage transmission coefficient T, voltage reflection coefficient R and insertion phase delay IPD;
(7) and obtaining the wall thickness distribution of the antenna housing through optimization iteration according to the obtained electrical parameters of the antenna housing wall.
The concrete implementation steps of the step (6) are as follows:
(6a) the impedance Zcn is calculated as follows:
wherein, is
The incident angle of the electromagnetic wave is,
for the wavelength of the operating frequency of the radar,
is the thickness of the n-th layer of medium,
is the relative dielectric constant of the nth layer of dielectric,
is the loss tangent of the nth layer dielectric;
(6b) when n =0, epsilon o =1, Zco is expressed as a free-space normalized impedance, the voltage transmission coefficient T of the antenna ray through the antenna shield wall can be obtained according to the theory of the microwave transmission network:
wherein the content of the first and second substances,
，
；
(6c) the voltage reflection factor R of the antenna radiation incident on the shield wall is determined as follows:
(6d) the insertion phase delay IPD of the antenna radiation through the radome wall at this time is:
furthermore, the shape parameter is obtained by performing inverse extrapolation according to the voltage transmission coefficient T, the voltage reflection coefficient R and the specific requirements of the insertion phase delay IPD when the electromagnetic wave is incident to the radome wall at different incidence angles and according to the calculation formulas of the voltage transmission coefficient T, the voltage reflection coefficient R and the insertion phase delay IPD.
Referring to fig. 2, the specific implementation steps of the optimization iteration of step (7) are:
(7a) taking a voltage transmission coefficient T, a voltage reflection coefficient R and an insertion phase delay IPD of the antenna housing as output results;
(7b) taking the shape parameters as input parameters, and calculating the voltage transmission coefficient, the voltage reflection coefficient and the insertion phase delay of the antenna housing according to the input of the shape parameters each time by using a simulation algorithm;
(7c) if at least one of the voltage transmission coefficient, the voltage reflection coefficient and the insertion phase delay does not meet the requirement, repeating the step (7 a) and the step (7 b); if the voltage transmission coefficient, the voltage reflection coefficient and the insertion phase delay all meet the requirements, iteration is completed.
As shown in fig. 3 and 4, the invention provides a variable-thickness double-arc millimeter wave radome, the thickness of the radome is designed by the above design method, the radome comprises a cover surface 1 and a cover wall 2 arranged on the periphery of the cover surface 1, and the cover surface 1 is provided with a first arc-shaped structure 11 and a second arc-shaped structure 12 which are adjacent to each other. The surface of the cover surface 1 in the cover wall 2 is defined as an inner surface, the surface on the other side of the inner surface is defined as an outer surface, and the inner surface and the outer surface of the first arc-shaped structure 11 and the second arc-shaped structure 12 are both arc-shaped.
Wherein a groove 13 is formed between the outer surfaces of the first arc-shaped structure 11 and the second arc-shaped structure 12. An isolating projection 14 is formed between the inner surfaces of the first arc-shaped structure 11 and the second arc-shaped structure 12, and the isolating projection 14 vertically extends downwards along the inner surface of the cover surface 1. In this embodiment, the cross section of the isolation protrusion 14 is rectangular, and in other embodiments, the cross section of the isolation protrusion 14 is inverted trapezoid or other shapes. By providing the groove 13 and the isolation protrusion 14, isolation can be formed between the first arc-shaped structure 11 and the second arc-shaped structure 12, and the first arc-shaped structure and the second arc-shaped structure are prevented from influencing each other.
Referring to fig. 5, in an embodiment, the antennas include a transmitting antenna 3 and a receiving antenna 4, the transmitting antenna 3 includes an antenna TX1 and an antenna TX2, and the receiving antenna 4 includes an antenna RX1, an antenna RX2, an antenna RX3, and an antenna RX 4.
Fig. 6 to 11 are graphs for comparing reflection coefficients of the transmitting antenna 3 and the receiving antenna 4 before loading the variable-thickness double-arc millimeter wave radome and after loading the variable-thickness double-arc millimeter wave radome in this embodiment, respectively. It can be known from the figure that the working frequency of the antenna and the working bandwidth of the antenna are not affected by the variable-thickness double-arc millimeter wave radome in the embodiment.
Fig. 12 to 17 are graphs comparing H-plane patterns of the transmitting antenna 3 and the receiving antenna 4 in this embodiment before the variable-thickness double-arc millimeter wave radome is loaded and after the variable-thickness double-arc millimeter wave radome is loaded. It can be known from the figure that the antenna H-plane directional pattern loaded with the radome is closer to the radar direction without the radome. Compared with a planar radome, the problem that an H directional diagram is sunken at a large angle is obviously improved after the variable-thickness double-arc-shaped millimeter wave radome is loaded, and the large-angle detection requirement can be well met.
Fig. 18 is a graph comparing H-plane patterns of another frequency before the variable thickness double arc millimeter wave radome is loaded on the antenna RX4 and after the variable thickness double arc millimeter wave radome is loaded on the antenna RX 4. It can be known that the antenna radiation characteristics of the loaded variable-thickness double-arc radome are consistent in the working bandwidth range (76-77 GHz).
In summary, in this embodiment, the variable-thickness double-arc millimeter wave radome does not affect the operating frequency and the operating bandwidth of the radar antenna, and improves the radiation performance of the radar antenna to a certain extent.
While the invention has been described in conjunction with the specific embodiments set forth above, it is evident that many alternatives, modifications, and variations will be apparent to those skilled in the art in light of the foregoing description. Accordingly, it is intended to embrace all such alternatives, modifications, and variations that fall within the spirit and scope of the appended claims.
Claims (5)
1. A design method of a variable-thickness double-arc millimeter wave radome is characterized by comprising the following steps of:
(1) the method comprises the following steps of establishing a coordinate system by taking the center of the bottom surface of the antenna housing as an original point, defining the bottom surface as an xy plane, and establishing an appearance curved surface equation of the antenna housing by taking the height direction of the antenna housing as a z direction:
wherein a, b, c, d and f are shape parameters of the antenna housing, and x, y and z are directions of a coordinate system respectively; the shape parameters are obtained by back-stepping according to the voltage transmission coefficient T, the voltage reflection coefficient R and the specific requirements of inserting the phase delay IPD when the electromagnetic waves enter the antenna housing wall at different incidence angles and according to the calculation formulas of the voltage transmission coefficient T, the voltage reflection coefficient R and the inserting phase delay IPD;
(2) defining the ray emitted by the antenna to be vertical to the antenna aperture surface, obtaining the direction vector (l, m, n) of the antenna ray in the coordinate system of the radome, defining that the radar has one point P (xp, yp, zp), and obtaining the ray equation of the ray emitted by any point on the antenna aperture surface as follows:
(3) jointly solving according to the outline curved surface equation and the ray equation in the step (1) and the step (2), obtaining real number solutions in the obtained multiple groups of solutions, and obtaining intersection point coordinates (xr, yr and zr) of the antenna rays and the radome curved surface;
(4) according to the intersection point coordinates (xr, yr, zr), a direction vector of the radome curved surface is defined as (u, v, w), and an incident angle θ i between an antenna ray and an incident plane of the radome curved surface is obtained as:
(5) defining the plane determined by the normal line at the intersection point of the antenna ray and the antenna cover surface as an incident plane, and defining the included angle between the electric field vector and the incident plane as the polarization angle of the electric wave, wherein the polarization angle xi formed by the antenna ray and the antenna cover surface is as follows:
wherein, the direction vector of the incident normal is (S1, S2, S3), and the antenna electric field vector is (E1, E2, E3);
(6) assuming that the radar is composed of multiple layers of media, the transmission matrix of the radar can be obtained according to the microwave transmission theory as follows:
wherein [ An]Is a transmission matrix of a multi-layer model, and
、
、
...
are respectively eachA transmission matrix of a layer of medium; for the Nth layer medium, the transmission matrix is as follows:
wherein:
；
the impedance Zcn, the voltage transmission coefficient T, the voltage reflection coefficient R, and the insertion phase delay IPD are obtained by:
(6a) the impedance Zcn is calculated as follows:
wherein, is
The incident angle of the electromagnetic wave is,
for the wavelength of the operating frequency of the radar,
is the thickness of the n-th layer of medium,
is the relative dielectric constant of the nth layer of dielectric,
is the loss tangent of the nth layer dielectric;
(6b) when n =0, epsilon o =1, Zco is expressed as a free-space normalized impedance, the voltage transmission coefficient T of the antenna ray through the antenna shield wall can be obtained according to the theory of the microwave transmission network:
wherein the content of the first and second substances,
，
；
(6c) the voltage reflection factor R of the antenna radiation incident on the shield wall is determined as follows:
(6d) the insertion phase delay IPD of the antenna radiation through the radome wall at this time is:
(7) according to the obtained electrical parameters of the radome wall, obtaining the radome wall thickness distribution through optimization iteration, wherein the optimization iteration specifically comprises the following steps:
(7a) taking a voltage transmission coefficient T, a voltage reflection coefficient R and an insertion phase delay IPD of the antenna housing as output results;
(7b) taking the shape parameters as input parameters, and calculating the voltage transmission coefficient, the voltage reflection coefficient and the insertion phase delay of the antenna housing according to the input of the shape parameters each time by using a simulation algorithm;
(7c) if at least one of the voltage transmission coefficient, the voltage reflection coefficient and the insertion phase delay does not meet the requirement, repeating the step (7 a) and the step (7 b); if the voltage transmission coefficient, the voltage reflection coefficient and the insertion phase delay all meet the requirements, iteration is completed.
2. The utility model provides a two arc millimeter wave radar antenna cover of thickness, its characterized in that, the thickness of antenna house is through the design method design of claim 1, the antenna house includes the top facing and locates the peripheral cover wall of top facing, the top facing is equipped with adjacent first arc structure and second arc structure, the internal surface and the surface of first arc structure and second arc structure all are the arc.
3. The variable thickness double arc millimeter wave radome of claim 2, wherein a groove is formed between the outer surfaces of the first arc structure and the second arc structure.
4. An arcuate millimeter wave radome according to claim 3 wherein an isolation boss is formed between the inner surfaces of the first and second arcuate structures, the isolation boss extending vertically downwardly along the inner surface of the cover.
5. The curved millimeter wave radome of claim 4, wherein the cross section of the isolation protrusion is rectangular or inverted trapezoidal.
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