CN110247643A - A kind of maximum pulse width protection of transmitter and maximum duty cycle protect analog circuit - Google Patents
A kind of maximum pulse width protection of transmitter and maximum duty cycle protect analog circuit Download PDFInfo
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- CN110247643A CN110247643A CN201910529304.XA CN201910529304A CN110247643A CN 110247643 A CN110247643 A CN 110247643A CN 201910529304 A CN201910529304 A CN 201910529304A CN 110247643 A CN110247643 A CN 110247643A
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- voltage
- transmitter
- constant
- pulse width
- protection
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
- H03F3/24—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers of transmitter output stages
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K3/00—Circuits for generating electric pulses; Monostable, bistable or multistable circuits
- H03K3/01—Details
- H03K3/017—Adjustment of width or dutycycle of pulses
Abstract
The present invention relates to the control protection technique field of transmitter, the maximum pulse width protection for disclosing a kind of transmitter protects analog circuit with maximum duty cycle.Including constant-current source, charging capacitor, comparator, the second diode, the constant-current source includes constant current signal positively and negatively to charging capacitor constant-current charge or constant-current discharge, charging capacitor one end ground connection, the charging capacitor other end is connected to the positive input of comparator, the negative input of the comparator connects reference voltage, connects the second diode between the output end and positive input of the comparator.Above scheme is using the current source of switching to capacitor charge and discharge; the switching of constant-current source simultaneously can be the switching for being followed by the generating positive and negative voltage or two positive voltages of deleting control signal switching; it realizes that bearing energy to transmitter measures, realized pulsewidth protection or energy accumulation protection；Secondly compared with the prior art the present invention, is reduced costs by simple analog circuit, reduces volume, improve reliability.
Description
Technical field
The present invention relates to the control protection technique field of transmitter, the maximum pulse width protection of especially a kind of transmitter and most
Big space rate protects analog circuit.
Background technique
Transmitter is that radio frequency low-power level signal is converted to powerful equipment, and vacuum transmitting can be divided into from physics realization
Machine and solid state transmitter.The core amplifier part of vacuum transmitter uses electron tube, usually travelling-wave tubes；Solid state transmitter
Core amplifier part using semiconductor devices.Continuous wave transmitter and pulse can be divided into from signal output characteristic emission machine
Type transmitter.Continuous wave transmitter can continuously export firm power, and impulse type transmitter is only capable of according to certain frequency and accounts for
Sky is then likely to result in transmitter more than the maximum value allowed than output pulse power, output pulse width or duty ratio and damages
It is bad.This is mainly due to can generate a large amount of heat when transmitter pulse work, impulse type transmitter is in order to reach lesser
High pulse power output is realized under volume, heat-sinking capability is designed according to average heat consumption.Therefore when working pulse has exceeded
Design value causes heat that cannot dissipate in time, and thermal accumlation causes device to overheat, and amplifier is caused to fail, and it is therefore necessary to right
The maximum duty cycle and maximum pulse width of transmitter are protected, to improve the reliability of transmitter applies.
Transmitter generallys use grid control and realizes pulse output, and grid-controlled pulsewidth is the pulsewidth of microwave output.
Currently used the used digital circuit of protected mode (usually CPLD, FPGA or DSP) measures pulse with the method for counting
The width of signal and period calculate duty ratio, then practical pulsewidth and duty ratio are compared with setting value, judge whether arteries and veins
Width crosses duty ratio, and then makes corresponding protection act.
Digital circuit not only designs complexity, needs using high speed device software and hardware while cooperating, at high cost, and number electricity
The problems such as there are single-particle inversion and latches in spaceborne equal application on road, and use analog circuit by it is safer, smaller, more hold
Easy to maintain, cost is also lower.
Summary of the invention
The technical problems to be solved by the present invention are: in view of the above problems, providing a kind of maximum of transmitter
Pulsewidth protection and maximum duty cycle protect analog circuit.
The technical solution adopted by the invention is as follows: the maximum pulse width protection and maximum duty cycle protection simulation of a kind of transmitter
Circuit, comprising: constant-current source, charging capacitor, comparator, the second diode, the constant-current source include constant current letter positively and negatively
Number charging capacitor constant-current charge or constant-current discharge are given, described charging capacitor one end ground connection, the charging capacitor other end, which is connected to, to be compared
The negative input of the positive input of device, the comparator connects reference voltage, and the output end and forward direction of the comparator are defeated
Enter and connects the second diode between end.
Further, the maximum pulse width protection of the transmitter and maximum duty cycle protection analog circuit further include the one or two
Pole pipe, charging capacitor first diode in parallel.
Further, the grid control signal synchronism switching of the constant-current source and transmitter, obtains perseverance positively and negatively
Flow signal.
Further, constant-current charge is carried out using to charging capacitor within the period that grid control signal is opened, in grid
Control signal is to carry out constant-current discharge to charging capacitor in the period closed.
Further, the maximum pulse width protection of the transmitter and maximum duty cycle protection analog circuit further include current source
Waveform generating circuit, the current source waveform generation circuit include operational amplifier, first resistor, voltage source reference voltage, institute
The output end for stating operational amplifier is separately connected the positive input and charging capacitor of comparator, and the first resistor is for detecting
The electric current of charging capacitor obtains detection voltage, will test voltage and voltage source reference voltage is separately input to operational amplifier
Negative input and positive input, the operational amplifier is for generating constant-current source.
Further, it is grounded after the charging capacitor connection first resistor, between the charging capacitor and first resistor
Node is connected to the negative input of operational amplifier, the positive input connection voltage source reference electricity of the operational amplifier
Pressure.
Further, the maximum pulse width protection of the transmitter and maximum duty cycle protection analog circuit further include the first base
It is inputted after the detection voltage superposition of quasi- positive voltage, voltage source reference voltage generation circuit, the benchmark positive voltage and first resistor
Output signal to the negative input of operational amplifier, the voltage source reference voltage generation circuit is supplied to operational amplifier
Positive input, the voltage source reference voltage of voltage source reference voltage generation circuit output includes two positive electricity of switching
Pressure.
Further, the voltage source reference voltage generation circuit includes the second benchmark positive voltage, direct impulse voltage, three
Pole pipe, the 5th resistance, the 6th resistance, the 7th resistance, the 8th resistance, the 9th resistance, the second capacitor, the triode pass through outside
Digital logic signal control turn-on and turn-off, the base stage of the triode is connect by the 8th resistance with direct impulse voltage,
The collector of the triode connects the second benchmark positive voltage, the emitter and collector of the triode after connecting the 5th resistance
Between the 6th resistance is set, the emitter of the triode is grounded after connecting the 7th resistance, second electricity of the 7th resistor coupled in parallel
Hold, the emitter of the triode is connected to the positive input of operational amplifier, triode ON and pass by the 9th resistance
Two different voltage source reference voltages are provided in disconnected process respectively to the positive input of operational amplifier.
Compared with prior art, the electricity for having the beneficial effect that above scheme and utilization being utilized to switch by adopting the above technical scheme
Stream source is to capacitor charge and discharge, while the switching of constant-current source can be and be followed by the generating positive and negative voltage for deleting control signal switching or two
The switching of positive voltage realizes that bearing energy to transmitter measures, realized pulsewidth protection or energy accumulation protection；This hair
It is bright compared with the prior art, reduced costs by simple analog circuit, reduce volume, improve reliability.
Detailed description of the invention
Fig. 1 is the maximum pulse width protection of transmitter of the present invention and the structure of maximum duty cycle protection analog circuit embodiment 1
Schematic diagram.
Fig. 2 is that the maximum pulse width of embodiment 1 protects waveform diagram.
Fig. 3 is that the maximum duty cycle of embodiment 1 protects (energy accumulation protection) waveform diagram.
Fig. 4 is the maximum pulse width protection of transmitter of the present invention and the structure of maximum duty cycle protection analog circuit embodiment 2
Schematic diagram.
Fig. 5 is the simulation waveform schematic diagram of embodiment 2.
Fig. 6 is that the maximum pulse width of embodiment 2 protects waveform diagram.
Fig. 7 is that the maximum duty cycle of embodiment 2 protects (energy accumulation protection) waveform diagram.
Fig. 8 is the maximum pulse width protection of transmitter of the present invention and the structure of maximum duty cycle protection analog circuit embodiment 3
Schematic diagram.
Fig. 9 is that the maximum pulse width of embodiment 3 protects waveform diagram.
Waveform diagram when Figure 10 is the capacitor charge and discharge equilibrium of embodiment 3.
Figure 11 is that the maximum duty cycle of embodiment 3 protects (energy accumulation protection) waveform diagram.
Specific embodiment
The present invention is described further with reference to the accompanying drawing.
Embodiment 1
A kind of maximum pulse width protection of transmitter and maximum duty cycle protect analog circuit, comprising: constant-current source Ipulse, fill
Capacitor C, comparator, the second diode D2, the constant-current source Ipulse include that constant current signal positively and negatively gives charging electricity
Hold constant-current charge or constant-current discharge, here by the grid control signal synchronism switching of the transmitter of constant-current source Ipulse, Ke Yishi
The switching of existing constant-current charge or constant-current discharge process, exports electric current I when grid are openedi, electric current I is sucked when grid closeO。
(1) protection of maximum pulse width wave is realized
Charging capacitor C opens t in gridonPeriod in use constant-current source with electric current IiTo charging, close toff's in grid
To charging capacitor C with electric current I in periodOCarry out constant-current discharge.Assuming that capacitor C initial voltage is 0, then:
Wherein, the variable quantity of Δ U capacitance voltage, Δ T are charge/discharge time.
The increment of capacitance voltage when then grid are opened are as follows:
The decrement of capacitance voltage when grid close are as follows:
Due to t in practical applicationonOften real-time change, when the capacitance voltage increment in some period has reached benchmark electricity
Vref is pressed, then comparator is overturn, and the high level that comparator once overturns output feeds back the forward direction to comparator by diode D2
Input terminal, so that comparator output is locked in high level, then it is at this time the maximum pulse width t that impulse type amplifier allowsonmax。
Transmitter pulse type in application, usually duty it is relatively low, design discharge current IOAllowing maximum pulse width tonmax's
In the case of just each period the voltage of capacitor can be put into 0, i.e., have at this time:
ΔUon=Δ Uoff
Wherein T is the pulse period.
I.e. discharge current meets following formula:
Corresponding protection circuit waveform is as shown in Fig. 2, right comparator output voltage Vout, reference voltage Vref and electricity
Hold the current source waveform that voltage and constant-current source provide.
Why give capacitor charge/discharge using constant-current source, be because voltage on such capacitor can with the charge/discharge time at
Direct ratio.
(2) energy accumulation is protected
The voltage of capacitor and the working time of TWT are directly proportional, if the single pulse time has been more than TWT maximum pulse width limit
System, then capacitance voltage trigger comparator overturning are protected, if signal period does not reach maximum pulse width limitation, capacitance voltage
Multicycle accumulation is carried out, maximum duty cycle dmax determines the ratio of capacitance charging current and discharge current.Accounted in TWT maximum
Sky than when capacitor charge and discharge balance, i.e., at this time " increment=decrement ":
Then
IidmaxT=Io(1-dmax)T
The then ratio of charge and discharge electric current are as follows:
When " decrement >=increment " in signal period (that is: duty ratio≤maximum duty cycle dmax), then each period capacitor
On voltage can return to 0 initial voltage (since the diode of capacitor parallel connection exists, capacitor will not be charged to negative voltage),
And when increment > decrement, the voltage of capacitor each period will not be put into 0, residual voltage be had, if subsequent each period has
Remaining then capacitance voltage meeting Cycle by Cycle accumulation, until capacitance voltage reaches reference voltage Vref, comparator overturning protection.Such as Fig. 3
It is shown.
Although here it is to be understood that t at this timeonSingle pulse width does not reach the maximum pulse width of transmitter permission,
But since duty compares the low of transmitter permission, transmitter is in tonThe heat of generation is in toffIt dissipates, does not have completely in time
Have and reach balance, causes the heat Cycle by Cycle of transmitter to accumulate and increase, and the energy that the protection circuit then will build up on is tired out
Meter, has reached maximum bearing value and has been protected.
Embodiment 2
Current source waveform generation circuit is increased on the basis of embodiment 1, and the circuit theory of formation is as shown in figure 4, be
Operational amplifier N1 is the charging capacitor in embodiment 1 for generating constant-current source, C1, and wherein R is the resistance value of first resistor, the
One resistance R1 is used to detect the charging current Ic of charging capacitor C1, is grounded after the charging capacitor connection first resistor, described to fill
Node between capacitor and first resistor is detection electrical voltage point, detects voltage Vs=R*Ic, and reference voltage v1_pulse passes through
It connects a resistance and generates the positive input that input voltage vin is connected to operational amplifier, operational amplifier N1 will test electricity
Pressure Vs is compared with input voltage vin, and the error voltage of the two is amplified, when detecting Vin of the voltage Vs less than input, fortune
It calculates amplifier N1 output voltage to increase, then charging current Ic increases, and then causes to detect voltage Vs increase, to reduce itself and Vin
Gap, otherwise when detect voltage Vs be greater than Vin when, operational amplifier N1 can feedback control detection voltage Vs reduce, such Vs
Voltage can be very good the waveform of tracking input Vin, and charging current Ic=Vs/R=Vin/R, then capacitance charging current Ic wave
The waveform of Vin can be traced in shape.Then voltage-to-ground V on capacitor CCG:
Compared to Figure 1 the input voltage of comparator N2 anode increases regulation biasing Vin, therefore only need to be by the forward direction of Vin
Voltage value increases on Vref, then voltage comparison result is in the same manner as in Example 1.The simulation waveform of embodiment 2 respectively such as Fig. 6 and
Shown in Fig. 7.
Embodiment 3
In embodiment 2, input control signal source (reference voltage v1_pulse) needs negative benchmark, due to amplifier need to export it is negative
Voltage, it is therefore desirable to negative supply power supply.On the basis of embodiment 2, embodiment 3 has done further improvement, circuit diagram
It is as shown in Figure 8: to further include the first benchmark positive voltage vref2.5, voltage source reference voltage generation circuit, the benchmark positive voltage
The negative input of operational amplifier N 1, the voltage source base are input to after the detection voltage superposition of vref2.5 and first resistor
The output signal of quasi- voltage generation circuit is supplied to the positive input of operational amplifier, and the voltage source reference voltage generates electricity
The voltage source reference voltage of road output includes two different positive voltages.
One of realization structure of voltage source reference voltage generation circuit: including the second benchmark positive voltage vref, forward direction
Pulse voltage v2_pulse, triode V8, the 5th resistance R5, the 6th resistance R6, the 7th resistance R7, the 8th resistance R8, the 9th electricity
It hinders R9, the second capacitor C2, the triode V8 and turn-on and turn-off, the triode V8 is controlled by external digital logic signal
Base stage connect with direct impulse voltage v2_pulse by the 8th resistance R8, it is electric that the collector of the triode V8 connects the 5th
The second benchmark positive voltage vref is connected after resistance R5, and the 6th resistance R6, institute are set between the emitter and collector of the triode
It is grounded after stating the 7th resistance R7 of emitter connection of triode V8, the second capacitor C2 of the 7th resistance R7 parallel connection, three pole
During the emitter of pipe is connected to the positive input of operational amplifier, triode ON and shutdown by the 9th resistance R9
Two different voltage source reference voltages are provided respectively to the positive input of operational amplifier；Specific production principle is as follows.
(1) connected positive first voltage benchmark Vref2.5 in the lower end of capacitance current detection resistance R1.Such capacitor
The positive voltage (being the reference voltage of 2.5V here) of the first voltage benchmark is superimposed on the feedback voltage of electric current, then operation amplifier
When the benchmark of the positive input of device N1 is higher than 2.5V, amplifier output becomes larger can be to capacitor charging, and operational amplifier N1
When the benchmark of positive input is lower than 2.5V, amplifier output becomes smaller and can discharge to capacitor, then operational amplifier N1 can save
Negative voltage source.
(2) input control signal can be realized using digital logic signal.Switching transistor V8 is by external Digital Logic
Signal controls turn-on and turn-off, then can be short-circuit or not short-circuit by divider resistance R6, the different benchmark electricity of two switched
Pressure, then can control the following by inputting voltages input control signal of operational amplifier N1 positive input in the two reference voltages
It switches over, and the two reference voltages are all positive voltages.Therefore entire control circuit can be real using single positive voltage source
It is existing.
Corresponding simulation waveform is as shown in figure 11, it can be seen that the charging current of charging capacitor has tracked benchmark electricity well
Corrugating.
The quantitative design example of embodiment 3:
The maximum allowable output pulse width of certain transmitter is 200us, it is first determined charging capacitor capacity is 0.1uF, electric current
Detection resistance resistance value is 1k Ω, and biased reference Vref2.5=2.5V, capacitor positive charge electric current is 0.5mA, then positive charge is
The detection voltage U of current sense resistorR=0.5mA*1k Ω=0.5V, then the positive amplitude of Vin is Vinon=2.5V+0.5V=
3V.Know the 200us that charges, the voltage increase of capacitor are as follows:Then comparator N2
Benchmark voltage setting are as follows: Δ U+UR+UREF=1+0.5+2.5=4V, as shown in figure 9, comparator N2 is exported in 200us
Overturn output protection signal.
If transmitter allows maximum duty cycle to be 20%, in maximum pulse width 200us, turn-off time 200us/
20%* (1-20%)=800us, can obtainThen discharge current IO=Ii/ 4=0.5mA/4
=0.125mA, the then pressure drop on current sense resistor at this time are as follows: VRoff=-0.125mA*1k Ω=- 0.125V, then when turning off
Input voltage vin are as follows: VinoffVref+VR=2.5V+0.125V=2.375V.Then as shown in Figure 10, capacitor charge and discharge is equal at this time
Weighing apparatus.
Assuming that the pulse width of grid control signal is 100us, period 400us, duty ratio 25% has been more than transmitting
The maximum duty cycle that machine allows, but since monocycle impulse width did not look into the limitation of the maximum 200us of transmitter,
Monocycle can't cause to protect circuit operation.The increment in each period is Assuming that being protected after n period, then as n Δ UT+ΔUi+VREF+VRon
>=4V, i.e. n × 0.125+0.5+2.5+0.5 >=4V, then n >=4, i.e. trigger protection after 4 periods, as shown in figure 11.Therefore
Circuit realizes energy accumulation protection (i.e. duty ratio protection) after 4 periods.
The invention is not limited to specific embodiments above-mentioned.The present invention, which expands to, any in the present specification to be disclosed
New feature or any new combination, and disclose any new method or process the step of or any new combination.If this
Field technical staff is altered or modified not departing from the unsubstantiality that spirit of the invention is done, should belong to power of the present invention
The claimed range of benefit.
Claims (8)
1. a kind of maximum pulse width protection of transmitter and maximum duty cycle protect analog circuit characterized by comprising constant current
Source, charging capacitor, comparator, the second diode, the constant-current source include that constant current signal positively and negatively gives charging capacitor perseverance
Current charge or constant-current discharge, charging capacitor one end ground connection, the charging capacitor other end are connected to the positive input of comparator,
The negative input of the comparator connects reference voltage, connects second between the output end and positive input of the comparator
Diode.
2. the maximum pulse width protection of transmitter as described in claim 1 and maximum duty cycle protect analog circuit, feature exists
In the maximum pulse width protection of the transmitter and maximum duty cycle protection analog circuit further include first diode, the charging
Capacitor first diode in parallel.
3. the maximum pulse width protection of transmitter as claimed in claim 2 and maximum duty cycle protect analog circuit, feature exists
In the grid control signal synchronism switching of the constant-current source and transmitter obtains constant current signal positively and negatively.
4. the maximum pulse width protection of transmitter as claimed in claim 3 and maximum duty cycle protect analog circuit, feature exists
In, within the period that grid control signal is opened using to charging capacitor carry out constant-current charge, grid control signal be pass
Constant-current discharge is carried out to charging capacitor in period.
5. the maximum pulse width protection of transmitter as claimed in claim 2 and maximum duty cycle protect analog circuit, feature exists
In, the maximum pulse width protection of the transmitter and maximum duty cycle protection analog circuit further include current source waveform generation circuit,
The current source waveform generation circuit includes operational amplifier, first resistor, voltage source reference voltage, the operational amplifier
Output end is separately connected the positive input and charging capacitor of comparator, and the first resistor is used to detect the electricity of charging capacitor
Stream obtains detection voltage, will test voltage and voltage source reference voltage be separately input to operational amplifier negative input and
Positive input, the operational amplifier is for generating constant-current source.
6. the maximum pulse width protection of transmitter as claimed in claim 5 and maximum duty cycle protect analog circuit, feature exists
In the charging capacitor is grounded after connecting first resistor, and the node between the charging capacitor and first resistor is connected to operation
The positive input of the negative input of amplifier, the operational amplifier connects voltage source reference voltage.
7. the maximum pulse width protection of transmitter as claimed in claim 5 and maximum duty cycle protect analog circuit, feature exists
In the maximum pulse width protection of the transmitter and maximum duty cycle protection analog circuit further include the first benchmark positive voltage, voltage
Operational amplifier is input to after the detection voltage superposition of source reference voltage generating circuit, the benchmark positive voltage and first resistor
The output signal of negative input, the voltage source reference voltage generation circuit is supplied to the positive input of operational amplifier,
The voltage source reference voltage of the voltage source reference voltage generation circuit output includes two positive voltages of switching.
8. the maximum pulse width protection of transmitter as claimed in claim 7 and maximum duty cycle protect analog circuit, feature exists
In, the voltage source reference voltage generation circuit include the second benchmark positive voltage, direct impulse voltage, triode, the 5th resistance,
6th resistance, the 7th resistance, the 8th resistance, the 9th resistance, the second capacitor, the triode pass through external digital logic signal
Turn-on and turn-off are controlled, the base stage of the triode is connect by the 8th resistance with direct impulse voltage, the collection of the triode
Electrode connects the second benchmark positive voltage after connecting the 5th resistance, the 6th electricity of setting between the emitter and collector of the triode
Resistance, the emitter of the triode are grounded after connecting the 7th resistance, the second capacitor of the 7th resistor coupled in parallel, the triode
Emitter mentions respectively during being connected to the positive input of operational amplifier, triode ON and shutdown by the 9th resistance
For two different voltage source reference voltages to the positive input of operational amplifier.
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| CN201910529304.XA CN110247643B (en) | 2019-06-19 | 2019-06-19 | Maximum pulse width protection and maximum duty ratio protection analog circuit of transmitter |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201910529304.XA CN110247643B (en) | 2019-06-19 | 2019-06-19 | Maximum pulse width protection and maximum duty ratio protection analog circuit of transmitter |
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| CN110247643A true CN110247643A (en) | 2019-09-17 |
| CN110247643B CN110247643B (en) | 2021-05-18 |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110943430A (en) * | 2019-11-12 | 2020-03-31 | 欣旺达电子股份有限公司 | DSP fault protection circuit and device |
| CN113572485A (en) * | 2021-06-28 | 2021-10-29 | 中国船舶重工集团公司第七二三研究所 | Over-pulse width protection circuit of traveling wave tube modulator |
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| JPH08154040A (en) * | 1994-11-25 | 1996-06-11 | Sony Corp | Variable frequency oscillator |
| CN1610277A (en) * | 2003-10-24 | 2005-04-27 | 夏普株式会社 | Infrared transmitter circuit and electronic device |
| CN101093983A (en) * | 2006-06-21 | 2007-12-26 | 夏普株式会社 | Comparing circuit and infrared receiver |
| CN105305961A (en) * | 2015-10-29 | 2016-02-03 | 上海华力微电子有限公司 | Oscillating circuit for eliminating comparator delay |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH06311004A (en) * | 1993-04-27 | 1994-11-04 | Mitsubishi Electric Corp | Power supply control circuit |
| JPH08154040A (en) * | 1994-11-25 | 1996-06-11 | Sony Corp | Variable frequency oscillator |
| CN1610277A (en) * | 2003-10-24 | 2005-04-27 | 夏普株式会社 | Infrared transmitter circuit and electronic device |
| CN101093983A (en) * | 2006-06-21 | 2007-12-26 | 夏普株式会社 | Comparing circuit and infrared receiver |
| CN105305961A (en) * | 2015-10-29 | 2016-02-03 | 上海华力微电子有限公司 | Oscillating circuit for eliminating comparator delay |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN110943430A (en) * | 2019-11-12 | 2020-03-31 | 欣旺达电子股份有限公司 | DSP fault protection circuit and device |
| CN113572485A (en) * | 2021-06-28 | 2021-10-29 | 中国船舶重工集团公司第七二三研究所 | Over-pulse width protection circuit of traveling wave tube modulator |
| CN113572485B (en) * | 2021-06-28 | 2022-05-20 | 中国船舶重工集团公司第七二三研究所 | Over-pulse width protection circuit of traveling wave tube modulator |
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