CN110165955B - Permanent magnet synchronous motor inductance parameter identification method based on quasi-proportional resonant controller - Google Patents

Permanent magnet synchronous motor inductance parameter identification method based on quasi-proportional resonant controller Download PDF

Info

Publication number
CN110165955B
CN110165955B CN201910392818.5A CN201910392818A CN110165955B CN 110165955 B CN110165955 B CN 110165955B CN 201910392818 A CN201910392818 A CN 201910392818A CN 110165955 B CN110165955 B CN 110165955B
Authority
CN
China
Prior art keywords
axis
signal
current
phase
voltage
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN201910392818.5A
Other languages
Chinese (zh)
Other versions
CN110165955A (en
Inventor
郭鸿浩
吕鹏程
杨峰
谷靖
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Nanjing University of Posts and Telecommunications
Original Assignee
Nanjing University of Posts and Telecommunications
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Nanjing University of Posts and Telecommunications filed Critical Nanjing University of Posts and Telecommunications
Priority to CN201910392818.5A priority Critical patent/CN110165955B/en
Publication of CN110165955A publication Critical patent/CN110165955A/en
Application granted granted Critical
Publication of CN110165955B publication Critical patent/CN110165955B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/022—Synchronous motors
    • H02P25/024—Synchronous motors controlled by supply frequency
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2205/00—Indexing scheme relating to controlling arrangements characterised by the control loops
    • H02P2205/01—Current loop, i.e. comparison of the motor current with a current reference

Abstract

The invention discloses a motorIn the control field, a method for identifying inductance parameters of a permanent magnet synchronous motor based on a quasi-resonant controller is provided
Figure 889706DEST_PATH_IMAGE002
Injecting a high-frequency pulsating current signal into the shaft, and designing a proportionality coefficient, a resonance coefficient and a cut-off frequency of the quasi-proportional resonance controller, so that the controller can realize no-static-error control of the injected high-frequency pulsating current signal near the resonance frequency, and further obtain a high-frequency voltage response signal under the injected high-frequency pulsating current; then, the amplitude of the high-frequency response signal is extracted by utilizing discrete Fourier transform, and further the amplitude is calculated
Figure 235237DEST_PATH_IMAGE002
Axial inductance value
Figure 588858DEST_PATH_IMAGE004
And
Figure DEST_PATH_IMAGE006
(ii) a The method can reduce the current harmonic content and avoid the overcurrent problem which may occur in the voltage injection inductance parameter identification scheme; and no additional hardware facilities are required to be added to the original equipment, and the algorithm is simple and reliable.

Description

Permanent magnet synchronous motor inductance parameter identification method based on quasi-proportional resonant controller
Technical Field
The invention relates to a permanent magnet synchronous motor, in particular to a permanent magnet synchronous motor inductance parameter identification method, and belongs to the technical field of motor control.
Background
The permanent magnet synchronous motor is widely applied to industry by virtue of the advantages of small volume, light weight, high power factor, good control performance and the like. The motor parameters of the permanent magnet synchronous motor need to be known for accurate control of the permanent magnet synchronous motor, and most of the permanent magnet synchronous motor needs to be controlled under the premise of knowing the motor parameters no matter the permanent magnet synchronous motor is controlled by a sensor or weak magnetic control of the motor and various novel control algorithms. Particularly, the magnetic field of the built-in permanent magnet synchronous motor is easy to enter a nonlinear region, and the inductance and the magnetic flux of the permanent magnet are greatly changed to cause the reduction of torque precision and the deterioration of system stability, so that the identification of inductance parameters of the permanent magnet synchronous motor under the action of different currents is very important.
Disclosure of Invention
The invention aims to provide a method for identifying inductance parameters of a permanent magnet synchronous motor based on a quasi-proportional resonant controller, which can accurately identify d-axis inductance and q-axis inductance of surface-mounted permanent magnet synchronous motors and embedded permanent magnet synchronous motors.
The purpose of the invention is realized as follows: the method for identifying the inductance parameters of the permanent magnet synchronous motor based on the quasi-proportional resonant controller comprises the following steps:
step 1) collecting a current signal at the input end of a permanent magnet synchronous motor by adopting a current sensor, wherein the A-phase stator current i of the current sensorAThe signal output end is connected to the A-phase stator current signal input end of the three-phase static-two-phase static coordinate transformation link; b-phase stator current i of current sensorBThe signal output end is connected to the B-phase stator current signal input end of the three-phase static-two-phase static coordinate transformation link;
step 2) alpha-axis current i of three-phase static-two-phase static coordinate transformation unitαThe signal output end is connected to the alpha-axis current signal input end of the two-phase static-two-phase rotating coordinate conversion unit and the beta-axis current i of the three-phase static-two-phase static coordinate conversion unitβThe signal output end is connected to the beta-axis current signal input end of the two-phase static-two-phase rotating coordinate conversion unit to obtain dq-axis current idAnd iq；
Step 3) d-axis current i of two-phase static-two-phase rotating coordinate transformation unitdThe signal output end is connected to the input end of the d-axis low-pass filter and the input end of the d-axis band-pass filter; q-axis current i of two-phase stationary-two-phase rotating coordinate transformation unitqThe signal output end is connected to the input end of the q-axis low-pass filter and the input end of the q-axis band-pass filter;
step 4) d-axis high-frequency injection current signal idhrefAnd output i of d-axis band-pass filterdhMaking a difference, wherein the difference is connected to the input end of a d-axis quasi-proportional resonant controller (PR); q-axis high-frequency injection current signal iqhrefAnd the output i of the q-axis band-pass filterqhTaking a difference value, wherein the difference value is connected to the input end of a q-axis quasi-proportional resonant controller (PR);
step 5) adopting a photoelectric encoder to collect a rotating speed signal of the permanent magnet synchronous motor, wherein the rotating speed omega measured by the photoelectric encodereGiven a rotational speed ωerefSubtracting the rotation speed omega measured by the photoelectric encodereTaking the obtained difference value as the input of the speed regulator;
step 6) outputting a q-axis current reference signal i by the output end of the speed regulatorqrefQ-axis current reference signal iqrefSubtracting the output signal i of the q-axis low-pass filterqlThe difference is connected to the input of the current regulator; d-axis given current signal idrefSubtracting the output signal i of the d-axis low-pass filterdlThe difference is connected to the input of the current regulator;
step 7) voltage signal U output by d-axis voltage output end of current regulatordAdding an output signal of a d-axis quasi-proportional resonant controller (PR), and connecting the output signal to a d-axis voltage input end of two-phase static-two-phase rotating coordinate transformation and an input end of a discrete Fourier transform module (DFT); voltage signal U output by q-axis voltage output end of current regulatorqAdding an output signal of a q-axis quasi-proportional resonant controller (PR), and connecting the q-axis voltage input end of the two-phase static-two-phase rotating coordinate transformation and the input end of a discrete Fourier transform module (DFT);
step 8) two-phase static-two-phase rotating coordinate transformation output alpha-axis voltage signal UαA beta-axis voltage signal U connected to the input end of the alpha-axis voltage given signal of voltage space vector pulse width modulation and output by two-phase static-two-phase rotating coordinate transformationβA beta axis voltage given signal input end connected to voltage space vector pulse width modulation;
step 9) state signal output ends of six power switching tubes in the voltage space vector pulse width modulation unit are simultaneously connected with a power switching tube-shaped state signal input end of a voltage type inverter, and three-phase voltage output ends of the voltage type inverter are respectively and correspondingly connected with three-phase voltage input ends of the permanent magnet synchronous motor;
step 10) separationThe output of the scattered Fourier transform (DFT) link is connected to an inductance parameter identification module which outputs a d-axis inductance value LdAnd q-axis inductance Lq。
As a further limitation of the present invention, the output of the Discrete Fourier Transform (DFT) element in step 10) is the amplitude of the high frequency response voltage signal in dq axis system, and the d-axis inductance L is calculated according to the amplitudedAnd q-axis inductance LqThe formula of (1) is:
Figure BDA0002057144770000031
in the formula of Udh_AmpAmplitude, U, of the high frequency response signal at the d-axis injection frequencyqh_AmpAmplitude, I, of the high-frequency response signal at the injection frequency for the q-axismhFor the amplitude, omega, of the injected high-frequency pulsating current signalhIs the frequency of the injected current signal.
Compared with the prior art, the invention adopting the technical scheme has the following technical effects: the invention discloses a system and a method for identifying inductance parameters of a permanent magnet synchronous motor based on quasi-proportional resonance control, which provides a scheme for identifying the inductance parameters of the permanent magnet synchronous motor by a current injection method, utilizes a quasi-proportional resonance controller to realize closed-loop control of high-frequency pulse oscillation current injection signals in a mode of injecting high-frequency pulse oscillation current signals, and reasonably designs a proportional gain coefficient K of the quasi-proportional resonance controllerpIntegral gain coefficient KrAnd a cut-off frequency omegacSo that it is at the resonant frequency omegahNearby high-frequency pulse oscillation current signals can be controlled without static error; the quasi-proportional resonant controller can accurately control the size of an injected current signal, reduce the current harmonic content and avoid the overcurrent problem possibly occurring in an inductance parameter identification experiment by a voltage injection method; the method has the advantages that extra hardware facilities do not need to be added on the original equipment, the algorithm is simple and reliable, d-axis inductance and q-axis inductance of the surface-mounted permanent magnet synchronous motor and the embedded permanent magnet synchronous motor can be accurately identified, and the motor shaft is not influenced to identify no matter in a free state or in a tightly-holding stateThe accuracy of (2); the parameters obtained through identification can be used in a vector control algorithm of the permanent magnet synchronous motor, so that the inductance parameter identification scheme has stronger universality.
Drawings
Fig. 1 is a schematic block diagram of a quasi-proportional resonance-based permanent magnet synchronous motor inductance parameter identification system according to the present invention, wherein DFT is a discrete fourier transform link.
FIG. 2 is a schematic block diagram of a quasi-proportional resonant controller of the present invention.
Fig. 3 is a flow chart of the amplitude extraction of the high frequency response signal of the discrete fourier segment according to the present invention.
FIG. 4 is a schematic block diagram of an inductance value calculation in the inductance identification unit according to the present invention.
Detailed Description
The technical scheme of the invention is further explained in detail by combining the attached drawings:
the invention mainly relates to a permanent magnet synchronous motor inductance parameter identification method based on a quasi-proportional resonant controller.
The identification method mainly comprises the following steps: the device comprises a three-phase inverter, a space vector pulse width modulation unit, a photoelectric encoder unit, a three-phase static-two-phase static coordinate transformation unit, a two-phase static-two-phase rotating coordinate transformation unit, a two-phase rotating-two-phase static coordinate transformation unit, a current regulator (proportional integral controller), a low-pass filter, a band-pass filter, a quasi-proportional resonant controller (PR), a discrete Fourier analysis unit (DFT) and an inductance identification unit.
The specific implementation comprises the following steps:
the method comprises the following steps: the current sensor is used for collecting current signals at the input end of the permanent magnet synchronous motor, and the a-phase stator current i and the b-phase stator current i of the current sensora、ibInputting the current to a three-phase static-two-phase static coordinate conversion unit to obtain alpha and beta axis current iα、iβ；
Step two: alpha beta axis current i obtained by three-phase static-two-phase static coordinate transformation unitα、iβInput to a two-phase static-two-phase rotating coordinate transformation unit to obtain dq-axis current id、iq；
Step three: dq-axis current i obtained by two-phase stationary-two-phase rotating coordinate transformation unitd、iqRespectively input into a low-pass filter to obtain currents idl、iqlWhile respectively inputting to the band-pass filters to obtain a current idh、iqh；
Step four: d-axis injected high-frequency current idhref＝Imh cos(ωht) subtracting the current i obtained by the d-axis band-pass filter in the step threedhThen input into a quasi-proportional resonant controller (PR) to obtain a voltage value Udh(ii) a q-axis injected high-frequency current iqhref＝Imh cos(ωht) subtracting the current i obtained by the q-axis band-pass filter in the step threeqhThen input into a quasi-proportional resonant controller (PR) to obtain a voltage value Uqh；
Step five: given value of speed of rotation omega of electric machineerefMotor speed omega obtained by subtracting photoelectric encoder uniteInputting the current into a speed regulator (PI controller) to obtain a current reference value iqref；
Step six: given d-axis current idrefSubtracting the current i obtained in the third stepdlInput to a current regulator (PI controller) to obtain a voltage Ud(ii) a The current reference value i obtained in the fifth stepqrefSubtracting the current i obtained in the third stepqlInput to a current regulator (PI controller) to obtain a voltage Uq；
Step seven: voltage value U obtained in step sixdAdding the voltage U obtained in the fourth stepdhThe two-phase rotation-two-phase static coordinate system is input, and simultaneously the two-phase rotation-two-phase static coordinate system is input to a discrete Fourier transform module; voltage value U obtained in step sixqAdding the voltage U obtained in the fourth stepqhThe two-phase rotation-two-phase static coordinate system is input, and simultaneously the two-phase rotation-two-phase static coordinate system is input to a discrete Fourier transform module;
step eight: alpha and beta axis voltage signal U obtained by two-phase rotation-two-phase static coordinate systemα、UβAnd simultaneously input to the space vector pulse width modulation unit;
step nine: the space vector pulse width modulation unit obtains six paths of control signals and inputs the six paths of control signals into the three-phase inverter to obtain three-phase input voltage of the permanent magnet synchronous motor;
step ten: in the seventh step, a discrete Fourier analysis unit (DFT) obtains omegahVoltage response signal amplitude at frequency; let d-axis be at omegahThe amplitude of the response voltage signal at the frequency is Udh_AmpAnd q axis is at ωhResponse voltage amplitude at frequency of Uqh_AmpAn input inductance identification unit to obtain a dq-axis inductance LdAnd Lq。
In the invention, the basic theory of the used permanent magnet synchronous motor is as follows:
the injected pulse vibration high-frequency current obtains high-frequency voltage quantity through a quasi-proportional resonance controller (PR), the voltage quantity is output through the power supply of an SVPWM voltage source inverter of a speed regulation system, and the voltage quantity is applied to a Permanent Magnet Synchronous Motor (PMSM); suppose the frequency of the injected high frequency current signal is ωhAmplitude of the high-frequency injection current ImhUsing dq coordinate system, the injected pulse-oscillation high-frequency current signal can be expressed as:
Figure BDA0002057144770000051
the injection frequency of the high-frequency current signal which is usually selected is far greater than the frequency of the fundamental current and is less than the switching frequency of the inverter; under a high-frequency signal, the impedance of the permanent magnet synchronous motor mainly depends on inductive reactance, and the voltage drop on the stator resistor is negligible; a simplified model at high frequency is obtained:
Figure BDA0002057144770000052
according to the formula (2) and the formula (1), under the condition of pulse vibration high-frequency current injection, the high-frequency feedback voltage signal of the permanent magnet synchronous motor is as follows:
Figure BDA0002057144770000061
as can be seen from the formula (3), the frequency in the dq axis is ωhAmplitude U of the high-frequency voltage response signaldh_Amp＝ImhωhLdAnd Uqh_Amp＝ImhωhLqD-axis inductance L of the permanent magnet synchronous motor can be obtaineddAnd q-axis inductance LqThe following formula:
Figure BDA0002057144770000062
the invention is further described below with reference to the accompanying drawings:
the speed regulator unit in fig. 1 is a PI regulator, and the current regulator in fig. 1 is also a PI regulator, so that the motor can complete closed-loop operation and operate at a given rotating speed and current, and inductance values under different currents can be conveniently obtained;
FIG. 2 shows details of the quasi-proportional resonant controller unit of FIG. 1;
the flow of the DFT (quasi-proportional resonant controller) module of fig. 1 is shown in fig. 3, for determining the amplitude of the high frequency voltage response signal;
the process of the inductance identification module in fig. 1 is shown in fig. 4, and is used for specifically calculating the dq-axis inductance value by using the amplitude of the high frequency response signal.
The above description is only an embodiment of the present invention, but the scope of the present invention is not limited thereto, and any person skilled in the art can understand that the modifications or substitutions within the technical scope of the present invention are included in the scope of the present invention, and therefore, the scope of the present invention should be subject to the protection scope of the claims.

Claims (2)

1. The method for identifying the inductance parameters of the permanent magnet synchronous motor based on the quasi-proportional resonant controller is characterized by comprising the following steps of:
step 1) collecting a current signal at the input end of a permanent magnet synchronous motor by adopting a current sensor, wherein the A-phase stator current i of the current sensorAThe signal output end is connected to the A-phase stator current signal input end of the three-phase static-two-phase static coordinate transformation link; b-phase stator current i of current sensorBThe signal output end is connected to the B-phase stator current signal input end of the three-phase static-two-phase static coordinate transformation link;
step 2) alpha-axis current i of three-phase static-two-phase static coordinate transformation unitαThe signal output end is connected to the alpha-axis current signal input end of the two-phase static-two-phase rotating coordinate conversion unit and the beta-axis current i of the three-phase static-two-phase static coordinate conversion unitβThe signal output end is connected to the beta-axis current signal input end of the two-phase static-two-phase rotating coordinate conversion unit to obtain dq-axis current idAnd iq；
Step 3) d-axis current i of two-phase static-two-phase rotating coordinate transformation unitdThe signal output end is connected to the input end of the d-axis low-pass filter and the input end of the d-axis band-pass filter; q-axis current i of two-phase stationary-two-phase rotating coordinate transformation unitqThe signal output end is connected to the input end of the q-axis low-pass filter and the input end of the q-axis band-pass filter;
step 4) d-axis high-frequency injection current signal idhrefAnd output i of d-axis band-pass filterdhMaking a difference, wherein the difference is connected to the input end of a d-axis quasi-proportional resonant controller (PR); q-axis high-frequency injection current signal iqhrefAnd the output i of the q-axis band-pass filterqhTaking a difference value, wherein the difference value is connected to the input end of a q-axis quasi-proportional resonant controller (PR);
step 5) adopting a photoelectric encoder to collect a rotating speed signal of the permanent magnet synchronous motor, wherein the rotating speed omega measured by the photoelectric encodereGiven a rotational speed ωerefSubtracting the rotation speed omega measured by the photoelectric encodereTaking the obtained difference value as the input of the speed regulator;
step 6) outputting a q-axis current reference signal i by the output end of the speed regulatorqrefQ-axis current reference signal iqrefSubtracting the output signal i of the q-axis low-pass filterqlThe difference is connected to the input of the current regulator; d-axis given current signal idrefSubtracting the output signal i of the d-axis low-pass filterdlThe difference is connected to the input of the current regulator;
step 7) voltage signal U output by d-axis voltage output end of current regulatordAdding an output signal of a d-axis quasi-proportional resonant controller (PR), and connecting the output signal to a d-axis voltage input end of two-phase static-two-phase rotating coordinate transformation and an input end of a discrete Fourier transform module (DFT); voltage signal U output by q-axis voltage output end of current regulatorqAdding an output signal of a q-axis quasi-proportional resonant controller (PR), and connecting the q-axis voltage input end of the two-phase static-two-phase rotating coordinate transformation and the input end of a discrete Fourier transform module (DFT);
step 8) two-phase static-two-phase rotating coordinate transformation output alpha-axis voltage signal UαA beta-axis voltage signal U connected to the input end of the alpha-axis voltage given signal of voltage space vector pulse width modulation and output by two-phase static-two-phase rotating coordinate transformationβA beta axis voltage given signal input end connected to voltage space vector pulse width modulation;
step 9) state signal output ends of six power switching tubes in the voltage space vector pulse width modulation unit are simultaneously connected with a power switching tube-shaped state signal input end of a voltage type inverter, and three-phase voltage output ends of the voltage type inverter are respectively and correspondingly connected with three-phase voltage input ends of the permanent magnet synchronous motor;
step 10) the output of the Discrete Fourier Transform (DFT) link is connected to an inductance parameter identification module, and the inductance parameter identification module outputs a d-axis inductance value LdAnd q-axis inductance Lq。
2. The method for identifying the inductance parameters of the PMSM based on the quasi-proportional resonant controller as claimed in claim 1, wherein the output of the Discrete Fourier Transform (DFT) in the step 10) is the amplitude of the high-frequency response voltage signal under dq shafting, and the d-axis inductance value L is calculated according to the amplitudedAnd q-axis inductance LqThe formula of (1) is:
Figure FDA0002057144760000021
in the formula of Udh_AmpAmplitude, U, of the high frequency response signal at the d-axis injection frequencyqh_AmpAmplitude, I, of the high-frequency response signal at the injection frequency for the q-axismhFor the amplitude, omega, of the injected high-frequency pulsating current signalhIs the frequency of the injected current signal.
CN201910392818.5A 2019-05-13 2019-05-13 Permanent magnet synchronous motor inductance parameter identification method based on quasi-proportional resonant controller Active CN110165955B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201910392818.5A CN110165955B (en) 2019-05-13 2019-05-13 Permanent magnet synchronous motor inductance parameter identification method based on quasi-proportional resonant controller

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201910392818.5A CN110165955B (en) 2019-05-13 2019-05-13 Permanent magnet synchronous motor inductance parameter identification method based on quasi-proportional resonant controller

Publications (2)

Publication Number Publication Date
CN110165955A CN110165955A (en) 2019-08-23
CN110165955B true CN110165955B (en) 2021-01-19

Family

ID=67634280

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201910392818.5A Active CN110165955B (en) 2019-05-13 2019-05-13 Permanent magnet synchronous motor inductance parameter identification method based on quasi-proportional resonant controller

Country Status (1)

Country Link
CN (1) CN110165955B (en)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114112396B (en) * 2021-10-29 2023-09-26 江苏大学 Bearing fault diagnosis method under rotating speed fluctuation quasi-stationary working condition by adopting current signal analysis
CN114583213B (en) * 2022-03-21 2024-01-23 苏州溯驭技术有限公司 Decoupling control method based on air path pressure and flow of fuel cell
CN117578936B (en) * 2024-01-16 2024-03-19 致瞻科技(上海)有限公司 Method and device for measuring dq axis inductance saturation curve of permanent magnet synchronous motor

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103956955B (en) * 2014-04-11 2016-08-17 浙江大学 A kind of monolateral controlled common bus opens the suppressing method of winding permanent magnet motor system and zero-sequence current thereof
CN104410345A (en) * 2014-10-24 2015-03-11 深圳市芯海科技有限公司 Field programmable gate array (FPGA)-based permanent magnet synchronous motor vector control device and method
CN104811115B (en) * 2015-04-15 2017-03-22 哈尔滨工业大学 Quasi-proportional resonance control-based permanent magnet synchronous motor parameter identification system and method
JP6917264B2 (en) * 2017-09-29 2021-08-11 日産自動車株式会社 Motor control method and motor control device.

Also Published As

Publication number Publication date
CN110165955A (en) 2019-08-23

Similar Documents

Publication Publication Date Title
CN110112973B (en) Permanent magnet synchronous motor inductance parameter identification method based on high-frequency rotating voltage injection
CN110165955B (en) Permanent magnet synchronous motor inductance parameter identification method based on quasi-proportional resonant controller
CN107359837B (en) Permanent magnet synchronous motor torque control method based on sliding mode observer and active disturbance rejection
CN104811115B (en) Quasi-proportional resonance control-based permanent magnet synchronous motor parameter identification system and method
CN110198150B (en) Permanent magnet synchronous motor multi-parameter online identification method
Wang et al. An EMF observer for PMSM sensorless drives adaptive to stator resistance and rotor flux linkage
CN110022106B (en) Permanent magnet synchronous motor position sensorless control method based on high-frequency signal injection
CN107482982B (en) Asynchronous motor vector control method based on iron loss model
CN109039189A (en) Two vector prediction control system of permanent magnet synchronous motor and method based on geometric method
CN104767453B (en) Automatic permanent magnet synchronous motor quadrature-direct axis inductance identification method
CN101650390B (en) Method of measuring inductance parameters of stator of surface AC permanent magnet synchronous motor on line
CN105680755B (en) The model-free current control device and method of a kind of permagnetic synchronous motor
CN108521242A (en) A kind of permanent magnet synchronous motor general-purpose control system and its control method
CN103338002A (en) Method for identifying permanent magnet flux and quadrature axis inductance of permanent magnet synchronous motor
CN107241042A (en) Pulsating High Frequency Injection signal extraction system and strategy based on EPLL in parallel
CN104467597A (en) V/F control method for inhibiting induction motor current oscillation
CN104167971B (en) A kind of electric excitation synchronous motor initial position of rotor detection means and detection method
Li et al. Absolute inductance estimation of PMSM considering high-frequency resistance
CN112054730A (en) Permanent magnet synchronous motor online parameter identification method
CN106230322A (en) Asynchronous motor DC pre-excitation based on flux compensation and deviation de-couple starts method
CN112511059B (en) High-precision position estimation method for permanent magnet synchronous motor
Zhang et al. MTPA-based high-frequency square wave voltage signal injection strategy for IPMSM control
CN110649847A (en) Position-sensorless control method of PMSLM (permanent magnet synchronous Motor) at low-speed stage
CN105429519B (en) A kind of detection device and detection method of permanent-magnetism synchronous motor permanent magnetic magnetic linkage
Zhang et al. A new inductance measurement method for permanent magnet synchronous linear motor

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant