CN110138422A - Millimetre-wave attenuator fast beam alignment methods based on sparse coding and without phase decoding - Google Patents
Millimetre-wave attenuator fast beam alignment methods based on sparse coding and without phase decoding Download PDFInfo
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- CN110138422A CN110138422A CN201910303624.3A CN201910303624A CN110138422A CN 110138422 A CN110138422 A CN 110138422A CN 201910303624 A CN201910303624 A CN 201910303624A CN 110138422 A CN110138422 A CN 110138422A
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/0413—MIMO systems
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L41/00—Arrangements for maintenance, administration or management of data switching networks, e.g. of packet switching networks
- H04L41/14—Network analysis or design
Abstract
The millimetre-wave attenuator fast beam alignment methods that the invention discloses a kind of based on sparse coding and without phase decoding, belong to millimeter wave wireless communication technology field.The present invention utilizes millimeter wave channel sparse characteristic, wave beam alignment issues are modeled as sparse coding and the problem of without phase decoding, and on the basis of sparse bigraph coding, in the case where only receiving the amplitude information of signal, by constructing the sparseness measuring matrix met certain condition, the algorithm estimation beam direction of low computation complexity and the path fading information in each direction are designed.Since the present invention is not against the phase information for receiving signal, there is higher robustness to noise.
Description
Technical field
The invention belongs to millimeter waves to wirelessly communicate (millimeter wave wireless communication) technology
Field, and in particular to millimetre-wave attenuator fast beam technique of alignment.
Background technique
Millimetre-wave attenuator technology is considered as one of key technology of next generation mobile communication, and it is logical that some researches show that millimeter waves
Letter can provide the peak rate of 10Gbit/s.However, millimeter-wave signal has more in wireless channel compared with traditional low-frequency communication
High decline and more serious air and rainwater absorb.Due to the low wavelength characteristic of millimeter wave frequency band, large-scale antenna array and
Beam forming technique can be applied in millimeter-wave communication system.It on the one hand, can will be big since millimetre wavelength is extremely short
Amount antenna is encapsulated with smaller size；On the other hand, in conjunction with mixing digital-to-analogue beam forming technique, the array gain and sky that provide
Divide the decaying of spatial multiplexing gain energy effective compensation, improves system transfer rate and quality.Beam forming technique requires best forming and group
It closes to offer high-gain, therefore high-precision wave beam technique of alignment is particularly important.
For the wave beam alignment issues of millimeter wave mimo system, existing research work, which is concentrated mainly on, directly carries out wave beam
Space search and the aspect of channel estimation two is carried out using the method for compressed sensing.The method of compressed sensing is mostly based on for surveying
Moment matrix has very high requirement, and is easy the influence by carrier shift (Carrier Frequency Offset, CFO),
And the sampling complexity of general space search is higher, time overhead is excessive.
Summary of the invention
Goal of the invention of the invention is: in view of the above problems, providing one kind can mention not against phase information
The method of high extensive MIMO millimeter-wave communication system wave beam alignment, and higher system performance is provided.
Wave beam alignment issues are modeled as sparse coding and the problem of without phase decodings by the present invention, and are compiled by sparse bigraph
Code (Sparse Bipartite Graph Coding, SBG-Coding) construct sparseness measuring matrix, only rely on amplitude information into
Row decoding obtains the alignment of AoD (Angle of Departure) information realization fast beam, and in low signal-to-noise ratio, remains to
Keep higher robustness.
Millimetre-wave attenuator fast beam alignment methods based on sparse coding and without phase decoding of the invention, including it is following
Step:
Step S1, L bigraph G is presetlAnd matrix
Wherein bigraph GlLeft sibling quantity N correspond to number of transmission antennas, right number of nodes M is preset value；
And it is based on bigraph GlObtain the corresponding connection matrix H of each bigraphl, wherein connection matrix HlEach element Hl(i,
J) value are as follows:
MatrixWherein ti≠tj, i ≠ j and tn> 0, i, j, n=1,2 ..., N；
Based on matrix HlWithAvailable sparse coding matrix
Step S2: transmitting terminal is based on sparse coding matrix A and carries out signal processing to signal to be sent.
Step S3: receiving end is based on received signal vector and bigraph carries out wave beam registration process:
Step S301: all bigraphs are looped through, judge bigraph GlRight node whether be zero node, and record bigraph
Gl
Zero node number:
Based on each bigraph GlCorresponding received vector yl, it is carried out above and below piecemeal processing, piecemeal is corresponding thereonLower piecemeal is corresponding
It willEnergy value be compared with preset threshold value ∈, if being less than, judgement beCorresponding right node is
Zero node, to obtain bigraph GlZero number of nodes；
Step S302: it is based on L bigraph GlIn zero number of nodes P of minimummin, it is P by zero interstitial contentminBigraph GlIt is fixed
Justice is that NM schemes, to obtain NM set of graphs.
Step S303: all bigraphs in traversal NM set of graphs, and execute lower column processing:
For m=1 ..., M, following judgement is repeated: ifThen by bigraph GlM-th of right node as single
Node, and estimate the range value of corresponding activation left siblingWith the coordinate value of sparse signal x
Wherein,Indicate withIt is corresponding
The connected left sibling set of right node；
All range values based on same NM figureObtain the estimate vector of amplitude zNM set of graphs has been traversed to work as
Afterwards, the set of the estimated value of amplitude can be obtainedWherein I indicates the rank (first prime number) of NM set of graphs, also corresponding setRank
Step S304: judgement if I=1, returnsAs final estimation
If setInterior element intersection is sky, then takes set at randomSome elementAs most
Estimation eventually
Otherwise, based on each estimate vector in setIn non-zero entryAnd all NM figure G are taken at randomiContain's
Element conduct in set intersectionThe estimated value of coordinate；And according toIt obtains corresponding to each non-zero entry most
Estimation eventuallyWherein k=1,2 ..., K, K indicate setIn non-zero entry number.
In conclusion by adopting the above-described technical solution, the beneficial effects of the present invention are: only needingA measured value
It can realize to degree of precision that system wave beam is aligned, and still maintain robustness in low signal-to-noise ratio；Compared to tradition
Millimetre-wave attenuator wave beam alignment algorithm, the present invention have stronger actual operation.
Detailed description of the invention
Fig. 1 is the extensive MIMO downlink block diagram of single user.
Fig. 2 is bigraph and homography HlRelational graph.
Fig. 3 is the processing flow schematic diagram of specific embodiment.
Fig. 4 is the relationship without success rate and measured value in the case of making an uproar.
Fig. 5 be have make an uproar in the case of NMSE and measured value T, Signal to Noise Ratio (SNR) relationship, wherein the corresponding measured value T of Fig. 5-a, figure
5-b corresponds to Signal to Noise Ratio (SNR).
Fig. 6 be have make an uproar in the case of beam forming gain and measured value T, Signal to Noise Ratio (SNR) relationship, wherein Fig. 6-a is corresponding to be surveyed
The corresponding Signal to Noise Ratio (SNR) of magnitude T, Fig. 6-b.
Specific embodiment
To make the object, technical solutions and advantages of the present invention clearer, below with reference to embodiment and attached drawing, to this hair
It is bright to be described in further detail.
The problem of present invention is by the way that the wave beam under millimeter-wave communication system to be aligned is modeled as a sparse coding and without phase
The problem of position decoding, in the case where only receiving the amplitude information of signal, by constructing the sparseness measuring met certain condition
The processing mode estimation beam direction of low computation complexity and the path fading information in each direction is arranged in matrix.Due to this hair
It is bright to have a higher robustness to noise not against the phase information for receiving signal, and algorithm complexity down toWherein
K is signal path item number.
Referring to Fig. 1, beam alignment of the invention is suitable for the millimetre-wave attenuator that antenna is arranged at uniform linear array
System for simplicity in present embodiment, is only furnished with the case where single omni for receiving end.It needs to infuse
Meaning, in present embodiment, although only by taking single user as an example, can simple extension to multi-user system.Only need base station
One public code word of periodic broadcast, each user is decoded to obtain paired channel information, by random access
Corresponding AoD information can be fed back to base station by control channel, each user.
In Fig. 1, N indicates transmitting terminal number of antennas, and R indicates transmitting terminal radio frequency link number, wherein R < < N, RF
Precoder FRFIndicate radio frequency precoding, RF Chain indicates that rf chain, A/D indicate analog-to-digital conversion, Baseband
Precoder fBBIndicate the precoding of base band.
In present embodiment, using following geometry channel model:
Wherein, P is channel path number, αpFor the complex gain of pth paths, at(θp) indicate corresponding angle θpAntenna
Array response vector, θp∈ [0,2 π] is corresponding angle of departure AoD；Wherein antenna-array response vector has following form:
Wherein, λ is signal wavelength, and d is aerial array spacing, and j indicates imaginary unit, and e indicates the nature truth of a matter.
Due to the condition of sparse channel characteristic of millimeter wave, rarefaction representation of the channel in Beam Domain are as follows:
H=Dx (3)
Wherein,It is discrete Fourier transform (DFT) matrix,It is the sparse (K- of K to be estimated
Sparse signal vector (referred to as sparse signal vector to be estimated or signal vector to be estimated)), if AoD true value is proper
It is located on the divided lattice point of DFT matrix well, then K=P.Assuming that transmitting terminal continues pilot signal transmitted s (t)=1, then signal is received
It can indicate are as follows:
R (t)=hTB (t) s (t)+w (t)=xTDTB (t)+w (t)=hTFRF(t)fBB(t)+ω(t) (4)
Wherein, b (t) indicates transmitting terminal in the precoding vector of t time slot, and s (t) indicates pilot signal, and ω (t) is indicated
It obeysAdditivity white complex gaussian noise, t indicate time slot, σ indicate noise criteria it is poor, in pilot signal s (t)=1
Under the conditions of, x then indicates channel gain to be estimated；Respectively indicate simulation pre-coding matrix
And base band precoding vector,.For the wave beam for being formed simultaneously multiple and different directions, pre-coding matrix F is simulatedRF(t)=D*S (t),
Wherein D*Indicate the conjugation of DFT matrix,For column selection matrix, i.e. each column only contains a non-zero entry.
It enablesWhereinIt is a non-to contain up to R
Null element, symbol []TRepresenting matrix transposition, TtimIt indicates timeslot number, is set as Ttim=2ML.Due in millimeter-wave communication system
The presence of CFO (Carrier frequency offset), receiving signal, there are unknowable phase drifts, only amplitude information
For reliable value, therefore receives signal and may be expressed as:
Wherein,ω=[ω (1), ω (2) ... ω (Ttim)]T, x indicates wait estimate
The signal vector of meter.
Enable amplitude Indicate the estimated value of z, then matrixIt can transform to:
Wherein, ⊙ indicates Khatri-Rao product, and L indicates bigraph quantity, Hl∈{0,1}M×NFor containing having N number of left sibling and M
First of bigraph G of a right nodelConnection matrix, wherein left sibling can correspond to the item of signal vector x, and each right node refers to
To one containing there are two the set of measured value, i.e. matrixA column, as shown in Fig. 2, wherein
Sparse signal vector x, if wherein n-th, i.e. xnNon-zero then claims bigraph GlLeft sibling n is activation node.For one
The signal x of a K-sparse schemes GlA total of K activation node.According to the connection of figure, dual graph G of the present inventionlRight section
Point does following classification:
Zero node: it is not connected with any activation left sibling and if only if right node；
Single node: it is connected and if only if right node with an activation left sibling；
Multinode: and if only if right node and multiple activation left sibling vectors.
As bigraph GlRight node in be free of any multinode, then the bigraph is referred to as NM (No-Multiton) figure.It will be N number of
It is M set that left sibling, which corresponds to M right node divisions, and preceding M-1 set containsA node, wherein function
Ceil () indicates to return to the smallest positive integral for being more than or equal to specified expression formula；The last one set contains r=N- (M-1)
Ceil (N/M) a node.To simplify explanation, it is assumed thatFor integer, to maximize bigraph GlFor the probability of NM figure, this tool
, it is specified that H in body implementationlEach column only has a non-zero entry, and every row has r non-zero entry.
In the present invention, by matrixIs defined as:
Wherein ti≠tj, i ≠ j andIt enablesIndicate figure GlWith m
The lower target set of the connected left sibling of a right node.First of bigraph G is only considered belowl,It can be abbreviated as
S={ m1 … mr}.Once bigraph GlIt is given, matrix HlDetermine.
Then
WhereinFor matrix HlM row, ωl,mExpression is added in bigraph GlThe height of m-th of right node
This white noise,Respectively indicate ωl,mFirst item and Section 2.For each bigraph Gl, to make signal resolution
Interval is maximum, definitionPlFor permutation matrix, i.e.,
It enablesI.e. problem is converted into
Due to y=at this time | Ax+ ω |, whereinThen with bigraph GlCorresponding measured value yl are as follows:
Referring to Fig. 3, of the invention the specific implementation steps are as follows:
Step S1, L bigraph G is presetlAnd matrix
Wherein bigraph GlLeft sibling quantity N correspond to number of transmission antennas, right number of nodes M is preset value；
And it is based on bigraph GlObtain the corresponding connection matrix H of each bigraphl, wherein connection matrix HlEach element Hl(i,
J) value are as follows:
Matrix is setWherein ti≠tj, i ≠ j and tn> 0, i, j, n=1,2 ..., N；
Based on matrix HlWithAvailable sparse coding matrix
Step S2: transmitting terminal is based on sparse coding matrix A and carries out signal processing to signal to be sent.Then emitted again
Processing.
The present invention is only that setting sparse coding matrix A, signal processing and transmitting processing to the improvement of transmitting terminal
Using any usual processing mode.
Step S3: wave beam registration process is carried out based on received signal vector and bigraph:
Step S301: all bigraphs are looped through:
Judge bigraph GlRight node whether be zero node, and record bigraph GlZero node number.
It is zero node by the right node definition when right node is not connected with any activation left sibling, and Zuo Jie
Point is for the condition of activation node: xnFor xnNonzero term.Then for left sibling there are for the left sibling of connection relationship, as long as
Determine its left sibling (x connectedn) it is inactive node, that is, it is zero, then can be determined that when front right node is zero
Node；As long as its left sibling connected there are nonzero term, can be determined that when front right node is non-zero node.
Based on first of bigraph GlCorresponding received vector yl, by its each yl,mThe first row be denoted asSecond row is denoted asI.e. to received vector ylEach yl,mPiecemeal processing up and down is carried out, piecemeal is corresponding thereonLower piecemeal is corresponding
Wherein, bigraph GlCorresponding received vector yl, i.e., received vector y is divided into L block, every piece respectively corresponds an idol
Scheme Gl, mapping relations can determine based on sparse coding matrix.
Pass through energy decision device:To judge bigraph GlRight node whether be zero node；
Wherein:
That is, ifLess than preset threshold ∈, then it is assumed thatOnly include noise item, then withCorresponding right node institute phase
Left sibling even is zero, i.e.,Corresponding right node is zero node；IfGreater than ∈, then it is assumed thatIncluding noise item
With transmission signal terms；The case where for being equal to energy threshold, can be judged to only including noise item, also can be determined that as noise
Item and transmission signal terms include.In present embodiment, it will be equal to and be determined as that noise item includes with signal terms are sent.
That is, in the present invention, it willEnergy value (Signal amplitude value square) be compared with threshold value ∈, if small
In then judgement isCorresponding right node is zero node, to obtain bigraph GlZero number of nodes；
Step S302: it is based on L bigraph GlIn zero number of nodes P of minimummin, it is P by zero interstitial contentminBigraph GlIt is fixed
Justice is that NM schemes, to obtain NM set of graphs.
Step S303: traversing all bigraphs, if bigraph GlIt is NM figure, then executes lower column processing, i.e., only to NM set of graphs
In each bigraph carry out following processing:
For m=1 ..., M, following judgement is repeated: ifThen by bigraph GlM-th of right node as single
Node, and the corresponding range value for activating left sibling is estimated by following formulaWith the coordinate value for corresponding to sparse signal x
All range values based on same NM figureObtain the estimate vector of amplitude zAll NM figures have been traversed to work as
When, the set of the estimated value of amplitude can be obtainedWherein I indicates the quantity of NM figure.
Step S304: judgement if I=1, returnsAs final estimation
If setInterior element intersection is sky, then takes set at randomSome elementAs most
Estimation eventually
Otherwise, for each estimate vector in setIn non-zero entrySequence, indicates to gather with KIn
Non-zero entry number, to obtain ranking resultsThenAll NM are taken at random
Scheme GiContainSet intersection in element conductThe estimated value of coordinate is returned.
By aforesaid operations, the estimation to sparse signal vector magnitude value and coordinate is just completed, maximum amplitude value pair is taken
The AoD value answered completes the wave beam alignment of millimeter-wave communication system.
Embodiment
In the present embodiment, linear antenna array spacingTransmitting terminal number of antennas N=128, rf chain number R
=8, millimeter wave channel vector h (formula (2)) contain K paths, and the value of the non-zero entry of x obeys the distribution of Cyclic Symmetry multiple GaussThe equal general selection at random of the position of x non-zero entry.Each result is 104The mean value of random experiment.Each bigraph Gl's
Right interstitial content M=16, signal-to-noise ratioEnergy detector threshold value ∈=3 σ.
MatrixIt is taken as:
Design based on above-mentioned model and sparse coding matrix A, the present invention provides a kind of efficient robusts without phase solution
Code algorithm carries out wave beam alignment.
Algorithm performance comparative analysis of the related algorithm based on phase decoding with the method for the present invention will be utilized below, with into
One step demonstrate,proves performance of the invention.
Without making an uproar, the correctness restored using success rate (Success Rate) come gauge signal is primary to test
IfIt is considered as successfully.Fig. 4 features success rate and number of measurement values T=2ML under different number of path
Relationship, as can be seen from the figure result of the invention and empirical value are very identical, and when number of path K is smaller, the present invention can
To restore AoD and decline (range value) with higher probability perfection.
When making an uproar, using two kinds of measurement indexs come the performance of metric algorithm.One is for measuring recovery signal
Error, be called normalized mean squared error (Normalized Mean Square Error, NMSE), be defined as
One is the gain generated for measuring beam forming, is defined as:WhereinTo estimate
The corresponding angle in the maximum path of the amplitude of meter.
Fig. 5-a, 5-b describe the method for the present invention (Robust SBG Code) and existing method (Robust Phase
Code) method restores the NMSE under signal in different number of path.From these figures it can be seen that for different path numbers, this
The obtained solution of inventive method has big advantage for related algorithm on NMSE, and remains to provide in low signal-to-noise ratio
Relatively reliable accuracy, and existing method falls flat.Fig. 6-a, 6-b feature the method for the present invention (Robust SBG Code)
Increase from the wave beam that existing method (Robust Phase Code and AgileLink) can be formed at different SNR and timeslot number
Benefit it can be seen from the figure that the present invention can provide bigger beam forming gain, and has stronger robustness for noise,
Since in a practical situation, signal-to-noise ratio when carrying out wave beam alignment is all lower, and the present invention has more practical significance.
Complexity can be both greatly reduced with respect to other algorithms in the present invention, and raising reverts to power, and can provide preferably
Noise robustness has apparent performance advantage compared to other algorithms.
It is to sum up told, invention proposed by the present invention is the millimetre-wave attenuator wave beam pair based on sparse coding and without phase decoding
Quasi- algorithm only relies on the coordinate of range value and sparse signal to restore the required AoD of wave beam alignment, by well-designed sparse
Encoder matrix, using take the means such as intersection carry out without phase decoding, it is only necessary toIt can restore information needed, and in low letter
It makes an uproar and remains to maintain higher robustness than in the case of.
The above description is merely a specific embodiment, any feature disclosed in this specification, except non-specifically
Narration, can be replaced by other alternative features that are equivalent or have similar purpose；Disclosed all features or all sides
Method or in the process the step of, other than mutually exclusive feature and/or step, can be combined in any way.
Claims (3)
1. the millimetre-wave attenuator fast beam alignment methods based on sparse coding and without phase decoding, which is characterized in that including under
Column step；
Step S1: L bigraph G is presetlAnd matrix
Wherein bigraph GlLeft sibling quantity N correspond to number of transmission antennas, right number of nodes M is preset value；
And it is based on bigraph GlObtain the corresponding connection matrix H of each bigraphl, wherein connection matrix HlEach element Hl(i's, j)
Value are as follows:
MatrixWherein ti≠tj, i ≠ j and tn> 0, i, j, n=1,2 ..., N；
Based on matrix HlWithAvailable sparse coding matrix
Step S2: transmitting terminal is based on sparse coding matrix A and carries out signal processing to signal to be sent；
Step S3: receiving end is based on received signal vector and bigraph carries out wave beam registration process:
Step S301: traversing all bigraphs, judges each bigraph GlRight node whether be zero node, and record each bigraph Gl
Zero node number:
Based on each bigraph GlCorresponding received vector yl, to received vector ylEach yl,mPiecemeal processing up and down is carried out, thereon
Piecemeal is correspondingLower piecemeal is corresponding
It willEnergy value be compared with preset threshold value ∈, if being less than, judgement beCorresponding right node is zero section
Point, to obtain bigraph GlZero number of nodes；
Step S302: it is based on L bigraph GlIn zero number of nodes P of minimummin, it is P by zero interstitial contentminBigraph GlIt is defined as
NM figure, to obtain NM set of graphs；
Step S303: all bigraphs in traversal NM set of graphs, and execute lower column processing:
For m=1 ..., M, following judgement is repeated: ifThen by bigraph GlM-th of right node as single node,
And estimate the range value of corresponding activation left siblingWith the coordinate value of sparse signal x
Wherein,{m1…mrIndicate withCorresponding right node is connected
Left sibling set；
All range values based on same NM figureObtain the estimate vector of amplitude zThus after having traversed NM set of graphs, it can
Obtain the set of the estimated value of amplitudeWherein I indicates setRank；
Step S304: judgement if I=1, returnsAs final estimation
If setInterior element intersection is sky, then takes set at randomSome elementAs final estimation
Otherwise, based on each estimate vector in setIn non-zero entryAnd all NM figure G are taken at randomiContainSet
Element conduct in intersectionThe estimated value of coordinate；And according toIt obtains finally estimating corresponding to each non-zero entry
MeterWherein k=1,2 ..., K, K indicate setIn non-zero entry number.
2. the method as described in claim 1, which is characterized in that matrixAre as follows:
3. method according to claim 1 or 2, which is characterized in that threshold value ∈=3 σ, σ indicate that noise criteria is poor.
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| CN112994765A (en) * | 2021-03-04 | 2021-06-18 | 电子科技大学 | Wave beam alignment method of intelligent reflecting surface auxiliary millimeter wave communication system |
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| CN114765852A (en) * | 2021-01-15 | 2022-07-19 | 大唐移动通信设备有限公司 | Positioning angle calibration method and device |
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Cited By (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110519188A (en) * | 2019-08-20 | 2019-11-29 | 电子科技大学 | A kind of compressed sensing based multi-user's time-varying millimeter wave channel estimation methods |
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| CN112543044B (en) * | 2020-11-24 | 2022-02-08 | 电子科技大学 | Millimeter wave beam alignment method based on sparse coding |
| CN114765852A (en) * | 2021-01-15 | 2022-07-19 | 大唐移动通信设备有限公司 | Positioning angle calibration method and device |
| CN112994765A (en) * | 2021-03-04 | 2021-06-18 | 电子科技大学 | Wave beam alignment method of intelligent reflecting surface auxiliary millimeter wave communication system |
| CN112994765B (en) * | 2021-03-04 | 2022-02-08 | 电子科技大学 | Wave beam alignment method of intelligent reflecting surface auxiliary millimeter wave communication system |
| CN113532617A (en) * | 2021-07-13 | 2021-10-22 | 中国人民解放军国防科技大学 | Line spectrum detection method for long-time beam phase statistical characteristics |
| CN113532617B (en) * | 2021-07-13 | 2023-11-03 | 中国人民解放军国防科技大学 | Line spectrum detection method for long-term beam phase statistical characteristics |
| CN113660619A (en) * | 2021-08-20 | 2021-11-16 | 上海无线电设备研究所 | Beam alignment method based on network node coordinate information |
| CN113660619B (en) * | 2021-08-20 | 2023-02-28 | 上海无线电设备研究所 | Beam alignment method based on network node coordinate information |
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