CN109768818B - Large-scale antenna signal space diversity transmitting method based on Doppler inhibition - Google Patents
Large-scale antenna signal space diversity transmitting method based on Doppler inhibition Download PDFInfo
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Abstract
The invention discloses a large-scale antenna space signal diversity transmitting method based on Doppler inhibition, which is characterized in that a transmitting end divides a transmitting signal of a frequency domain into blocks, when enough antennas exist, a channel in each data block can be regarded as time-invariant, and then signal space diversity precoding is carried out; a Doppler suppression method of data block by data block is adopted at a sending end, a sending signal subjected to Doppler frequency shift is subjected to beam forming processing block by block, and fast jump of a channel among data blocks is introduced by introducing random phase block by block into a beam. Through the above two operations, the channel of the receiving end becomes a standard block time-varying channel. Based on this, the present invention is further based on a signal space diversity technique to obtain a channel diversity gain. Compared with the prior art, the invention can effectively utilize the channel diversity gain while inhibiting Doppler spread, and improves the reliability of a wireless communication link.
Description
Technical Field
The invention belongs to the field of high-speed mobile communication, and relates to a large-scale antenna signal space diversity transmitting method based on Doppler inhibition.
Background
Due to the openness of the wireless transmission environment, when signals propagate in the space, phenomena such as reflection, diffraction, scattering, interference and the like are generated, so that the mobile wireless communication is accompanied by the multipath effect. On the one hand, the transmitted signal arrives at the receiving end at different times through different paths in space, and when the delay spread and the sampling interval of the signal are comparable, the signals experiencing different delays are superposed together at the receiving end, which may cause significant inter-symbol interference (ISI); from the frequency domain, frequency selective fading is formed. On the other hand, relative motion between the transmitting end and the receiving end can cause Doppler frequency shift, and because the angles reaching the receiving end are different, the Doppler Frequency Shifts (DFOs) suffered by signals on different paths are different; signals with different Doppler frequency offsets are superposed together at a receiving end to cause the envelope of the signals to change, thereby forming time selective fading. It is this dual selective fading that presents significant difficulties for high-speed mobile wireless communications.
The Orthogonal Frequency Division Multiplexing (OFDM) technology divides a broadband channel into a plurality of parallel narrow-band sub-channels which are overlapped with each other, so that the frequency spectrum efficiency is effectively improved, intersymbol interference is effectively resisted by adding a cyclic prefix, frequency selective fading is converted into multiplicative flat fading on each subcarrier, and the Orthogonal Frequency Division Multiplexing (OFDM) technology becomes a core technology of 5G wireless communication. However, just because the sub-channels overlap each other, the performance of OFDM depends heavily on the orthogonality between different sub-carriers, which is very sensitive to frequency offset. The frequency offset may destroy orthogonality between subcarriers, thereby causing severe inter-subcarrier interference (ICI) to impair the performance of the OFDM system. Therefore, when the OFDM system is adopted in a high-speed mobile communication environment with dual selective fading characteristics, how to cope with multiple doppler frequency offsets is a primary problem.
Disclosure of Invention
The present invention is to solve the above problems in the prior art, and provide a large-scale antenna signal space diversity transmission method based on doppler suppression.
In order to achieve the purpose, the invention adopts the following technical scheme to realize the purpose:
a large-scale antenna signal space diversity transmitting method based on Doppler inhibition comprises the following steps:
the method comprises the following steps: the method comprises the steps that data to be transmitted are partitioned at a transmitting end, and then signal space diversity precoding is carried out on each data subcarrier in a plurality of continuous data blocks;
step two: the signal is subjected to Doppler frequency offset compensation by data blocks at a sending end, then beam forming is carried out by data blocks, and finally the signal is transmitted after being processed by an antenna weighting technology;
step three: the receiving and transmitting channel is assumed to be a Jake model, the transmitting signal passes through the channel to reach the receiving end of the base station, under the ideal condition of a large-scale transmitting antenna, the channel passed by each data block is equivalent to a time-invariant channel, and then the maximum likelihood decoding is utilized to obtain the receiving signal.
The invention is further improved in that the specific process of the step one is as follows:
for a high-speed mobile uplink communication scene, a high-speed train is provided with an M-element large-scale uniform linear array U L A, a base station end adopts a single antenna for receiving, and assuming that an OFDM mode of N subcarriers is adopted, the maximum Doppler frequency caused by the movement of the high-speed train is recorded as fdV/λ, where v and λ denote the moving speed and the radio frequency wavelength, respectively;
assuming that the pilot symbols transmitted by the transmitting end on the pilot subcarriers of each block are all 1, I ∈ I is used for the data subcarriersd，IdA set of subcarrier indices for data subcarriers; each data subcarrier is signal space diversity precoded at consecutive K1, 2.
X(i)＝[X1(i) X2(i) … XK(i)]T
Wherein, x (i) ═ Θ d (i); k is the number of blocks of the transmitted subcarrier dispersion; theta is composed of
The first K rows and K columns of the sub-matrix,
is composed of
The DFT matrix is normalized to the value of the DFT matrix,
d (i) is the original information data symbol of the ith subcarrier.
The invention has the further improvement that the specific process of the step two is as follows:
① phase reversal phi of transmitted signal caused by frequency offset x at time delay tt(x) Is composed of
Wherein f issIs the sampling frequency;
② denote the selected beamforming pointing angle as θqQ is 1,2, …, Q, and the frequency offset of the beamformed signal is-fdcos(θq) And the phase is reversed to phi under the condition of no time delay0(-fdcos(θq) Therefore, the matrix of the transmitted signal N × M of the q-th beam after the signal is beamformed is recorded as:
wherein
Random phase deflection introduced for the beam, a (θ)q) To correspond to an angle thetaqArray steering vector of, skFor the time domain symbols corresponding to the transmit frequency domain block of the kth block,
Xka transmit frequency domain block, X, for the k-th blockk＝[Xk(1) Xk(2)… Xk(N)]T；
③ after the step ②, the transmitted signals are processed by antenna weighting technique to obtain the total multi-antenna transmission signal matrix SkComprises the following steps:
where w is the weight vector of the antenna weights.
The invention has the further improvement that the specific process of the step three is as follows:
the receiving and transmitting channel through which the transmitted signal passes is assumed to be Jake model, and the channel between the receiving and transmitting ends is assumed to contain 1+ LpDefining taps l as 0,1, …, LpWherein the first tap is composed of infinite multipath components ranging from 0 to pi; let the gain of the incident path at the angle θ corresponding to the l-th tap be κl(θ)；
① assume that the receiving end is equipped with a single antenna, and that the received signal vector at the base station for k data blocks is represented as:
wherein Sk(l) Represents the transmit-end signal matrix S in the case of CP extensionkA version shifted by l bits, represented as follows:
wherein
Denotes skCyclically shift down versions of l bits;
transmitting end signal matrix S under CP extension conditionkVersion S with l bits shifted downk(l) Substituted into the received signal vector ykIn (1), obtaining:
② for a large-scale antenna array, considering that when M tends to be large enough, the steering vectors of the corresponding angles are assumed to be orthogonal, and the following vectors are obtained:
under the ideal condition, a transmitting and receiving end is equivalent to pass through a time-invariant channel in a k data block, and fast channel hopping exists between different blocks;
the time domain channel equivalent to the kth block is represented in matrix form as:
hk＝[hk,0hk,1… hk,Lp]T
the corresponding frequency domain channel response is:
frequency domain representation of the received signal:
Yk＝Fyk＝diag(Hk)Xk
for data sub-carrier I ∈ IdFrequency domain representation of the received signal:
Y(i)＝[Y1(i) Y2(i) … YK(i)]T
namely:
Y(i)＝H(i)Θd(i)
wherein H (i) ═ diag (H)1(i) H2(i) … HK(i))；
③ the received signal is obtained by maximum likelihood decoding the signal received by the receiving end.
A further improvement of the present invention is that, in step ②, considering the ideal situation that M tends to be large enough, the transceiving end is equivalent to passing a time-invariant signal in k data blocks, and there is fast channel hopping between different blocks.
In a further development of the invention, in step ③, the maximum likelihood decoding is as follows:
compared with the prior art, the invention has the following beneficial effects:
1) the invention mainly utilizes the wave beam domain Doppler precompensation and the antenna weighting to restrain the Doppler expansion, and can minimize the Doppler expansion to a great extent. When there are enough antennas, the channel within each data block can be considered time invariant. Therefore, the receiving end can realize receiving based on the traditional time-invariant channel estimation and equalization method without time-variant channel estimation tracking and other high-complexity operations.
2) The invention introduces the block-by-block random phase into the wave beam, thereby introducing the fast jump of the channel among the data blocks, and leading the channel of the receiving end to become a standard block time-varying channel. Based on this, the present invention is further based on a signal space diversity technique to obtain a channel diversity gain. Based on the method, the device and the system, the Doppler spread can be inhibited, the channel diversity gain can be effectively utilized, and the reliability of a wireless communication link is improved.
Drawings
FIG. 1 is a block diagram of a system model employed by the present invention;
fig. 2 is a block diagram illustrating an optimal antenna weighting technique employed in the present invention;
fig. 3 is a schematic representation of SER performance for the present invention versus a comparative scheme.
Detailed Description
The invention is described in further detail below with reference to the accompanying drawings:
the method of the invention comprises the following steps:
the method comprises the following steps: the method comprises the following steps of partitioning data to be transmitted at a transmitting end, and then carrying out signal space diversity precoding on each data subcarrier in a plurality of continuous data blocks, wherein the specific process is as follows:
considering the high-speed mobile uplink communication scene, a high-speed train is provided with an M-element large-scale uniform linear array U L A, a base station end adopts a single antenna for receiving, an OFDM mode adopting N subcarriers is assumed, and the maximum Doppler frequency brought by high-speed rail movement is recorded as fdV/λ. Where v and λ denote the moving speed and the radio frequency wavelength, respectively.
It is assumed that the transmitting end transmits pilot symbols all 1 at the pilot subcarriers of each block. The following symbols are defined:
Id: a set of subcarrier indices for the data subcarriers;
k: the number of blocks of transmitted sub-carrier dispersion;
d (i): original information data symbols of the ith subcarrier;
Θ: by
The first K rows and K columns of the array form a sub-matrix.
Xk: transmitting frequency domain block, X, of the kth blockk＝[Xk(1) Xk(2) … Xk(N)]T；
sk: the time domain symbols corresponding to the transmit frequency domain blocks of the kth block,
for I ∈ IdEach data subcarrier is signal space diversity precoded at consecutive K1, 2., K blocks:
X(i)＝[X1(i) X2(i) … XK(i)]T
wherein x (i) ═ Θ d (i).
Step two: the signal carries out Doppler frequency offset compensation by data blocks at a sending end; then, carrying out beam forming by data blocks; finally, the antenna weighting technology is carried out for processing and then the antenna is transmitted; the specific process is as follows:
① phase reversal phi of transmitted signal caused by frequency offset x at time delay tt(x) Is composed of
Wherein f issIs the sampling frequency.
② denote the selected beamforming pointing angle as θqQ is 1,2, …, Q, and the frequency offset of the beamformed signal is-fdcos(θq) And the phase is reversed to phi under the condition of no time delay0(-fdcos(θq) ). the matrix of transmitted signals N × M of the q-th beam after the signals are formed into the beam is recorded as:
wherein
Random phase deflection introduced to the beam. Note that each block independently introduces a random phase. a (theta)q) To correspond to an angle thetaqThe array steering vector. H denotes conjugate transpose.
③ after the step ②, the transmit signal is processed by antenna weighting technique, and the total multi-antenna transmit signal matrix is recorded as:
where w is the weight vector of the antenna weights.
Step three: the receiving and transmitting channel is assumed as a Jake model, and a transmitting signal reaches a receiving end of a base station through the channel; under the ideal condition of a large-scale transmitting antenna, a channel passed by each data block is equivalent to a time-invariant channel, and then a received signal is obtained by utilizing maximum likelihood decoding. The specific process is as follows:
the channel through which the transmitted signal passes is assumed to be of the Jake model, and the channel between the transmitting and receiving ends is assumed to contain 1+ LpDefine tap l as 0,1, …, Lp. Where the first tap is made up of an infinite number of multipath components ranging from 0 to pi. Let the gain of the incident path at the angle θ corresponding to the l-th tap be κl(θ)。
① assume that the receiving end is equipped with a single antenna, the received signal vector for k data blocks at its base station can be expressed as:
wherein Sk(l) Represents the transmit-end signal matrix S in the case of CP extensionkA version shifted by l bits, represented as follows:
wherein
Denotes skThe l bit shifted down versions are cycled.
Therefore, the above-mentioned transmitting end signal matrix S in the case of CP extensionkVersion S with l bits shifted downk(l) Substituted into the received signal vector ykIn (1), obtaining:
② the model proposed by the invention is a large-scale antenna array, and for M antennas, considering that M tends to be large enough, the steering vectors of the corresponding angles are assumed to be orthogonal.
It can be seen that in this ideal case, the transceiving end is equivalent to passing a time-invariant signal in the k data block. And fast channel hopping exists between different blocks.
The time domain channel equivalent to the kth block can be represented in matrix form as:
the corresponding frequency domain channel response is:
frequency domain representation of the received signal:
Yk＝Fyk＝diag(Hk)Xk
for data sub-carrier I ∈ IdFrequency domain representation of the received signal:
Y(i)＝[Y1(i) Y2(i) … YK(i)]T
namely:
Y(i)＝H(i)Θd(i)
wherein H (i) ═ diag (H)1(i) H2(i) … HK(i))
③, maximum likelihood decoding is carried out to the signal received by the receiving end, the maximum likelihood decoding is as follows:
the present invention is described in detail below by way of an example.
Referring to fig. 1, in the high-speed mobile uplink communication scene of the invention, a high-speed train is provided with an M-element large-scale uniform linear array U L A, a base station end adopts a single antenna for receiving, and a wireless channel model assumes a Jake channel.
Fig. 2 is a block diagram illustrating an optimal antenna weighting technique employed in the present invention. Referring to fig. 2, the specific process of step two is as follows:
① after Doppler frequency shift compensation, the phase of the transmission signal is inverted by frequency offset x under time delay t
Wherein f issIs the sampling frequency.
② the Doppler shift compensated signal is beamformed, the selected beamforming pointing angle is noted as θqQ is 1,2, …, Q, the matrix of the transmitted signal N × M of the qth beam after the signal is beamformed is recorded as:
wherein
Random phase deflection introduced to the beam. Note that each block independently introduces a random phase. a (theta)q) To correspond to an angle thetaqThe array steering vector.
③ after the step ②, the transmit signal is processed by antenna weighting technique, and the total multi-antenna transmit signal matrix is recorded as:
fig. 3 is a schematic diagram of SER performance of a large-scale antenna signal space diversity transmission method based on doppler suppression and a conventional comparison method (i.e., a doppler suppression-free method and a common doppler suppression method) provided by the present invention, the parameters are set such that an M64U L a antenna is adopted on a high-speed moving train, the number of subcarriers N is 1024, a radio frequency carrier 5.5ghz, a high-speed rail moving speed 540Km/h, an OFDM symbol rate of 15.36mhz, a channel is assumed to be a Jake model, it is assumed that 64 pilot subcarriers are simulated in each data block at equal intervals for channel estimation, the pilot symbols are all 1, and the data symbols are 16 qam.
The above-mentioned contents are only for illustrating the technical idea of the present invention, and the protection scope of the present invention is not limited thereby, and any modification made on the basis of the technical idea proposed by the present invention falls within the protection scope of the claims of the present invention.
Claims (3)
1. A large-scale antenna signal space diversity transmitting method based on Doppler inhibition is characterized by comprising the following steps:
the method comprises the following steps: the method comprises the steps that data to be transmitted are partitioned at a transmitting end, and then signal space diversity precoding is carried out on each data subcarrier in a plurality of continuous data blocks;
step two: the signal is subjected to Doppler frequency offset compensation by data blocks at a sending end, then beam forming is carried out by data blocks, and finally the signal is transmitted after being processed by an antenna weighting technology;
step three: the receiving and transmitting channel is assumed to be a Jake model, the transmitting signal passes through the channel to reach the receiving end of the base station, under the ideal condition of a large-scale transmitting antenna, the channel passed by each data block is equivalent to a time-invariant channel, and then the maximum likelihood decoding is utilized to obtain the receiving signal;
the specific process of the step one is as follows:
for a high-speed mobile uplink communication scene, a high-speed train is provided with an M-element large-scale uniform linear array U L A, a base station end adopts a single antenna for receiving, and assuming that an OFDM mode of N subcarriers is adopted, the maximum Doppler frequency caused by the movement of the high-speed train is recorded as fdV/λ, where v and λ denote the moving speed and the radio frequency wavelength, respectively;
the pilot frequency symbols transmitted by the transmitting terminal on the pilot frequency sub-carriers of each block are all assumed to be 1; for data sub-carriers
A set of subcarrier indices for data subcarriers; each data subcarrier is signal space diversity precoded at consecutive K1, 2.
X(i)＝[X1(i) X2(i) … XK(i)]T
Wherein, x (i) ═ Θ d (i); k is the number of blocks of the transmitted subcarrier dispersion; theta is composed of
The first K rows and K columns of the sub-matrix,
is composed of
The DFT matrix is normalized to the value of the DFT matrix,
d (i) is the original information data symbol of the ith subcarrier;
the specific process of the second step is as follows:
① phase reversal phi of transmitted signal caused by frequency offset x at time delay tt(x) Is composed of
Wherein f issIs the sampling frequency;
② denote the selected beamforming pointing angle as θqQ is 1,2, …, Q, and the frequency offset of the beamformed signal is-fdcos(θq) And the phase is reversed to phi under the condition of no time delay0(-fdcos(θq) Therefore, the matrix of the transmitted signal N × M of the q-th beam after the signal is beamformed is recorded as:
wherein
Random phase deflection introduced for the beam, a (θ)q) To correspond to an angle thetaqArray steering vector of, skFor the time domain symbols corresponding to the transmit frequency domain block of the kth block,
Xka transmit frequency domain block, X, for the k-th blockk＝[Xk(1) Xk(2) …Xk(N)]T；
③ after the step ②, the transmitted signals are processed by antenna weighting technique to obtain the total multi-antenna transmission signal matrix SkComprises the following steps:
wherein w is a weight vector of antenna weighting;
the concrete process of the third step is as follows:
the receiving and transmitting channel through which the transmitted signal passes is assumed to be Jake model, and the channel between the receiving and transmitting ends is assumed to contain 1+ LpDefining taps l as 0,1, …, LpWherein the first tap is composed of infinite multipath components ranging from 0 to pi; let the gain of the incident path at the angle θ corresponding to the l-th tap be κl(θ)；
① assume that the receiving end is equipped with a single antenna, and that the received signal vector at the base station for k data blocks is represented as:
wherein Sk(l) Represents the transmit-end signal matrix S in the case of CP extensionkA version shifted by l bits, represented as follows:
wherein
Denotes skCyclically shift down versions of l bits;
transmitting end signal matrix S under CP extension conditionkVersion S with l bits shifted downk(l) Substituted into the received signal vector ykIn (1), obtaining:
② for a large-scale antenna array, considering that when M tends to be large enough, the steering vectors of the corresponding angles are assumed to be orthogonal, and the following vectors are obtained:
under the ideal condition, a transmitting and receiving end is equivalent to pass through a time-invariant channel in a k data block, and fast channel hopping exists between different blocks;
the time domain channel equivalent to the kth block is represented in matrix form as:
the corresponding frequency domain channel response is:
frequency domain representation of the received signal:
Yk＝Fyk＝diag(Hk)Xk
for data sub-carriers
Frequency domain representation of the received signal:
Y(i)＝[Y1(i) Y2(i) … YK(i)]T
namely:
Y(i)＝H(i)Θd(i)
wherein H (i) ═ diag (H)1(i) H2(i) … HK(i))；
③ the received signal is obtained by maximum likelihood decoding the signal received by the receiving end.
2. The method of claim 1, wherein in step ②, considering the ideal situation that M tends to be large enough, the transceiving end is equivalent to passing a time-invariant signal in k data blocks, and there is fast channel hopping between different blocks.
3. The method for massive antenna signal space diversity transmission based on doppler suppression as claimed in claim 1, wherein in step ③, the maximum likelihood decoding is as follows:
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| CN103888168A (en) * | 2012-12-21 | 2014-06-25 | 中国科学院声学研究所 | Doppler compensation method for synthetic aperture underwater acoustic communication and system |
| CN103986675A (en) * | 2013-08-20 | 2014-08-13 | 广东工业大学 | Carrier wave frequency offset estimation algorithm for orthogonal frequency division multiplexing system under quick-change channel condition |
| WO2015037943A1 (en) * | 2013-09-15 | 2015-03-19 | Lg Electronics Inc. | Broadcast receiving device and method for operating the same |
| CN107925895A (en) * | 2015-08-17 | 2018-04-17 | 瑞典爱立信有限公司 | Mobility reference signal is distributed |
| CN108400853A (en) * | 2017-02-06 | 2018-08-14 | 中兴通讯股份有限公司 | Configuration method, configuration device and the communication node of reference signal |
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| US10462801B2 (en) * | 2017-05-05 | 2019-10-29 | At&T Intellectual Property I, L.P. | Multi-antenna transmission protocols for high doppler conditions |
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| CN103888168A (en) * | 2012-12-21 | 2014-06-25 | 中国科学院声学研究所 | Doppler compensation method for synthetic aperture underwater acoustic communication and system |
| CN103986675A (en) * | 2013-08-20 | 2014-08-13 | 广东工业大学 | Carrier wave frequency offset estimation algorithm for orthogonal frequency division multiplexing system under quick-change channel condition |
| WO2015037943A1 (en) * | 2013-09-15 | 2015-03-19 | Lg Electronics Inc. | Broadcast receiving device and method for operating the same |
| CN107925895A (en) * | 2015-08-17 | 2018-04-17 | 瑞典爱立信有限公司 | Mobility reference signal is distributed |
| CN108400853A (en) * | 2017-02-06 | 2018-08-14 | 中兴通讯股份有限公司 | Configuration method, configuration device and the communication node of reference signal |
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