CN109586777B - Codebook generation and transceiving cooperative adaptive beam training method with analytic structure - Google Patents

Codebook generation and transceiving cooperative adaptive beam training method with analytic structure Download PDF

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CN109586777B
CN109586777B CN201910054980.6A CN201910054980A CN109586777B CN 109586777 B CN109586777 B CN 109586777B CN 201910054980 A CN201910054980 A CN 201910054980A CN 109586777 B CN109586777 B CN 109586777B
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code word
codebook
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codeword
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CN109586777A (en
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张华�
张仁民
许威
赵春明
尤肖虎
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Southeast University
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0617—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal for beam forming
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
    • H04B7/0842—Weighted combining
    • H04B7/086—Weighted combining using weights depending on external parameters, e.g. direction of arrival [DOA], predetermined weights or beamforming

Abstract

The invention provides a codebook generation and transceiving cooperative adaptive beam training method with an analytic structure, which comprises a PS-DFT multi-precision codebook generation algorithm and an adaptive beam training algorithm, wherein the multi-precision codebook has an analog/digital mixed structure: DFT basic sub-beams on the array are generated by an analog radio frequency assembly, and the selection of the sub-beams, the phase adjustment among the sub-beams and the power distribution are realized by a digital baseband assembly; the adaptive beam training algorithm adaptively selects an initial stage and an end stage of beam training according to different transmission signal-to-noise ratios and coherence times. The invention has low hardware realization complexity, flat in-band wave beam, high angle estimation accuracy and high effective spectrum efficiency, is suitable for a millimeter wave large-scale antenna point-to-point wireless communication system with two communication parties adopting a full-connection hybrid precoding structure, and the arrays used at the transmitting side and the receiving side are uniform linear arrays of half-wave antenna spacing.

Description

Codebook generation and transceiving cooperative adaptive beam training method with analytic structure
Technical Field
The invention belongs to the technical field of wireless communication, and particularly relates to a PS-DFT codebook generation and transceiver cooperation adaptive beam training method with an analytic structure.
Background
In the last decade, millimeter wave (mmWave) and sub-terahertz (sub-THz) band communication has attracted extensive attention in academia and industry due to its abundant spectrum resources. In order to solve the problem of increased transmission loss caused by high frequency band, the erection of large-scale antenna arrays at the transmitting and receiving ends becomes an effective countermeasure and a necessary choice. However, as the number of antennas increases dramatically, channel estimation is challenging. Based on the consideration of hardware complexity and channel estimation overhead, the traditional channel estimation strategy of MIMO with multiple inputs and outputs is unrealistic to be used in mmWave and sub-THz communication systems. Considering the sparsity of the transmission characteristics of the high-frequency band channel, beam training in the radio frequency band is a compromise and feasible strategy.
To further reduce the overhead of searching the codebook, the industry and academia have proposed a hierarchical search scheme based on a multi-precision codebook-the time overhead of beam alignment can be reduced to the order of a logarithm of the number of antennas. The angle estimation accuracy of the hierarchical search beam training depends mainly on the codebook performance for training. A good codebook requires good flatness in-band, suppression of leakage as much as possible out-of-band, and a fast convergence rate in the transition band. However, when the Radio-Frequency (RF) chain is limited, there is a great technical difficulty in simultaneously pursuing these technical criteria.
Meanwhile, the angle estimation accuracy of hierarchical search based on the multi-precision codebook is not linear with the increase of the transmission signal-to-noise ratio, and especially, a basin effect exists at the time of (extremely) low transmission signal-to-noise ratio (when the total transmission power is limited, the final angle estimation accuracy is not obviously increased with the increase of the transmission signal-to-noise ratio due to the extremely low receiving signal-to-noise ratio caused by the large coverage of the initial training beam). To ensure sufficient angle estimation accuracy, it is inevitable to select a higher codebook layer as an initial stage of hierarchical search under low snr conditions. However, searching in a higher layer codebook implies a larger search time overhead, which in turn leads to a reduction in effective spectral efficiency. Therefore, there is a contradiction between high angle estimation accuracy and low training overhead.
Disclosure of Invention
In order to solve the problems, the invention discloses a PS-DFT codebook generation and transceiver cooperation adaptive beam training method with an analytic structure, which can effectively improve the accuracy and the effective spectrum efficiency of beam training. The method comprises a PS-DFT multi-precision codebook generation algorithm and an adaptive beam training algorithm, wherein the multi-precision codebook has an analog/digital mixed structure: DFT basic sub-beams on the array are generated by an analog radio frequency assembly, and the selection of the sub-beams, the phase adjustment among the sub-beams and the power distribution are realized by a digital baseband assembly; the adaptive beam training algorithm adaptively selects an initial stage and an end stage of beam training according to different transmission signal-to-noise ratios and coherence times.
In order to achieve the purpose, the invention provides the following technical scheme:
the codebook generating and transceiving cooperative adaptive beam training method with the analytic structure comprises the following steps:
(1) determining the number of layers of the multi-precision codebook according to the number R of radio frequency chains
Figure BDA0001952125600000021
Then, according to the number N of the antennas of the uniform linear array, a digital codebook in the multi-precision codebook is determined
Figure BDA0001952125600000022
And an analog codebook
Figure BDA0001952125600000023
Are respectively R × S and S × N × N × R, and are respectively initialized to
Figure BDA0001952125600000024
(2) Digital codebook for generating PS-DFT multi-precision codebook layer by layer from S-1 layer to S-S layer
Figure BDA0001952125600000025
And an analog codebook
Figure BDA0001952125600000026
(3) According to false alarm probability PFASignal to noise ratio of transmission
Figure BDA0001952125600000027
Radio frequency chain number R, antenna number N and angle support domain DAS＝[ΦAS,min,ΦAS,max) Predicting the optimal initial level for a given transmission signal-to-noise ratio by the coherence time T
Figure BDA0001952125600000028
Codeword range [ i ] for optimal initial level searchmin,imax]And an optimal termination level
Figure BDA0001952125600000029
(4) In that
Figure BDA00019521256000000210
Layer codeword range of [ i ]min,imax]Performing finite search in the interval, and finding out the code word serial number of the receiving end corresponding to the maximum receiving power by the receiving end
Figure BDA00019521256000000211
And code word serial number of the transmitting end
Figure BDA00019521256000000212
And will be
Figure BDA00019521256000000213
Feeding back to the sending end through a feedback channel;
(5) from the first
Figure BDA00019521256000000214
Layer start to layer
Figure BDA00019521256000000215
Layer-by-layer hierarchical search is carried out, and the receiving end updates the maximum receiving power after the search of each layer is finished
Figure BDA00019521256000000216
And feed back the current
Figure BDA00019521256000000217
Sending the data to a sending end;
(6) for both transmitting and receiving sides respectively
Figure BDA00019521256000000218
And
Figure BDA00019521256000000219
the number words configure the beamforming matrix and the beam combining matrix.
Further, the step (2) comprises the following sub-steps:
(21) calculating configuration parameters for the current s-th layer: configuring the number of active radio frequency chains of the current layer as
Figure BDA00019521256000000220
Each codeword has a beam width of
Figure BDA00019521256000000221
Number of code words is Is＝2/Bs；
(22) Constructing a first analog codeword for a current s-th layer
Figure BDA00019521256000000222
And digital code word
Figure BDA00019521256000000223
First analog code word
Figure BDA00019521256000000224
Is configured as
Figure BDA00019521256000000225
Wherein
Figure BDA00019521256000000226
a (N, phi) is an array weighting vector with length N pointing to phi; if it is
Figure BDA00019521256000000227
The first digital code word is configured as
Figure BDA00019521256000000228
If it is
Figure BDA00019521256000000229
The first digital code word is configured as
Figure BDA00019521256000000230
Wherein j is an imaginary unit,
Figure BDA00019521256000000231
otherwise, the first digital code word is configured as
Figure BDA00019521256000000232
Wherein
Figure BDA00019521256000000233
Figure BDA00019521256000000234
(23) The first analog code word of the s-th layer constructed by the step (22)
Figure BDA0001952125600000031
And a first digital code word
Figure BDA0001952125600000032
Generating an arbitrary ith analog codeword for the layer
Figure BDA0001952125600000033
And digital code word
Figure BDA0001952125600000034
Wherein I is more than or equal to 1 and less than or equal to Is: the ith analog codeword is
Figure BDA0001952125600000035
Wherein the operator [ ] is Hadamard product, the ith digital codeword is
Figure BDA0001952125600000036
(24) If S is equal to S, performing step (3); otherwise, s is s +1 and returns to (21).
Further, the step (3) comprises the following sub-steps:
(31) initializing path gain to | αLS|＝1；
(32) According to the formula
Figure BDA0001952125600000037
Determining an optimal initial stage
Figure BDA0001952125600000038
And then determine the first
Figure BDA0001952125600000039
The beam bandwidth of the code word in the layer is
Figure BDA00019521256000000310
(33) According to angle support domain DAS＝[ΦAS,min,ΦAS,max) Determine it is in
Figure BDA00019521256000000311
Corresponding codeword range [ i ] within a layermin,imax]And time overhead of initial stage search
Figure BDA00019521256000000312
Wherein
Figure BDA00019521256000000313
(34) Determining an optimal termination level
Figure BDA00019521256000000314
Value range at the end level
Figure BDA00019521256000000315
In particular, the predicted maximum effective spectral efficiency is found
Figure BDA00019521256000000316
Corresponding termination stage sLAs an optimal termination level, wherein
Figure BDA00019521256000000317
Is the total time overhead.
Compared with the prior art, the invention has the following advantages and beneficial effects:
1. because the analog radio frequency assembly is configured into an equal-length DFT array weighting vector form, the hardware implementation complexity of the invention is low.
2. The invention flattens the in-band beam as the phase coupling between the sub-beams is effectively adjusted by the digital baseband assembly.
3. The receiving signal-to-noise ratio is ensured through the adaptive beam training, and the angle estimation accuracy is high.
4. The training sequence is optimized through the adaptive beam training algorithm, so that the effective spectrum efficiency is high.
5. Experiments prove that the method has an approximately ideal beam pattern and higher effective spectrum efficiency compared with other methods, is suitable for a millimeter wave large-scale antenna point-to-point wireless communication system with a fully-connected hybrid precoding structure adopted by two communication parties, and the arrays used at the transmitting side and the receiving side are uniform linear arrays of half-wave antenna spacing.
Drawings
FIG. 1 is a schematic diagram of a system architecture for implementing the present invention.
Fig. 2 is a diagram illustrating beam pattern effects in an embodiment of the invention.
Fig. 3 is a diagram of the effective spectrum efficiency effect obtained by the embodiment of the present invention and other training methods.
Detailed Description
In order that those skilled in the art will better understand the technical solution of the present invention, the following detailed description will be given with reference to specific examples, which should be understood as merely illustrative of the present invention and not as limiting the scope of the present invention.
The invention relates to a method for improving effective transmission rate by considering Beam training (Beam training) time overhead in a point-to-point Frequency Division Duplex (FDD) millimeter wave (mmWave) large-scale antenna (Massive MIMO) full-connection structure communication system.
As shown in fig. 1, R-8 rf chains are arranged on both sides of the transceiver in this example, and the uniform linear array with half-wavelength spacing includes N-32 antennas.
The invention provides a codebook generation and transceiving cooperative adaptive beam training method with an analytic structure, which comprises the following steps:
(1) determining the layer number of the multi-precision codebook according to the number R of the radio frequency chains being 8
Figure BDA00019521256000000420
And then determining a digital codebook in the multi-precision codebook according to the number N of the antennas of the uniform linear array which is 32
Figure BDA0001952125600000041
And an analog codebook
Figure BDA0001952125600000042
Are respectively initialized to R × S ═ 8 × 4 and S × N × R ═ 4 × 32 × 32 × 8
Figure BDA0001952125600000043
And
Figure BDA0001952125600000044
(2) digital codebook for generating PS-DFT multi-precision codebook layer by layer from s-1 layer to s-4 layer
Figure BDA0001952125600000045
And an analog codebook
Figure BDA0001952125600000046
The implementation method takes s-3 as an example to explain the implementation process of the step (2), and specifically comprises the following substeps:
(21) calculating configuration parameters for the current s-3 th layer: the number of active RF chains in the current layer is
Figure BDA0001952125600000047
Each codeword has a beam width of B s＝31/8, the number of codewords is Is＝3＝16；
(22) Constructing a first analog codeword for the current s-3 th layer
Figure BDA0001952125600000048
And digital code word
Figure BDA0001952125600000049
First analog code word
Figure BDA00019521256000000410
Is configured as
Figure BDA00019521256000000411
Wherein r is more than or equal to 1 and less than or equal to 2; due to the fact that
Figure BDA00019521256000000412
So that the first digital code word is
Figure BDA00019521256000000413
Wherein j is an imaginary unit,
Figure BDA00019521256000000419
in this embodiment, the curve labeled "s ═ 3" in fig. 2 is obtained.
(23) The first analog codeword constructed by step (22)
Figure BDA00019521256000000415
And a first digital code word
Figure BDA00019521256000000416
Generating an arbitrary ith analog codeword for the layer
Figure BDA00019521256000000417
And digital code word
Figure BDA00019521256000000418
Wherein i is more than or equal to 1 and less than or equal to 16: the ith analog codeword is
Figure BDA0001952125600000051
The ith digital code word is
Figure BDA0001952125600000052
(24) Since S is 3 ≠ S is 4, S +1 is 4 and returns to (21); the other 3 curves in fig. 2 were obtained in this embodiment.
(3) According to false alarm probability PFA0.01, transmission signal-to-noise ratio
Figure BDA0001952125600000053
The range is [ -10dB,20 dB)]The number of radio frequency chains R is 8, the number of antennas N is 32, and an angle support domain DAS＝[ΦAS,min,ΦAS,max) The best initial level under different transmission signal-to-noise ratios is predicted by [ -1,1) and the coherence time T ═ 250
Figure BDA0001952125600000054
Codeword range [ i ] for optimal initial level searchmin,imax]And an optimal termination level
Figure BDA0001952125600000055
The step (3) specifically comprises the following substeps:
(31) initializing path gain to | αLS|＝1；
(32) According to the formula
Figure BDA0001952125600000056
Determining an optimal initial stage
Figure BDA0001952125600000057
And then determine the first
Figure BDA0001952125600000058
The beam bandwidth of the code word in the layer is
Figure BDA0001952125600000059
(33) According to angle support domain DAS[ -1,1), i.e. the physical angular distribution interval is [ -pi/2, pi/2), determined at
Figure BDA00019521256000000510
Corresponding codeword range [ i ] within a layermin,imax]And time overhead of initial stage search
Figure BDA00019521256000000511
Wherein
Figure BDA00019521256000000512
(34) Determining an optimal termination level
Figure BDA00019521256000000513
Value range at the end level
Figure BDA00019521256000000514
Finding predicted maximum effective spectral efficiency
Figure BDA00019521256000000515
Corresponding termination stage sLAs an optimal termination level, wherein
Figure BDA00019521256000000516
Is the total time overhead;
(4) in that
Figure BDA00019521256000000517
Layer codeword range of [ i ]min,imax]Performing finite search in the interval, and finding out the code word serial number of the receiving end corresponding to the maximum receiving power by the receiving end
Figure BDA00019521256000000518
And code word serial number of the transmitting end
Figure BDA00019521256000000519
And will be
Figure BDA00019521256000000520
Feeding back to the sending end through a feedback channel;
(5) from the first
Figure BDA00019521256000000521
Layer start to layer
Figure BDA00019521256000000522
Layer-by-layer hierarchical search is carried out, and the receiving end updates the maximum receiving power after the search of each layer is finished
Figure BDA00019521256000000523
And feed back the current
Figure BDA00019521256000000524
Sending the data to a sending end;
(6) for both transmitting and receiving sides respectively
Figure BDA00019521256000000525
And
Figure BDA00019521256000000526
the number words configure the beamforming matrix and the beam combining matrix.
The above embodiment, which results from the curve labeled "deployed" as shown in fig. 3, was tested in comparison with the training scheme using the fixed initial level and fixed end level searches, and the remaining curves were the training schemes using the fixed initial level and fixed end level searches. In this embodiment, the present invention has a signal-to-noise ratio range of
Figure BDA00019521256000000527
And
Figure BDA00019521256000000528
respectively adaptively selecting beam training orders
Figure BDA00019521256000000529
This example shows that: compared with the existing beam training scheme, the method has the advantages of approximate ideal beam pattern and higher effective spectrum efficiency.
The technical means disclosed in the invention scheme are not limited to the technical means disclosed in the above embodiments, but also include the technical scheme formed by any combination of the above technical features. It should be noted that those skilled in the art can make various improvements and modifications without departing from the principle of the present invention, and such improvements and modifications are also considered to be within the scope of the present invention.

Claims (1)

1. The codebook generation and transceiving cooperative adaptive beam training method with the analysis structure is characterized by comprising the following steps of:
(1) determining the number of layers of the multi-precision codebook according to the number R of radio frequency chains
Figure FDA0003027062160000011
Then, according to the number N of the antennas of the uniform linear array, a digital codebook in the multi-precision codebook is determined
Figure FDA0003027062160000012
And an analog codebook
Figure FDA0003027062160000013
Are respectively R × S and S × N × N × R, and are respectively initialized to
Figure FDA0003027062160000014
And
Figure FDA0003027062160000015
(2) digital codebook for generating PS-DFT multi-precision codebook layer by layer from S-1 layer to S-S layer
Figure FDA0003027062160000016
And an analog codebook
Figure FDA0003027062160000017
The method comprises the following substeps:
(21) computing configuration parameters for the current s-th layerNumber: configuring the number of active radio frequency chains of the current layer as
Figure FDA0003027062160000018
Each codeword has a beam width of
Figure FDA0003027062160000019
Number of code words is Is＝2/Bs；
(22) Constructing a first analog codeword for a current s-th layer
Figure FDA00030270621600000110
And digital code word
Figure FDA00030270621600000111
First analog code word
Figure FDA00030270621600000112
Is configured as
Figure FDA00030270621600000113
Wherein
Figure FDA00030270621600000114
a (N, phi) is an array weighting vector with length N pointing to phi; if it is
Figure FDA00030270621600000115
The first digital code word is configured as
Figure FDA00030270621600000116
If it is
Figure FDA00030270621600000117
The first digital code word is configured as
Figure FDA00030270621600000118
Where j is the imaginary unit，
Figure FDA00030270621600000119
Otherwise, the first digital code word is configured as
Figure FDA00030270621600000120
Wherein
Figure FDA00030270621600000121
(23) The first analog code word of the s-th layer constructed by the step (22)
Figure FDA00030270621600000122
And a first digital code word
Figure FDA00030270621600000123
Generating an arbitrary ith analog codeword for the layer
Figure FDA00030270621600000124
And digital code word
Figure FDA00030270621600000125
Wherein I is more than or equal to 1 and less than or equal to Is: the ith analog codeword is
Figure FDA00030270621600000126
Wherein the operator [ ] is Hadamard product, the ith digital codeword is
Figure FDA00030270621600000127
(24) If S is equal to S, performing step (3); otherwise, s is s +1 and returns to (21);
(3) according to false alarm probability PFASignal to noise ratio of transmission
Figure FDA00030270621600000128
Radio frequencyNumber of chains R, number of antennas N, angle support domain DAS＝[ΦAS,min,ΦAS,max) Predicting the optimal initial level for a given transmission signal-to-noise ratio by the coherence time T
Figure FDA00030270621600000129
Codeword range [ i ] for optimal initial level searchmin,imax]And an optimal termination level
Figure FDA0003027062160000021
The method comprises the following substeps:
(31) initializing path gain to | αLS|＝1；
(32) According to the formula
Figure FDA0003027062160000022
Determining an optimal initial stage
Figure FDA0003027062160000023
And then determine the first
Figure FDA0003027062160000024
The beam bandwidth of the code word in the layer is
Figure FDA0003027062160000025
(33) According to angle support domain DAS＝[ΦAS,min,ΦAS,max) Determine it is in
Figure FDA0003027062160000026
Corresponding codeword range [ i ] within a layermin,imax]And time overhead of initial stage search
Figure FDA0003027062160000027
Wherein
Figure FDA0003027062160000028
(34)Determining an optimal termination level
Figure FDA0003027062160000029
Value range at the end level
Figure FDA00030270621600000210
In particular, the predicted maximum effective spectral efficiency is found
Figure FDA00030270621600000211
Corresponding termination stage sLAs an optimal termination level, wherein
Figure FDA00030270621600000212
Is the total time overhead;
(4) in that
Figure FDA00030270621600000213
Layer codeword range of [ i ]min,imax]Performing finite search in the interval, and finding out the code word serial number of the receiving end corresponding to the maximum receiving power by the receiving end
Figure FDA00030270621600000214
And code word serial number of the transmitting end
Figure FDA00030270621600000215
And will be
Figure FDA00030270621600000216
Feeding back to the sending end through a feedback channel;
(5) from the first
Figure FDA00030270621600000217
Layer start to layer
Figure FDA00030270621600000218
Layer-by-layer hierarchical search is carried out, and the receiving end updates the maximum receiving power after the search of each layer is finished
Figure FDA00030270621600000219
And feed back the current
Figure FDA00030270621600000220
Sending the data to a sending end;
(6) for both transmitting and receiving sides respectively
Figure FDA00030270621600000221
And
Figure FDA00030270621600000222
the number words configure the beamforming matrix and the beam combining matrix.
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