CN109286587B - Multi-active generalized spatial modulation detection method - Google Patents

Multi-active generalized spatial modulation detection method Download PDF

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CN109286587B
CN109286587B CN201811297299.6A CN201811297299A CN109286587B CN 109286587 B CN109286587 B CN 109286587B CN 201811297299 A CN201811297299 A CN 201811297299A CN 109286587 B CN109286587 B CN 109286587B
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CN109286587A (en
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冯兴乐
段国彬
王相相
牛晓珂
朱文霞
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Shaanxi Qiteng Electronic Technology Co.,Ltd.
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03891—Spatial equalizers
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0868—Hybrid systems, i.e. switching and combining
    • H04B7/0874—Hybrid systems, i.e. switching and combining using subgroups of receive antennas
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0045—Arrangements at the receiver end
    • H04L1/0047—Decoding adapted to other signal detection operation
    • H04L1/0048—Decoding adapted to other signal detection operation in conjunction with detection of multiuser or interfering signals, e.g. iteration between CDMA or MIMO detector and FEC decoder
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
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    • H04L1/0054—Maximum-likelihood or sequential decoding, e.g. Viterbi, Fano, ZJ algorithms
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
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    • H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity

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Abstract

The invention discloses a multi-active generalized spatial modulation detection method, which comprises the steps of utilizing zero forcing linear equalization to detect all possible activated antenna combinations, obtaining corresponding Euclidean distances according to information bits after each group of equalization, then sequencing the Euclidean distances, using the antenna combination with the minimum Euclidean distance as an activated antenna index, judging whether partial maximum likelihood detection is carried out on the antenna combination according to a threshold value, and detecting adjacent constellation points after equalization to obtain constellation modulation symbols. The invention separately detects the antenna index and the constellation symbol, greatly reduces the complexity of the algorithm, in addition, after the constellation symbol is roughly detected by zero forcing equalization, whether the constellation symbol is further detected or not is judged by setting a threshold value, and the detection performance of the method is improved while the complexity is reduced.

Description

Multi-active generalized spatial modulation detection method
Technical Field
The invention belongs to the technical field of communication, and particularly relates to a multi-active generalized spatial modulation detection method based on zero-forcing equalization and partial maximum likelihood.
Background
In the Multiple-Input Multiple-Output (MIMO) technology, Multiple antennas are arranged at a transmitting end and a receiving end, so that the system capacity is effectively improved by using space domain resources on the premise of not increasing the system bandwidth and the transmitting power. However, in the 5G system using the massive MIMO technology, transmission performance is restricted by problems such as Inter-channel Interference (ICI), Inter-Antenna Synchronization (IAS), and Radio Frequency (RF) between hundreds of antennas disposed in the same base station. For this reason, Spatial Modulation (SM) in which only a part of antennas are activated while information is transmitted using antenna numbers has attracted attention. In the conventional SM system, only one antenna is activated in each time slot, the other antennas are kept silent, a part of input information bits is used to select an index number of one transmitting antenna, and the rest of bit information is used for constellation modulation.
However, the conventional SM only activates one transmitting antenna, and cannot fully utilize spatial resources of massive MIMO, and the total transmission rate is low. For this purpose, General Spatial Modulation (GSM) activates at least two or more antennas per slot for transmitting data symbols. At this time, the spatial domain information corresponds to the activated transmitting antenna combination, rather than the independent antenna serial number, each activated antenna transmits the same information bit, the acquired diversity gain is larger, and the multiplexing gain is zero. To achieve higher transmission rates, a new scheme incorporating a Vertical Space-time layered coding (V-BLAST) technique, which is called a Multiple Active-spatial Modulation (MA-SM) technique, is proposed. In a MA-SM system, each active transmit antenna transmits a different constellation modulation symbol. Although the transmission rate of information bits is increased, the system suffers from a serious ICI problem at the receiving end. Therefore, the MA-SM system has a much higher complexity at the receiving end compared to the conventional spatial modulation technique.
The signal detection methods that have been proposed so far are classified into optimal and suboptimal methods. The optimal method searches all antenna combinations and jointly estimates the antenna serial number and the constellation symbol, which is called Maximum Likelihood detection (ML). The ML detection method can achieve the optimal system detection performance, but the complexity of the method increases exponentially with the number of transmit antennas and the modulation order, and many searches in the method are ineffective. Subsequently, many researchers have proposed some suboptimal detection methods, which are generally divided into two steps, the first step of detecting one or several possible active antenna combinations, and the second step of symbol detection. The Maximum Received Ratio Combining (MRRC) method first orders the possible combinations of active antennas and then demodulates the constellation symbols for the most likely combinations. The method has certain limitations and is not suitable for general fading channels, such as flat rayleigh fading channels. The complexity of the existing method is low, and the difference between the overall detection performance of the method and the ML method is large. In addition, for the MIMO system with the number of receiving antennas less than the number of transmitting days, the pseudo-inverse matrix of the channel may not be unique, and the method has little effect on detecting the antenna sequence number. The other method firstly uses a sorting method to sort all possible antenna combinations, then uses the minimum mean square error method to sequentially detect the antenna combinations according to the sequence from the high possibility to the low possibility, and verifies the reliability of the estimated signal according to a preset termination threshold value.
Disclosure of Invention
The technical problem to be solved by the present invention is to provide a multi-active generalized spatial modulation detection method based on zero-forcing equalization and partial maximum likelihood to solve the problems of high complexity and poor performance of the detection method of the generalized spatial modulation system.
The invention adopts the following technical scheme:
a multi-active generalized spatial modulation detection method utilizes zero forcing linear equalization to detect all possible activated antenna combinations, obtains corresponding Euclidean distances according to information bits after each group of equalization, then sequences the Euclidean distances, takes the antenna combination with the minimum Euclidean distance as an activated antenna index, then judges whether partial maximum likelihood detection is carried out on the antenna combination according to a threshold value, and detects adjacent constellation points after equalization to obtain constellation modulation symbols.
Specifically, the method comprises the following steps:
s1 detecting all possible active antenna combinations using ZF linear equalization
Figure BDA0001851492020000031
S2, comparing the result obtained in the step S1
Figure BDA0001851492020000032
Performing digital demodulation to obtain coarse detected constellation symbols
Figure BDA0001851492020000033
S3, according to the result of demodulation in S2, the Euclidean distance is calculated to obtain
Figure BDA0001851492020000034
(ii) the Euclidean distance;
s4, sequencing the Euclidean distances determined in the step S3, and selecting the antenna combination with the minimum Euclidean distance as an activated antenna combination;
s5, eliminating interference among different transmitting antennas at a receiving end through linear equalization;
s6, carrying out maximum likelihood on the adjacent constellation points of the constellation symbol with the minimum Euclidean distance;
and S7, sorting the D obtained in the step S6, and selecting the constellation point with the minimum Euclidean distance as the demodulation result of the constellation symbol.
Further, in step S1, all possible activated antenna combinations
Figure BDA0001851492020000035
The method specifically comprises the following steps:
Figure BDA0001851492020000036
wherein, WZFRepresenting the corresponding ZF linear equalization matrix, y being NrX 1-dimensional transmit signal vector, NrFor the number of receiving antennas (·)HRepresents the conjugate transpose of the matrix and,
Figure BDA0001851492020000037
channel matrix representing all possible active antenna combinations, H being Nr×NtA dimensional channel matrix.
Further, the method comprisesIn step S2, constellation symbols are coarsely detected
Figure BDA0001851492020000038
The calculation is as follows:
Figure BDA0001851492020000039
wherein Q (·) denotes a digital demodulation function.
Further, in step S3, the euclidean distance is specifically:
Figure BDA00018514920200000310
wherein d is a set of Euclidean distances calculated according to all possible combinations of activated antennas, and y is NrX 1-dimensional transmit signal vector, NrIn order to determine the number of the receiving antennas,
Figure BDA00018514920200000311
the channel matrix for all possible combinations of active antennas,
Figure BDA00018514920200000312
f is the Frobenius norm for the coarsely detected constellation symbols.
Further, in step S4, the sequence specifically includes:
[d1,d2,…,dN]＝argsort(d)
where sort (. cndot.) represents an ascending sort function, d1Is the minimum of d, which is the set of euclidean distances computed over all possible combinations of active antennas.
Further, in step S5, a threshold V is setthFirstly, judging the accuracy of signal detection, and if the Euclidean distance is smaller than a threshold value, finishing the detection of the antenna combination and the constellation symbol; otherwise, the constellation symbol is re-detected.
Further, a threshold value VthThe calculation is as follows:
Vth＝2Nrσ2
wherein N isrFor number of receiving antennas, σ2Is the variance.
Further, in step S6, the process of performing maximum likelihood on the neighboring constellation point of the constellation symbol with the smallest euclidean distance is as follows:
Figure BDA0001851492020000041
wherein the content of the first and second substances,
Figure BDA0001851492020000042
to represent
Figure BDA0001851492020000043
And
Figure BDA0001851492020000044
according to adjacent constellation points, D is
Figure BDA0001851492020000045
And
Figure BDA0001851492020000046
y is NrX 1-dimensional transmit signal vector, NrIn order to determine the number of the receiving antennas,
Figure BDA0001851492020000047
the channel matrix for all possible combinations of active antennas,
Figure BDA0001851492020000048
f is the Frobenius norm for the coarsely detected constellation symbols.
Specifically, the generalized spatial modulation system includes NtA transmitting antenna and NrA receiving antenna, and in each time slot, NpThe root antenna is activated to transmit information bits, the channel is quasi-static flat Rayleigh fading, and between sub-channelsIndependent of each other, the receiving end has ideal channel estimation and synchronous reception, and the received signal is:
y＝Hx+n
wherein y is NrA transmit signal vector of x 1 dimension; h is Nr×NtA channel matrix of dimensions; n is NrWhite Gaussian noise of x 1 dimension, mean 0, variance σ2(ii) a x is NtA modulated transmit signal vector of dimension x 1.
Compared with the prior art, the invention has at least the following beneficial effects:
the invention discloses a multi-active generalized spatial modulation detection method, which separately detects an activated antenna index and a constellation symbol, greatly reduces the complexity of an algorithm compared with joint detection, and improves the bit error rate performance while reducing the complexity by adopting a method of firstly roughly and then finely detecting the constellation symbol.
Further, zero forcing linear equalization is used to detect all possible active antenna combinations because of the low complexity of the zero forcing algorithm.
Further, the equalized result is digitally demodulated to obtain a constellation symbol which is roughly detected, so that the detection complexity of the constellation symbol is low.
Further, the euclidean distances corresponding to all possible antenna combinations are calculated, and the activation possibility of the antenna combinations can be determined according to the euclidean distances.
Further, the obtained euclidean distances are ranked, and the smaller the distance is, the more likely the antenna combination is activated, so that the antenna combination with the smallest distance is selected as the detection result.
Further, the value of the minimum distance is compared with a set threshold, if the value is smaller than the threshold, the detection of the previous constellation symbol is completed, and if the value is larger than the threshold, the probability of the detection error of the constellation symbol is high, and further detection is needed.
Further, for the case that the constellation symbol is larger than the set threshold, maximum likelihood detection is performed on the constellation symbol, and in order to reduce complexity, only the adjacent constellation symbol of the previously detected constellation symbol is subjected to maximum likelihood detection, so as to obtain the final constellation symbol.
Further, compared with the traditional MIMO system, the generalized spatial modulation system introduces multiplexing gain in a spatial domain, reduces the cost of multiple radio frequency links, and also reduces the problem of interference between channels.
Further, the method is simple and convenient to operate.
In summary, compared with the maximum likelihood joint detection algorithm, the multi-active generalized spatial modulation detection method of the present invention separately detects the antenna index and the constellation symbol, greatly reduces the complexity of the algorithm, and in addition, after the constellation symbol is roughly detected by zero forcing equalization, whether to further detect the constellation symbol is judged by setting a threshold, thereby improving the detection performance of the method while reducing the complexity.
The technical solution of the present invention is further described in detail by the accompanying drawings and embodiments.
Drawings
FIG. 1 is a block diagram of a transmit receive architecture of the present invention;
FIG. 2 is a flowchart of the detection sequence of the present invention;
FIG. 3 is a diagram of comparing bit error rates corresponding to other detection methods, where the abscissa is the average symbol SNR at the receiving antenna, and the ordinate is the bit error rate BER, and the Monte Carlo method is used for simulation;
FIG. 4 is a diagram of comparing bit error rates corresponding to the detection method without threshold, wherein the abscissa is the average symbol SNR at the receiving antenna, and the ordinate is the bit error rate BER, and the Monte Carlo method is adopted for simulation;
FIG. 5 is a comparison graph of the multiplication complexity of the present invention and a maximum likelihood detection method ML, a detection method without adding a threshold, wherein the abscissa is the average symbol signal-to-noise ratio SNR at the receiving antenna, and the ordinate is the number of times of multiplication, and the simulation is performed by a Monte Carlo method;
fig. 6 is a second multiplication complexity comparison diagram of the present invention and a maximum likelihood detection method ML, a detection method without adding a threshold, wherein the abscissa is the average symbol signal-to-noise ratio SNR at the receiving antenna, and the ordinate is the number of times of addition, and a monte carlo method is adopted for simulation.
Detailed Description
The invention provides a multi-active generalized spatial modulation detection method based on zero forcing equalization and partial maximum likelihood, which is characterized in that zero forcing equalization is utilized to detect all possible activated antenna combinations, corresponding Euclidean distances are obtained according to information bits after each group of equalization, then the Euclidean distances are sequenced, the antenna combination with the minimum Euclidean distance is used as an activated antenna index, whether partial maximum likelihood detection is carried out on the antenna combination is judged according to a threshold value, namely, adjacent constellation points after equalization are detected, and finally constellation modulation symbols are obtained.
Referring to FIG. 1, let the generalized spatial modulation system have NtA transmitting antenna and NrA receiving antenna having N in each time slotpThe root antenna is activated for transmitting information bits. The channel is quasi-static flat Rayleigh fading, all sub-channels are mutually independent, a receiving end has ideal channel estimation and synchronous receiving, and a received signal is y ═ Hx + N, wherein y is NrA transmit signal vector of x 1 dimension; h is Nr×NtA channel matrix of dimensions; n is NrWhite Gaussian noise of x 1 dimension, mean 0, variance σ2(ii) a x is NtA modulated transmit signal vector of dimension x 1.
Referring to fig. 2, a method for detecting multiple active generalized spatial modulations according to the present invention includes the following steps:
s1, detecting all possible activated antenna combinations using ZF linear equalization, specifically:
Figure BDA0001851492020000071
wherein, WZFRepresents the corresponding ZF linear equalization matrix, (-)HRepresents the conjugate transpose of the matrix and,
Figure BDA0001851492020000072
representing channel moments for all possible active antenna combinationsArraying;
s2, pair
Figure BDA0001851492020000073
Performing digital demodulation to obtain coarse detected constellation symbols
Figure BDA0001851492020000074
The method specifically comprises the following steps:
Figure BDA0001851492020000075
wherein Q (·) denotes a digital demodulation function.
S3, according to the result of demodulation, calculating the Euclidean distance to obtain
Figure BDA0001851492020000076
(ii) the Euclidean distance;
the method specifically comprises the following steps:
Figure BDA0001851492020000077
wherein d is a set of Euclidean distances calculated according to all possible combinations of activated antennas, and y is NrX 1-dimensional transmit signal vector, NrIn order to determine the number of the receiving antennas,
Figure BDA0001851492020000078
the channel matrix for all possible combinations of active antennas,
Figure BDA0001851492020000079
f is a Frobenius norm, which is a constellation symbol of the coarse detection;
s4, sequencing the Euclidean distances determined in the step S3, wherein the smaller the Euclidean distance value is, the higher the possibility that the corresponding transmitting antenna combination is activated is, and therefore, the antenna combination with the minimum Euclidean distance is selected as an activated antenna combination;
the sequence is specifically as follows:
[d1,d2,…,dN]＝argsort(d)
where sort (. cndot.) represents an ascending sort function, d1Is the minimum value in d.
S5, ZF detection eliminates the interference between different transmitting antennas at the receiving end through linear equalization, and a threshold value V is setthFirstly, judging the accuracy of signal detection, and if the Euclidean distance is smaller than a threshold value, finishing the detection of the antenna combination and the constellation symbol; otherwise, detecting the constellation symbol again;
determined according to steps S1 and S2
Figure BDA0001851492020000081
It can be seen that ZF linear equalization amplifies noise, resulting in a decrease in the output signal-to-noise ratio of the system, which may cause some errors in the demodulated constellation symbols, so it is referred to as step S2
Figure BDA0001851492020000082
Is a coarsely detected constellation symbol; therefore, the constellation symbols need to be corrected. If the maximum likelihood detection is directly adopted for constellation symbols, the complexity of the algorithm is inevitably high due to the fact that the search range is still large and many searches are invalid, specifically:
setting a threshold V in the algorithmthFirst, the accuracy of signal detection is judged, d1≤VthIf the Euclidean distance is smaller than the threshold value, correction is not carried out, maximum likelihood can be avoided, and complexity is reduced.
The size of the threshold has great influence on the complexity of the algorithm, and too small a threshold can cause too many times of constellation symbol search, and too large a threshold can reduce the accuracy of constellation symbol detection. Here, the threshold is set to Vth＝2Nrσ2And if the Euclidean distance is smaller than the threshold value, completing the antenna combination and the constellation symbol detection. Otherwise, detecting the constellation symbol again;
s6, carrying out maximum likelihood on the adjacent constellation points of the constellation symbol with the minimum Euclidean distance;
because there may be some errors in constellation symbols detected by ZF, in order to correct the error in constellation symbol detection and reduce the complexity of the algorithm, the maximum likelihood is only performed on the adjacent constellation points of the constellation symbol with the minimum euclidean distance, and the process is as follows:
Figure BDA0001851492020000083
wherein the content of the first and second substances,
Figure BDA0001851492020000084
to represent
Figure BDA0001851492020000085
And
Figure BDA0001851492020000086
according to adjacent constellation points, D is
Figure BDA0001851492020000087
And
Figure BDA0001851492020000088
the calculated set of euclidean distances of adjacent constellation points;
and S7, sorting the D obtained in the step S6, and selecting the constellation point with the minimum Euclidean distance as the demodulation result of the constellation symbol.
In order to make the objects, technical solutions and advantages of the embodiments of the present invention clearer, the technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are some, but not all, embodiments of the present invention. The components of the embodiments of the present invention generally described and illustrated in the figures herein may be arranged and designed in a wide variety of different configurations. Thus, the following detailed description of the embodiments of the present invention, presented in the figures, is not intended to limit the scope of the invention, as claimed, but is merely representative of selected embodiments of the invention. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
Referring to fig. 3, a BER performance diagram of the ZF-based partial maximum likelihood detection method, ML method, pseudo-inverse matrix detection method, OB-MMSE method, and N adopted for simulation are showntIs 4, NpIs 2, NrThe constellation symbols are modulated with 4 QPSK. The simulation of the OB-MMSE method comprises setting a threshold and not setting the threshold, wherein the threshold also adopts 2Nrσ2All antenna combinations are traversed without setting a threshold in order to better verify the OB-MMSE approach. It can be seen from the figure that the existing method has a large gap between the performance and the ML method. The performance of the OB-MMSE method is close to the maximum likelihood detection under the condition of traversing all the antenna combinations, and the performance of the OB-MMSE method added with the threshold value is lower at the time of low signal-to-noise ratio, which indicates that the performance of the ordering method of the activated antenna combinations in the OB-MMSE method is slightly poor. The BER performance of the present invention is close to that of the ML method and higher than that of the OB-MMSE method. At BER equal to 10-4The SNR of the method provided by the invention is 0.5dB higher than that of the OB-MMSE method.
Referring to fig. 4, a comparison graph of SNR performance without threshold values of the ZF-based partial maximum likelihood detection method and the proposed method is shown, and the simulation conditions are the same as those in fig. 3, and it can be seen that the bit error rate performance of the threshold value and the bit error rate performance of the threshold value are similar. It is shown that the accuracy of the antenna combination serial number detected by ZF detection and euclidean distance is high.
Referring to fig. 5, a comparison graph of the number of multiplications of the ZF-based partial maximum likelihood detection method, the method without threshold, and the ML method is shown, where C1 in the ordinate represents the number of multiplications, and for clarity of comparison, the ordinate calculates the number of computations in a logarithmic form, and it can be seen from the graph that the complexity of the detection method of the present invention is much lower than that of the ML method, and when the SNR is equal to 12, the complexity of the method of the present invention is reduced by more than 85% compared with the ML method.
Referring to fig. 6, a comparison diagram of the number of addition operations of the ZF-based partial maximum likelihood detection method, the method without adding a threshold, and the ML method according to the present invention is shown. C2 in the ordinate represents the number of addition operations, and for the sake of clear contrast, the ordinate calculates the number of operations in a logarithmic manner, and it can be seen from the figure that the complexity of the detection method of the present invention is much lower than that of the ML method, and when the SNR is equal to 12, the complexity of the method of the present invention is reduced by more than 85% compared with the ML method.
The above-mentioned contents are only for illustrating the technical idea of the present invention, and the protection scope of the present invention is not limited thereby, and any modification made on the basis of the technical idea of the present invention falls within the protection scope of the claims of the present invention.

Claims (2)

1. A multi-active generalized spatial modulation detection method is characterized in that a generalized spatial modulation system comprises NtA transmitting antenna and NrA receiving antenna, and in each time slot, NpThe root antenna is activated to transmit information bits, the channel is quasi-static flat Rayleigh fading, all sub-channels are independent, the receiving end has ideal channel estimation and synchronous receiving, and the received signal is as follows:
y＝Hx+n
wherein y is NrA received signal vector of x 1 dimension; h is Nr×NtA channel matrix of dimensions; n is NrWhite Gaussian noise of x 1 dimension, mean 0, variance σ2(ii) a x is NtA modulated transmit signal vector of dimension x 1;
detecting all possible activated antenna combinations by utilizing zero forcing linear balance, obtaining corresponding Euclidean distances according to information bits after each group of balanced antennas, then sequencing the Euclidean distances, taking the antenna combination with the minimum Euclidean distance as an activated antenna index, judging whether to carry out partial maximum likelihood detection on the antenna combination according to a threshold value, and detecting adjacent constellation points after balancing to obtain constellation modulation symbols, wherein the specific steps are as follows:
s1 detecting all possible active antenna combinations using ZF linear equalization
Figure FDA0003224665580000011
All possible active antenna combinations
Figure FDA0003224665580000012
The method specifically comprises the following steps:
Figure FDA0003224665580000013
wherein, WZFRepresenting the corresponding ZF Linear equalization matrix, NrFor the number of receiving antennas (·)HRepresents the conjugate transpose of the matrix and,
Figure FDA0003224665580000014
channel matrix representing all possible active antenna combinations, H being Nr×NtA channel matrix of dimensions;
s2, comparing the result obtained in the step S1
Figure FDA0003224665580000015
Performing digital demodulation to obtain coarse detected constellation symbols
Figure FDA0003224665580000016
S3, according to the result of demodulation in S2, the Euclidean distance is calculated to obtain
Figure FDA0003224665580000017
The Euclidean distance is specifically as follows:
Figure FDA0003224665580000018
where d is the set of Euclidean distances computed from all possible combinations of active antennas, NrIn order to determine the number of the receiving antennas,
Figure FDA0003224665580000019
the channel matrix for all possible combinations of active antennas,
Figure FDA00032246655800000110
f is a Frobenius norm, which is a constellation symbol of the coarse detection;
s4, sorting the Euclidean distances determined in the step S3, selecting the antenna combination with the minimum Euclidean distance as an activated antenna combination, wherein the sorting specifically comprises the following steps:
[d1,d2,…,dN]＝argsort(d)
where sort (. cndot.) represents an ascending sort function, d1Is the minimum value of d, which is the set of euclidean distances calculated from all possible combinations of activated antennas;
s5, eliminating the interference between different transmitting antennas at the receiving end through linear equalization, and setting a threshold value VthFirstly, judging the accuracy of signal detection, and if the Euclidean distance is smaller than a threshold value, finishing the detection of the antenna combination and the constellation symbol; otherwise, the constellation symbol is re-detected by a threshold VthThe calculation is as follows:
Vth＝2Nrσ2
wherein N isrFor number of receiving antennas, σ2Is the variance;
s6, performing maximum likelihood on the adjacent constellation point of the constellation symbol with the minimum euclidean distance, the process is as follows:
Figure FDA0003224665580000021
wherein the content of the first and second substances,
Figure FDA0003224665580000022
to represent
Figure FDA0003224665580000023
And
Figure FDA0003224665580000024
according to adjacent constellation points, D is
Figure FDA0003224665580000025
And
Figure FDA0003224665580000026
n, of adjacent constellation pointsrIn order to determine the number of the receiving antennas,
Figure FDA0003224665580000027
the channel matrix for all possible combinations of active antennas,
Figure FDA0003224665580000028
f is a Frobenius norm, which is a constellation symbol of the coarse detection;
and S7, sorting the D obtained in the step S6, and selecting the constellation point with the minimum Euclidean distance as the demodulation result of the constellation symbol.
2. The method for detecting multiple active generalized spatial modulations according to claim 1, wherein in step S2, the constellation symbols are coarsely detected
Figure FDA0003224665580000029
The calculation is as follows:
Figure FDA00032246655800000210
wherein Q (·) denotes a digital demodulation function.
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