CN109164446B - Double-frequency-band vital sign detection radar system based on superheterodyne and low-intermediate frequency structure - Google Patents
Double-frequency-band vital sign detection radar system based on superheterodyne and low-intermediate frequency structure Download PDFInfo
- Publication number
- CN109164446B CN109164446B CN201811094519.5A CN201811094519A CN109164446B CN 109164446 B CN109164446 B CN 109164446B CN 201811094519 A CN201811094519 A CN 201811094519A CN 109164446 B CN109164446 B CN 109164446B
- Authority
- CN
- China
- Prior art keywords
- mixer
- power
- low
- pass filter
- band
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
- 238000001514 detection method Methods 0.000 title claims abstract description 30
- 230000015572 biosynthetic process Effects 0.000 claims abstract description 18
- 238000003786 synthesis reaction Methods 0.000 claims abstract description 18
- 230000009977 dual effect Effects 0.000 claims 2
- 101710096655 Probable acetoacetate decarboxylase 1 Proteins 0.000 claims 1
- 101710096660 Probable acetoacetate decarboxylase 2 Proteins 0.000 claims 1
- 230000000694 effects Effects 0.000 abstract description 3
- 230000001629 suppression Effects 0.000 abstract 1
- 238000005516 engineering process Methods 0.000 description 11
- 230000005540 biological transmission Effects 0.000 description 7
- 238000012545 processing Methods 0.000 description 6
- 230000002612 cardiopulmonary effect Effects 0.000 description 5
- 238000000034 method Methods 0.000 description 5
- 230000010355 oscillation Effects 0.000 description 4
- 238000011160 research Methods 0.000 description 4
- 238000013461 design Methods 0.000 description 3
- 238000010586 diagram Methods 0.000 description 3
- 238000001914 filtration Methods 0.000 description 3
- 101100434411 Saccharomyces cerevisiae (strain ATCC 204508 / S288c) ADH1 gene Proteins 0.000 description 2
- 101100381996 Saccharomyces cerevisiae (strain ATCC 204508 / S288c) BRO1 gene Proteins 0.000 description 2
- 101150102866 adc1 gene Proteins 0.000 description 2
- 101150042711 adc2 gene Proteins 0.000 description 2
- 238000004458 analytical method Methods 0.000 description 2
- 230000009286 beneficial effect Effects 0.000 description 2
- 230000008878 coupling Effects 0.000 description 1
- 238000010168 coupling process Methods 0.000 description 1
- 238000005859 coupling reaction Methods 0.000 description 1
- 230000007547 defect Effects 0.000 description 1
- 230000007613 environmental effect Effects 0.000 description 1
- 210000004072 lung Anatomy 0.000 description 1
- 238000004519 manufacturing process Methods 0.000 description 1
- 238000005259 measurement Methods 0.000 description 1
- 230000007903 penetration ability Effects 0.000 description 1
- 230000001766 physiological effect Effects 0.000 description 1
- 230000000241 respiratory effect Effects 0.000 description 1
- 238000005070 sampling Methods 0.000 description 1
- 238000012795 verification Methods 0.000 description 1
Images
Classifications
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
- G01S13/50—Systems of measurement based on relative movement of target
- G01S13/52—Discriminating between fixed and moving objects or between objects moving at different speeds
- G01S13/536—Discriminating between fixed and moving objects or between objects moving at different speeds using transmission of continuous unmodulated waves, amplitude-, frequency-, or phase-modulated waves
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
- G01S13/06—Systems determining position data of a target
- G01S13/08—Systems for measuring distance only
- G01S13/32—Systems for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated
- G01S13/36—Systems for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated with phase comparison between the received signal and the contemporaneously transmitted signal
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/88—Radar or analogous systems specially adapted for specific applications
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/03—Details of HF subsystems specially adapted therefor, e.g. common to transmitter and receiver
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/35—Details of non-pulse systems
Landscapes
- Engineering & Computer Science (AREA)
- Radar, Positioning & Navigation (AREA)
- Remote Sensing (AREA)
- Physics & Mathematics (AREA)
- Computer Networks & Wireless Communication (AREA)
- General Physics & Mathematics (AREA)
- Electromagnetism (AREA)
- Radar Systems Or Details Thereof (AREA)
Abstract
The invention discloses a double-frequency-band vital sign detection radar system based on superheterodyne and a low-intermediate frequency structure, which comprises a receiving antenna and a transmitting antenna, wherein the receiving antenna is connected with a low-noise amplifier, a first frequency mixer and a band-pass filter in series; the transmitting antenna is connected with a power amplifier, the power amplifier is connected with a power synthesis structure, one path of the input end of the power synthesis structure is connected with a second phase-locked loop chip connected with the input end of the second mixer, and the other path of the input end of the power synthesis structure is connected with a power divider; the input end of the power divider is connected with a phase-locked loop chip, one path of the output end of the power divider is connected to the input end of the power synthesis structure, and the other path of the output end of the power divider is connected to the input end of the first frequency mixer. The invention can simultaneously solve the problems of direct current bias and image suppression and realize the detection effect of the vital sign signals with higher precision.
Description
Technical Field
The invention relates to the field of vital sign detection, in particular to a dual-band vital sign detection radar system based on superheterodyne and a low-intermediate frequency structure.
Background
The vital sign detection technology mainly observes the parameters of human cardiopulmonary activity, and the detected cardiopulmonary information is used for judging a life body and emergently processing medical emergencies. Therefore, the vital sign detection technology is very practical and significant [1]. The method of the sensor for realizing vital sign detection is a contact sensor, the sensor finishes the collection and processing of cardiopulmonary signals by being attached to the surface of a human body, such as a respiratory monitor, an ultrasonic cardiograph and the like in a hospital, the sensor has high precision measurement, but has huge volume and high cost, is not beneficial to being popularized to families and individuals, and has a plurality of limitations in use, for example, a patient with large-area burn cannot use the contact sensor to measure the cardiopulmonary information [2]; the above disadvantages are well avoided by the contactless vital sign detection technology, especially the doppler radar detection technology in the contactless vital sign detection technology, which detects the tiny movements of the living body caused by the physiological activities based on the doppler effect, and obtains the information of the heart and lung through the tiny movements. And the penetration ability of the detector is very strong, the environmental adaptability is high, and the detector is very suitable for being applied to places such as earthquake rescue, critical patients and the like [3].
At present, the challenges faced by non-contact life detection technology are dc bias, image rejection, etc. To date, many research teams have proposed various solutions to the problem of the non-contact vital sign detection technology, such as an ac coupling technology for eliminating the influence of dc offset, but it also affects the signal while reducing the influence of dc offset, which is easy to cause distortion of the signal, and the implementation method is complicated [4]; moreover, the image rejection problem is commonly found in the superheterodyne structure adopted in the vital sign detection technology, and when the superheterodyne structure is used as the main structure of the transceiver, the image rejection problem is generated.
In summary, in order to solve the problems of dc offset and image rejection existing in the existing vital sign detection method, a novel detector structure method is urgently needed to achieve higher detection precision and achieve the purpose of more accurately detecting the vital sign signal.
[ REFERENCE ] to
[1] Huwei, research on non-contact vital sign detection technology based on doppler radar [ D ]. University of science and technology in china, 2014.
[2] Research on a radio frequency bio-radar system [ D ]. University of physical engineering, tokyo, 2016.
[3] MaleCel, human vital sign detection research for rescue after disaster [ D ]. Electronic science and technology university.2016.
[4] Yao, non-contact vital sign radar detection system and antenna design [ D ]. Nanjing university of science and industry, 2014.
Disclosure of Invention
The invention aims to overcome the defects in the prior art, and provides a dual-band vital sign detection radar system based on a superheterodyne and low-intermediate frequency structure, which can simultaneously solve the problems of direct current offset and image rejection and realize the detection effect of a vital sign signal with higher precision.
The purpose of the invention is realized by the following technical scheme.
The invention relates to a double-frequency-band vital sign detection radar system based on a superheterodyne and low-intermediate frequency structure, which comprises a receiving antenna and a transmitting antenna, wherein the receiving antenna is sequentially connected with a low-noise amplifier, a first frequency mixer and a band-pass filter in series, the first frequency mixer is connected with a first low-pass filter, the first low-pass filter is connected with a first analog-to-digital converter, and the band-pass filter is sequentially connected with a second frequency mixer, a second low-pass filter and a second analog-to-digital converter in series;
the transmitting antenna is connected with a power amplifier, the power amplifier is connected with a power synthesis structure, the input end of the power synthesis structure is divided into two paths, one path is connected with a second phase-locked loop chip connected with the input end of the second frequency mixer, and the other path is connected with a power divider; the input end of the power divider is connected with a first phase-locked loop chip, the output end of the power divider is divided into two paths, one path of the output end of the power divider is connected to the input end of the power synthesis structure, and the other path of the output end of the power divider is connected to the input end of the first frequency mixer.
The output end of the first frequency mixer is respectively connected with the input end of the band-pass filter and the input end of the first low-pass filter.
The input end of the second frequency mixer is connected with the output end of the band-pass filter and the output end of the second phase-locked loop chip respectively, and the output end of the second frequency mixer is connected with the input end of the second low-pass filter.
The power synthesis structure adopts a combiner.
Compared with the prior art, the technical scheme of the invention has the following beneficial effects:
(1) The invention can improve the accuracy of vital sign detection by using the dual-frequency band and can monitor the position information of a target by using the dual-frequency band;
(2) The invention can reduce power loss;
(3) The invention simplifies the structure of the receiver, can realize the functions of receiving and processing signals by only using one receiver structure, does not use an I/Q structure, and can save the design cost and time of a circuit.
Drawings
Fig. 1 is a schematic diagram of a dual-band vital sign detection radar system based on a superheterodyne and low-if architecture.
The reference signs are a Powersynthesis Power synthesis structure, a PA Power amplifier, a Tx _ Antenna transmitting Antenna, an Rx _ Antenna receiving Antenna, a Power _ Divider, a LO1 first phase-locked loop chip, an LO2 second phase-locked loop chip, a BPF band-pass filter, a Mixer1 first frequency Mixer, a Mixer2 second frequency Mixer, an LNA low-noise amplifier, an LPF1 first low-pass filter, an LPF2 second low-pass filter and an ADC1 first analog-to-digital converter; ADC2 analog-to-digital converter.
Detailed Description
In order to more clearly illustrate the technical solution of the present invention, the present invention is further described below with reference to the accompanying drawings. For a person skilled in the art, without inventive effort, other figures can also be derived from these figures.
The dual-band radar system for vital sign detection based on superheterodyne and low-if structure of the present invention, as shown in fig. 1, includes a receiving Antenna Rx _ Antenna and a transmitting Antenna Tx _ Antenna. The receiving Antenna Rx _ Antenna is sequentially connected with a low noise amplifier LNA, a first Mixer Mixer1 and a band-pass filter BPF in series. The first Mixer1 is connected with a first low pass filter LPF1, and the first low pass filter LPF1 is connected with a first analog-to-digital converter ADC1. The band-pass filter BPF is sequentially connected with a second Mixer Mixer2, a second low-pass filter LPF2 and a second analog-to-digital converter ADC2 in series.
The transmitting Antenna Tx _ Antenna is connected with a Power amplifier PA, the input end of the Power amplifier PA is connected with the output end of a Power synthesis structure, the input end of the Power synthesis structure is divided into two paths, one path is connected with a second phase-locked loop chip LO2, the second phase-locked loop chip LO2 is also connected with the input end of a second Mixer Mixer2, and the other path is connected with a Power Divider Power _ Divider. The Power Divider Power _ Divider input end is connected with a first phase-locked loop chip LO1, the output end is divided into two paths, one path is connected to the Power synthesis structure input end, and the other path is connected to the first Mixer1 input end.
Specifically, the input end of the first Mixer1 is connected to the output end of the low noise amplifier LNA and the output end of the Power Divider respectively, and the output end of the first Mixer1 is connected to the input end of the band pass filter BPF and the input end of the first low pass filter LPF1 respectively. The input end of the second Mixer Mixer2 is respectively connected with the output end of the band-pass filter BPF and the output end of the second phase-locked loop chip LO2, and the output end of the second Mixer Mixer2 is connected with the input end of the second low-pass filter LPF 2. The Power synthesis architecture may employ a combiner.
The principle of realizing the core of vital sign detection is shown in formulas (1) and (2):
sig 1 (t)＝cos(2πf 1 t+θ 1 (t)) (1)
sig 2 (t)＝cos(2πf 2 t+θ 2 (t)) (2)
as can be seen from formulas (1) and (2), the transmitted signal source is two paths of signals, wherein sig 1 (t) is a low frequency signal, sig 2 (t) is a high frequency signal, the frequencies of the transmitted signals are respectively f 1 And f 2 ，θ 1 (t) is a transmission signal f 1 Total phase noise of theta 2 (t) is a transmission signal f 2 And the two signals f 1 Is the frequency of the low-frequency signal, f 2 Is the frequency of the high frequency signal and t is time.
Assuming that the fixed distance between the transmission signal source and the human body is L, and the distance generated by the heart beat is x (t), for the transmission signal, when the transmission signal passes through a distance of 2L (t) =2l +2x (t) in total from the transmission to the reception, the expression of the received signal is:
wherein, sre 1 (t) is a low frequency signal, sre, modulated with a baseband signal 2 (t) is the high frequency signal modulated with the baseband signal, c is the speed of signal propagation, and λ = c/f is the wavelength of the transmitted signal. When receiving two paths of signals Sre 1 (t)、Sre 2 (t) phase locking with the first phaseAfter local oscillation signals LO _1 generated by the ring chip enter the first frequency mixer at the same time for first frequency mixing, four paths of signals are generated, and the frequencies of other three paths of signals in the generated four paths of signals are respectively as follows: 2f 1 、f 1 +f 2 、f 1 -f 2 Also, a baseband signal is generated:
dividing the obtained four paths of signals into two paths, wherein one path of signals passes through a first low-pass filter to filter other high-frequency signals except the baseband signals to obtain the required baseband signals Sig B1 (t); the other signal will undergo secondary mixing. From the result of the first mixing, we can obtain an intermediate frequency signal with a frequency f 1 -f 2 (ii) a This intermediate frequency signal is then processed, and the Sig generated by the system 2 (t) the signal obtained after the fourth frequency division is exactly equal to f 1 -f 2 The intermediate frequency signal corresponds to the intermediate frequency signal, so that reuse of a mixer is avoided, and the phenomenon of local oscillation drift is also avoided. After the second mixing, another baseband signal Sig is obtained B2 (t) is:
and the two paths of signals both containing baseband signals are subjected to signal processing, and parameters, waveforms and the like obtained after the signal processing are observed.
For convenient operation, the specific implementation process of the invention is as follows:
first, a suitable transmit signal frequency is determined. The same signal frequency is selected based on the existing double-frequency amplifier circuit board in the laboratory.
Then, based on the proposed radar system, theoretical verification is performed.
The analysis was as follows: the signal source of the emission is two-way signal, whereinThe frequency of the transmitted signal being f 1 And f 2 As shown in formulas (1) and (2). The signals received by the receiver part are shown in formulas (3) and (4), and when the two paths of signals Sre 1 、Sre 2 And when the Mixer1 is entered simultaneously, the local oscillator signal LO _1 is used for first mixing, wherein LO _1 is shown in formula (7).
LO_1＝cos(2πf 1 t+θ 1 (t)) (7)
After the first mixing, four types of signals are generated, as shown in equations (5), (8), (9) and (10):
it can be seen from the equations (5), (8), (9) and (10) that after the first mixing, a baseband signal Sig is obtained B1 An intermediate frequency signal S 2 And two high frequency signals S 1 And S 3 What we need is a baseband signal Sig B1 And intermediate frequency signal S 2 Therefore for the baseband signal Sig B1 It is necessary to add a low pass filter LPF1 after the Mixer1 to filter the intermediate frequency signal S 2 And a high frequency signal S 1 、S 3 Filtering; for intermediate frequency signal S 2 It is necessary to add a band-pass filter BPF after the Mixer Mixer1 to convert the baseband signal Sig B1 And a high frequency signal S 1 、S 3 And (4) filtering. The baseband signal Sig obtained B1 Continuing to process the signal to obtain the intermediate frequency signal S 2 And then the second mixing is performed. The local oscillator signal LO _2 generated by the phase-locked loop chip of the second mixing is used, and the formula (11) is as follows:
the local oscillator signals LO _2 are somewhat different, and have frequencies of one of the transmission signals f 2 Is so because of the intermediate frequency signal S 2 Signal frequency f 1 -f 2 Exactly the transmitted signal f 2 And generates a transmit signal f 2 Can just divide the frequency output. Then, the second frequency mixing is carried out by utilizing the condition, so that the reuse of a local oscillation source is omitted, and the local oscillation drift is also avoided. LO _2 is mixed with the intermediate frequency signal S 2 After mixing, the baseband signal Sig obtained by formula (6) is obtained B2 . Two baseband signals (Sig) to be obtained B1 、Sig B2 ) The obtained cardiopulmonary signals are observed by digital filtering, sampling and other processing in a virtual instrument (LABVIEW).
The third step: and selecting proper chips such as a first phase-locked loop chip LO1, a second phase-locked loop chip LO2, a first Mixer Mixer1, a second Mixer Mixer2, a low noise amplifier LNA and the like. Based on the analysis of the theory, when the phase-locked loop chip is selected, one phase-locked loop chip needs to output two paths of signals simultaneously, and the frequencies of the two paths of signals are n times.
The fourth step: designing a schematic diagram and manufacturing a PCB. The matching relationship between the individual circuit blocks is to be noted when designing the schematic diagram. The data sheet of the chip can be referred to for the circuit design of each module.
Claims (4)
1. A radar system for detecting dual-band vital signs based on superheterodyne and a low-intermediate frequency structure comprises a receiving Antenna (Rx _ Antenna) and a transmitting Antenna (Tx _ Antenna), and is characterized in that the receiving Antenna (Rx _ Antenna) is sequentially connected in series with a Low Noise Amplifier (LNA), a first Mixer (Mixer 1) and a Band Pass Filter (BPF), the first Mixer (Mixer 1) is connected with a first low pass filter (LPF 1), the first low pass filter (LPF 1) is connected with a first analog-to-digital converter (ADC 1), and the Band Pass Filter (BPF) is sequentially connected in series with a second Mixer (Mixer 2), a second low pass filter (LPF 2) and a second analog-to-digital converter (ADC 2);
the transmitting Antenna (Tx _ Antenna) is connected with a Power Amplifier (PA), the Power Amplifier (PA) is connected with a Power synthesis structure (Powersynthesis), the input end of the Power synthesis structure (Powersynthesis) is divided into two paths, one path is connected with a phase-locked loop chip (LO 2) which is connected with the input end of a Mixer (Mixer 2), and the other path is connected with a Power Divider (Power _ Divider); the second phase-locked loop chip (LO 2) is required to output two paths of signals at the same time, and the frequencies of the two paths of signals are n times of the relationship; the input end of the Power Divider (Power _ Divider) is connected with a phase-locked loop chip (LO 1), the output end is divided into two paths, one path is connected to the input end of a Power synthesis structure (Power synthesis), and the other path is connected to the input end of a Mixer (Mixer 1).
2. The dual band vital sign detection radar system based on superheterodyne and low-if structure according to claim 1, wherein the input terminal of the first Mixer (Mixer 1) is connected to the output terminal of the Low Noise Amplifier (LNA) and the output terminal of the Power Divider (Power Divider), respectively, and the output terminal of the first Mixer (Mixer 1) is connected to the input terminal of the Band Pass Filter (BPF) and the input terminal of the first low pass filter (LPF 1), respectively.
3. The dual-band vital sign detection radar system based on superheterodyne and low-intermediate frequency structure, according to claim 1, wherein the input terminal of the second Mixer (Mixer 2) is connected to the output terminal of the Band Pass Filter (BPF) and the output terminal of the second phase-locked loop chip (LO 2), respectively, and the output terminal of the second Mixer (Mixer 2) is connected to the input terminal of the second low pass filter (LPF 2).
4. The dual band vital sign detection radar system based on superheterodyne and low-if structure (claim 1), wherein the power synthesis structure (Powersynthesis) employs a combiner.
Priority Applications (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201811094519.5A CN109164446B (en) | 2018-09-19 | 2018-09-19 | Double-frequency-band vital sign detection radar system based on superheterodyne and low-intermediate frequency structure |
| LU101282A LU101282B1 (en) | 2018-09-19 | 2019-07-02 | Dual-band vital signs detection radar system based on superheterodyne and low-intermediate frequency structure |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201811094519.5A CN109164446B (en) | 2018-09-19 | 2018-09-19 | Double-frequency-band vital sign detection radar system based on superheterodyne and low-intermediate frequency structure |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN109164446A CN109164446A (en) | 2019-01-08 |
| CN109164446B true CN109164446B (en) | 2023-01-06 |
Family
ID=64879642
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201811094519.5A Active CN109164446B (en) | 2018-09-19 | 2018-09-19 | Double-frequency-band vital sign detection radar system based on superheterodyne and low-intermediate frequency structure |
Country Status (2)
| Country | Link |
|---|---|
| CN (1) | CN109164446B (en) |
| LU (1) | LU101282B1 (en) |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112558062A (en) * | 2019-09-25 | 2021-03-26 | 天津大学 | Multi-target vital sign radar detection system based on coding and phased array antenna |
| CN117526974A (en) * | 2022-07-29 | 2024-02-06 | 天津大学 | 5G dual-frequency bidirectional transceiver with high image rejection degree |
Family Cites Families (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20080074307A1 (en) * | 2006-05-17 | 2008-03-27 | Olga Boric-Lubecke | Determining presence and/or physiological motion of one or more subjects within a doppler radar system |
| CN101458326B (en) * | 2007-12-14 | 2011-04-27 | 南京理工大学 | Life detecting device based on pseudocode phase-modulated continuous wave system |
| CN102419434B (en) * | 2011-08-12 | 2013-04-03 | 西安天伟电子系统工程有限公司 | Intermediate-frequency and radio-frequency universal target simulator for pulse pressure radar |
| DE102013114735A1 (en) * | 2013-12-20 | 2015-06-25 | Endress + Hauser Gmbh + Co. Kg | PRF frequency generator for a level gauge |
| US9833200B2 (en) * | 2015-05-14 | 2017-12-05 | University Of Florida Research Foundation, Inc. | Low IF architectures for noncontact vital sign detection |
| CN204794979U (en) * | 2015-06-23 | 2015-11-18 | 江苏星宇芯联电子科技有限公司 | Wireless receiver circuit |
| CN105796099A (en) * | 2016-03-08 | 2016-07-27 | 太原理工大学 | Radar type remote vital sign monitoring system based on self-rotating microwave detector |
| CN107453775B (en) * | 2017-08-24 | 2019-05-07 | 南京理工大学 | A kind of zero intermediate frequency reciver |
-
2018
- 2018-09-19 CN CN201811094519.5A patent/CN109164446B/en active Active
-
2019
- 2019-07-02 LU LU101282A patent/LU101282B1/en active IP Right Grant
Also Published As
| Publication number | Publication date |
|---|---|
| LU101282B1 (en) | 2019-11-08 |
| CN109164446A (en) | 2019-01-08 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| Droitcour et al. | Range correlation and I/Q performance benefits in single-chip silicon Doppler radars for noncontact cardiopulmonary monitoring | |
| CN105786185B (en) | Non-contact gesture identifying system and method based on continuous wave micro-doppler radar | |
| Li et al. | A review on recent advances in Doppler radar sensors for noncontact healthcare monitoring | |
| US9375153B2 (en) | Motion/vibration sensor | |
| US9603555B2 (en) | Motion/vibration detection system and method with self-injection locking | |
| Xiao et al. | A Ka-band low power Doppler radar system for remote detection of cardiopulmonary motion | |
| CN103070728A (en) | Non-contact type vital sign monitoring equipment | |
| Mostafanezhad et al. | Benefits of coherent low-IF for vital signs monitoring using Doppler radar | |
| CN109164446B (en) | Double-frequency-band vital sign detection radar system based on superheterodyne and low-intermediate frequency structure | |
| Lie et al. | A 2.4 GHz non-contact biosensor system for continuous monitoring of vital-signs | |
| Li et al. | Recent advances in Doppler radar sensors for pervasive healthcare monitoring | |
| KR20040027577A (en) | Wireless detection system and method of heart rates | |
| CN109239708A (en) | A kind of double frequency circuit structure for realizing vital signs detecting and short distance positioning | |
| Jang et al. | Wireless bio-radar sensor for heartbeat and respiration detection | |
| Hafner et al. | Non-contact cardiopulmonary sensing with a baby monitor | |
| Das et al. | Antenna evaluation of a non-contact vital signs sensor for continuous heart and respiration rate monitoring | |
| Xiao et al. | Accuracy of a low-power Ka-band non-contact heartbeat detector measured from four sides of a human body | |
| TWI682649B (en) | Signal demodulation device with iq mixer and demodulated method thereof | |
| TWI556797B (en) | Motion/interference sensor | |
| KR100665567B1 (en) | Bio radar | |
| Ganguly et al. | Sensitive transmit receive architecture for body wearable RF plethysmography sensor | |
| Huang et al. | A 5.8-GHz radar sensor chip in 0.18-μm CMOS for non-contact vital sign detection | |
| Gu et al. | An instruments-built Doppler radar for sensing vital signs | |
| CN114646956A (en) | Vital sign radar sensor using wireless network signals | |
| TWI799095B (en) | Non-contact vital signs detector |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant | ||
| TR01 | Transfer of patent right |
Effective date of registration: 20240109 Address after: 300392 Industrial Incubator-6, North 2-301, No. 18 Haitai West Road, Huayuan Industrial Zone, Binhai New Area, Tianjin Patentee after: Xinlingtong (Tianjin) Technology Co.,Ltd. Address before: 300072 Tianjin City, Nankai District Wei Jin Road No. 92 Patentee before: Tianjin University |
|
| TR01 | Transfer of patent right |