CN108848047A - A kind of filter bank multi-carrier transmitter implementation method - Google Patents
A kind of filter bank multi-carrier transmitter implementation method Download PDFInfo
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2626—Arrangements specific to the transmitter only
- H04L27/2627—Modulators
- H04L27/264—Pulse-shaped multi-carrier, i.e. not using rectangular window
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2602—Signal structure
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2614—Peak power aspects
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Abstract
The present invention relates to a kind of filter bank multi-carrier transmitter implementation methods, belong to wireless communication technology field.This method includes：S1：The data flow of transmission is subjected to OQAM modulation, the data flow of modulation number is then subjected to data block grouping, and carry out IFFT respectively；S2：PAPR suppression module is designed, optimum angle search is realized, after obtaining the optimum angle factor, is multiplied respectively with data block after each group IFFT；S3：PPN module is designed, is added after the data block after every group of optimization is inputted multiphase filtering network PPN；S4：The delay of I/Q two-way is added, and generates FBMC signal.The present invention can reduce the computation complexity of FBMC transmitter, and obtain the FBMC waveform with lower PAPR.
Description
Technical field
The invention belongs to mobile communication technology fields, are related to the FBMC transmitter implementation method of low PAPR a kind of.
Background technique
FBMC technology can meet the total demand of future mobile communications as one of 5G candidate's waveform.FBMC is based on son
Carrier wave filters, and does not need strict orthogonal between subcarrier.Subcarrier spacing can flexible setting so that efficiently using scattered frequency
Spectrum resource becomes feasible.In order to avoid the interference and biggish spectral leakage between FBMC subcarrier, FBMC base band uses OQAM
Modulation and each subcarrier individually filter, but increase the complexity of receive-transmit system simultaneously, therefore how to reduce FBMC system complex
Degree becomes one of research hotspot.Another in waveform research process by the topic of extensive discussions is PAPR performance, and low PAPR can be improved
The working efficiency of power amplifier, and then bigger MPS process or lower power consumption of terminal can be converted into.Therefore PAPR
It is one of the key factor for influencing FBMC system performance.
Patent [CN106878220A] proposes that the road I FBMC symbol sebolic addressing will be divided by the constellation graphic sequence of modulation FBMC symbol
With the road Q FBMC symbol sebolic addressing, the even carriers and odd carriers of the road I FBMC symbol sebolic addressing merge into the frequency domain of the road I FBMC symbol
Sequence, the even carriers and odd carriers of the road Q FBMC symbol sebolic addressing merge into the frequency domain sequence of the road Q FBMC symbol.Merge the I
The frequency domain sequence of the frequency domain sequence of road FBMC symbol and the road the Q FBMC symbol, and the frequency domain sequence after the merging done inverse
Fourier transformation obtains the time domain sequences of modulated FBMC symbol.What the program was taken is that frequency domain expansion mode realizes FBMC
Waveform, but FFT points can extend K times.
Patent [CN105681241A] proposes a kind of algorithm for reducing FBMC system PAPR.The algorithm reflects symbol to be sent
It penetrates as real number symbol, the real number symbol after obtaining phase rotation is modulated the real number symbol after each phase rotation, obtains
Modulated time-domain signal calculates each modulated time-domain signal and obtains minimum corresponding phase rotation coefficient vector, by this
Phase rotation coefficient vector is as optimum angle twiddle factor vector.The phase factor that the algorithm uses for traditional phase because
Son, the real part data and imaginary data of FBMC signal respectively correspond an optimum angle twiddle factor vector, although reducing letter
Number PAPR, but computation complexity is higher.
Therefore, the present invention carries out PAPR inhibition to FBMC waveform using unified algorithm, reduces computation complexity.
Summary of the invention
In view of this, can be dropped the purpose of the present invention is to provide a kind of FBMC transmitter implementation method by this method
The computation complexity of low FBMC transmitter, and obtain the FBMC waveform with lower PAPR.
In order to achieve the above objectives, the present invention provides the following technical solutions：
A kind of filter bank multi-carrier transmitter implementation method, includes the following steps：
S1：By the data flow of transmission carry out staggeredly it is orthogonal (Offset Quadrature Amplitude Modulation,
OQAM it) modulates, the data flow of modulation number is then subjected to data block grouping, and carry out IFFT respectively；
S2：Design papr (Peak to Average Power Ratio, PAPR) suppression module, the mould
Block mainly realizes that optimum angle is searched for, and after obtaining the optimum angle factor, is multiplied respectively with data block after each group IFFT；
S3：PPN module is designed, is added after the data block after every group of optimization is inputted PPN；
S4：The delay of I/Q two-way is added, and generates FBMC signal.
Further, the step S1 specifically includes following steps：
S11：The data flow of transmission is subjected to OQAM modulation；
S12：Data flow carries out carrier wave distribution and the insertion of training sequence after OQAM modulation, and completes string simultaneously
Conversion process；
S13：Carrier wave classifier modules are called, setting parameter FFT counts, and passes through the parameter setting total number of sub-carriers mesh；
S14：Training sequence parameter is set and generates synchronization character one and synchronization character two；
S15：Setting occupies subcarrier parameter, realizes subcarrier maps；
S16：After setting the above parameter, by data flow multiplied by linear phase matrix, then IFFT transformation is carried out.
Further, the OQAM modulation, specifically includes following steps：
S111：The data flow of transmission is completed into QAM mapping；
S112：It carries out the QAM complex symbol being mapped to take real and imaginary parts, obtains data vector D；
S113：By obtained data vector D multiplied by vector thetak,mIt is alternate to carry out frequency domain actual situation, θk,mValue is shown below：
Wherein, k is subcarrier index, and m is symbolic label.
Further, the step S2 specifically includes following steps：
The PAPR suppression module combines the partial transmission sequence algorithm and MBJO-PTS algorithm pair of novel phase factor
FBMC waveform carries out PAPR inhibition and is divided into v group wherein the data block inputted is the m OQAM symbol modulated,
It is expressed as a vector：
Wherein m is sign flag,Indicate that m symbol kth group data, this group of data are passed through after IFFT, the sequence of signal
List is shown as：
Wherein k is subcarrier index, and M indicates IFFT point number；
The phase factor matrix of symbol m is expressed as：
WhereinThe phase factor for indicating the kth group of symbol m, meets following equation：
Wherein ω is discrete phase number, and after every group multiplied by phase factor, m-th of symbol sebolic addressing is expressed as：
Wherein,WithRespectively indicate kth group data by the first half and latter half after IFFT, i.e.,：
WithRespectively indicate the first half of kth group and the phase factor of latter half, first half and later half
Partial phase respectively byWithIt indicates, the two meets following equation：
α value is 0~0.5, when optimizing than the m-th data block, the plyability of m data block before this method only considers；It is false
If the phase factor of preceding m-1 data block is it has been determined that the objective function of optimization than the m-th data block is
Subject to
bm=bm+1=...=bM-1=0
Wherein K is overlap factor, PqThe value for indicating q sections of PAPR is expressed as with following formula：
Wherein, L indicates that the total number of transmitting symbol, n indicate discrete time-domain label, SnIndicate that the n moment sends time-domain value, E
{|Sn|2Indicate that the n moment sends time domain energy mean value.
Further, the step S3 is specifically included：The optimum angle factor is obtained by step S2, and by the optimum angle factor
It is multiplied to obtain parallel M circuit-switched data respectively at each group of data block, sharing group number is v；If the time domain impulse response length of filter is
LP=K*M carries out displacement extraction to it with interval M, obtains M group decimation value, and the number of every class value is K；The M that each group has been optimized
After circuit-switched data makees convolution algorithm with K sample value of M group respectively, every circuit-switched data carries out M sampling, and it is long that delay addition obtains data
Degree is the data of K*M；After repeating above step v times, the data obtained is overlapped mutually to obtain I circuit-switched data；M point DFT is integrally transported
Calculation magnitude, which is considered as, is proportional to M*log2M, and frequency domain expansion algorithm is needed in carrier wave mapping, and data volume is extended K times, therefore,
It is about KM*log that it, which calculates total amount,2(KM)；And in heterogeneous structure, M point IFFT is directly carried out to data flow first, calculates total amount
About M*log2M, computation complexity are lower.
Further, the step S4 specifically includes following steps：Step S3 is repeated, after obtaining Q circuit-switched data, delayed symbol week
The half of phase is added with the road I, generates the FBMC waveform with lower PAPR.
The beneficial effects of the present invention are：The present invention is different from tradition PTS algorithm, and the method for the invention accords with m-th
The influence of m-1 symbol before being considered when number optimizing, and optimized using novel phase factor, effective inhibition
PAPR and the side information without additionally increasing transmitter.The present invention combines PPN structural generation FBMC symbol simultaneously, reduces
Computation complexity.
Detailed description of the invention
In order to keep the purpose of the present invention, technical scheme and beneficial effects clearer, the present invention provides following attached drawing and carries out
Explanation：
Fig. 1 is FBMC transmitter block diagram of the present invention；
Fig. 2 is complementary cumulative distribution function (the Complementary Cumulative Distribution of algorithms of different
Function, CCDF) curve compares figure；
Fig. 3 is algorithm complexity comparison diagram.
Specific embodiment
Below in conjunction with attached drawing, a preferred embodiment of the present invention will be described in detail.
Present invention mainly solves FBMC waveforms to have the problem of higher PAPR, the method includes：By the data flow of transmission
It is modulated by OQAM；The data flow modulated is subjected to data block grouping, every group of data are evenly dividing two according to subcarrier sequence
Part, respectively multiplied by different phase factors, phase meets α times of relationship；Optimum angle search is carried out, determines every group optimal
Phase factor, when optimizing m-th of symbol, the influence of m-1 symbol before considering；Phase after data block input PPN after every group of optimization
Add.Present invention combination PPN structure and partial transmission sequence (the Improved Partial for combining Novel photo location factor
Transmission Sequence, Improved-PTS) algorithm and more data block combined optimizations partial transmission sequence
(Multi-Block-Joint-Optimization Partial Transmission Sequence, MBJO-PTS) algorithm pair
FBMC waveform carries out PAPR inhibition, can effectively inhibit PAPR and without the additional side information for increasing transmitter, reduction
Computation complexity.
As shown in Figure 1, FBMC transmitter implementation method of the present invention specifically includes following steps：
S1：It generates data flow and carries out QAM modulation, define the parity of symbolic number.Odd even is defined according to subcarrier number
Subcarrier characteristic.It carries out obtained QAM complex symbol to take real and imaginary parts.By obtained real number multiplied by vector thetak,mCarry out frequency
Domain actual situation is alternate.The actual situation of the carrier wave mapping of even number symbols is with odd number symbols on the contrary, the composition actual situation of time domain is alternate.At this
Reason process is divided into three steps：
S11：The bit stream of input is completed into QAM mapping；
S12：Real and imaginary parts are taken to obtain data vector D the QAM complex symbol being mapped to implementation；
S13：By obtained data vector D multiplied by vector thetak,mIt is alternate to carry out frequency domain actual situation, θk,mValue is shown below：
Wherein, k is subcarrier index, and m is symbolic label.
S2：Data flow implements carrier wave distribution and the insertion of training sequence after OQAM modulation, and completes string simultaneously
Conversion process.Carrier wave classifier modules are called, setting parameter FFT counts, and passes through the parameter setting total number of sub-carriers mesh.Setting instruction
Practice sequential parameter and generates synchronization character one and synchronization character two.Setting occupies subcarrier parameter, realizes subcarrier maps.The above ginseng of setting
After number, by data flow multiplied by linear phase matrix, then IFFT transformation is carried out.
S3：Above step is completed, data flow enters PAPR suppression module.The module implementation process is as follows；
S31：Generate phase factor matrix, all combinations of phase factor which contains two data blocks
Situation, the phase factor search in process flow scans in the matrix later；
S32：Two data of each symbol are divided, traverse phase factor matrix, and correspondence is multiplied by symbol data；
S33：The minimum value of the sum of PARP value of n symbol, n value are every before successively traversing m FBMC-OQAM symbol and calculating
It is secondary to increase by 1.The each PARP value for dividing segment of preceding n symbol is calculated to obtain the sum of the PARP value of preceding n symbol.It is every herein
A symbol divides the sampling number that fragment length is IFFT.This step handles the corresponding preceding n of available phase factor combination
The PARP value of a symbol；
S34：Obtained by the PARP value minimum value of n symbol before screening optimum phase corresponding to preceding n symbol because
Son, finally as n value successively increases, the corresponding optimum phase factor of m FBMC-OQAM symbol of available input；
As shown in Fig. 2, for traditional partial transmission sequence (Partial Transmission Sequence, PTS) side
Method and the PTS method for using novel phase factor, due to not accounting for the plyability of FBMC symbol, in threshold values (10-13) range
Interior, there is no improvement for PAPR performance, or even cause certain peak value hyperplasia.And MBJO-PTS algorithm and present invention joint used are calculated
Method (Multi-Block-Joint-Optimization Partial Transmission Sequence with New
Factor, MBJO-Newfactor-PTS) do not cause peak value proliferative conditions, it is more obvious to improve PAPR performance.Using connection
Hop algorithm ratio MBJO-PTS algorithm improves PAPR performance more preferably, and experiment parameter is as shown in table 1.
The main simulation parameter of table 1
For entire FBMC-OQAM signal, (L is neededP+ 1) the filtered signal of MN real multiplications, wherein N is to send
Symbol numbers, LPFor the length of filter.Signal is divided into after v group, and every group of carry out IFFT modulation needs v (L altogetherP+M/2)M
A complex multiplication, and (v-1) (LP+ M/2) M complex addition, each complex multiplication contains 4 real multiplications and 2 real numbers
Addition；Each complex addition contains 2 real additions.It is each to be grouped shared ω for traditional PTS algorithmvKind combination is divided
Match, needs v (LP+ M/2) a complex multiplication, and (v-1) (LP+ M/2) a complex addition.In general, the time needed for multiplication and
Hardware resource is greater than addition, therefore is (4vN (L for the real multiplications computation complexity of traditional PTS algorithmP+M/2)(N+
ωv)+2(LP+ 1) MN), for unified algorithm, each data segment phase combination has ωvKind, need vLPComplex multiplication, and (v-1)
LPComplex addition, furthermore it is a to share (N+K) for data slot, therefore the real multiplications computation complexity of unified algorithm is (4v (LP+
NM-M/2)(N+ωv)+2(LP+1)MN).As shown in figure 3, the computation complexity of unified algorithm is lower than traditional PTS algorithm.
S4：The optimum angle factor obtained above is multiplied with the data after IFFT transformation, at PPN module
Reason completes signal filtering.Generate FIR filter time domain impulse response matrix h, the length is overlap factor and IFFT point number it
Product.The process flow is divided into three steps：
S41：Setup parameter filter tap coefficients matrix；
S42：Setup parameter IFFT point number M and overlap factor COEFFICIENT K extract filter impulse receptance function with M times
To M group, every group contains K data, then each circuit-switched data after IFFT is done convolution with K data of M group respectively；
S43：By every group of K data respectively with M times of interpolation zero padding, finally it is delayed addition；
S5：Repeat above step, after obtaining Q circuit-switched data, the half in delayed symbol period is added with the road I, generation with compared with
The FBMC waveform of low PAPR.
Finally, it is stated that preferred embodiment above is only used to illustrate the technical scheme of the present invention and not to limit it, although logical
It crosses above preferred embodiment the present invention is described in detail, however, those skilled in the art should understand that, can be
Various changes are made to it in form and in details, without departing from claims of the present invention limited range.
Claims (6)
1. a kind of filter bank multi-carrier transmitter implementation method, which is characterized in that this approach includes the following steps：
S1：By the data flow of transmission carry out staggeredly it is orthogonal (Offset Quadrature Amplitude Modulation,
OQAM it) modulates, the data flow of modulation number is then subjected to data block grouping, and carry out IFFT respectively；
S2：Papr (Peak to Average Power Ratio, PAPR) suppression module is designed, is realized optimal
Phase search after obtaining the optimum angle factor, is multiplied with data block after each group IFFT respectively；
S3：Design PPN module, by after every group of optimization data block input multiphase filtering network (Polyphase Network,
PPN it) is added afterwards；
S4：The delay of I/Q two-way is added, and generates filter bank multi-carrier (Filter Bank Multicarrier, FBMC) signal.
2. a kind of filter bank multi-carrier transmitter implementation method according to claim 1, which is characterized in that the step
S1 specifically includes following steps：
S11：The data flow of transmission is subjected to OQAM modulation；
S12：Data flow carries out carrier wave distribution and the insertion of training sequence, and complete serioparallel exchange after OQAM modulation
Process；
S13：Carrier wave classifier modules are called, setting parameter FFT counts, and passes through the parameter setting total number of sub-carriers mesh；
S14：Training sequence parameter is set and generates synchronization character one and synchronization character two；
S15：Setting occupies subcarrier parameter, realizes subcarrier maps；
S16：After setting the above parameter, by data flow multiplied by linear phase matrix, then IFFT transformation is carried out.
3. a kind of filter bank multi-carrier transmitter implementation method according to claim 1 or 2, which is characterized in that described
OQAM modulation, specifically includes following steps：
S111：The data flow of transmission is completed into QAM mapping；
S112：It carries out the QAM complex symbol being mapped to take real and imaginary parts, obtains data vector D；
S113：By obtained data vector D multiplied by vector thetak,mIt is alternate to carry out frequency domain actual situation, θk,mValue is shown below：
Wherein, k is subcarrier index, and m is symbolic label.
4. a kind of filter bank multi-carrier transmitter implementation method according to claim 1, which is characterized in that the step
S2 specifically includes following steps：The PAPR suppression module combines the partial transmission sequence (Improved of novel phase factor
Partial Transmission Sequence, Improved-PTS) algorithm and more data block combined optimizations fractional transmission sequence
Arrange (Multi-Block-Joint-Optimization Partial Transmission Sequence, MBJO-PTS) algorithm
PAPR inhibition is carried out to FBMC waveform and is divided into v wherein the data block inputted is the m OQAM symbol modulated
Group is expressed as a vector：
Wherein m is sign flag,Indicate that the kth group data of m symbol, this group of data are passed through after IFFT, the sequence of signal
It is expressed as：
Wherein k is subcarrier index, and M indicates IFFT point number；
The phase factor matrix of symbol m is expressed as：
WhereinThe phase factor for indicating the kth group of m symbol, meets following equation：
Wherein ω is discrete phase number, and after every group multiplied by phase factor, m-th of symbol sebolic addressing is expressed as：
Wherein,WithRespectively indicate kth group data by the first half and latter half after IFFT, i.e.,：
WithRespectively indicate the first half of kth group and the phase factor of latter half, first half and latter half
Phase respectively byWithIt indicates, the two meets following equation：
α value is 0~0.5, when optimizing than the m-th data block, the plyability of m data block before this method only considers；Before assuming that
The phase factor of m-1 data block is it has been determined that the objective function of optimization than the m-th data block is：
Subject to
bm=bm+1=...=bM-1=0
Wherein K is overlap factor, PqThe value for indicating q sections of PAPR is expressed as with following formula：
Wherein, L indicates that the total number of transmitting symbol, n indicate discrete time-domain label, SnIndicate that the n moment sends time-domain value, E | Sn
|2Indicate that the n moment sends time domain energy mean value.
5. a kind of filter bank multi-carrier transmitter implementation method according to claim 4, which is characterized in that the step
S3 is specifically included：The optimum angle factor is obtained by step S2, and the optimum angle factor is mutually multiplied respectively at each group of data block
To parallel M circuit-switched data, sharing group number is v；If the time domain impulse response length of filter is LP=K*M, to it with interval M progress
Displacement is extracted, and M group decimation value is obtained, and the number of every class value is K；The M circuit-switched data that each group has been optimized is taken out with K of M group respectively
After sample value makees convolution algorithm, every circuit-switched data carries out M sampling, and delay, which is added, obtains the data that data length is K*M；More than repeating
After step v times, the data obtained is overlapped mutually to obtain I circuit-switched data；In heterogeneous structure, M point is directly carried out to data flow first
IFFT, calculating total amount is about M*log2M。
6. a kind of filter bank multi-carrier transmitter implementation method according to claim 5, which is characterized in that the step
S4 specifically includes following steps：Step S3 is repeated, after obtaining Q circuit-switched data, the half in delayed symbol period is added with the road I, is generated
FBMC waveform with lower PAPR.
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109951194A (en) * | 2019-01-30 | 2019-06-28 | 华中科技大学 | A kind of data transmission method |
| CN112995085A (en) * | 2021-02-08 | 2021-06-18 | 重庆邮电大学 | GFDM carrier system optimization method based on FW-CCDF algorithm |
| CN115225443A (en) * | 2022-06-28 | 2022-10-21 | 苏州大学 | Carrier cyclic shift method and cyclic shift optical filter bank multi-carrier system |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101340417A (en) * | 2008-08-28 | 2009-01-07 | 北京交通大学 | Improved iterative PTS method for lowering peak-average-ratio in OFDM system |
| CN105681241A (en) * | 2016-01-06 | 2016-06-15 | 北京邮电大学 | Method and device for reducing peak-to-average power ratio of FBMC-OQAM signal |
| CN106789828A (en) * | 2016-12-26 | 2017-05-31 | 中南大学 | A kind of method that FBMC OQAM system peak-to-average power ratios are reduced based on peak time tracking feedback |
| CN107196886A (en) * | 2017-04-24 | 2017-09-22 | 北京航空航天大学 | A kind of constellation Choose for user method based on selection window |
-
2018
- 2018-07-02 CN CN201810705720.6A patent/CN108848047B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101340417A (en) * | 2008-08-28 | 2009-01-07 | 北京交通大学 | Improved iterative PTS method for lowering peak-average-ratio in OFDM system |
| CN105681241A (en) * | 2016-01-06 | 2016-06-15 | 北京邮电大学 | Method and device for reducing peak-to-average power ratio of FBMC-OQAM signal |
| CN106789828A (en) * | 2016-12-26 | 2017-05-31 | 中南大学 | A kind of method that FBMC OQAM system peak-to-average power ratios are reduced based on peak time tracking feedback |
| CN107196886A (en) * | 2017-04-24 | 2017-09-22 | 北京航空航天大学 | A kind of constellation Choose for user method based on selection window |
Non-Patent Citations (3)
| Title |
|---|
| CHEN YE等: "PAPR Reduction of OQAM-OFDM Signals Using Segmental PTS Scheme With Low Complexity", 《IEEE TRANSACTIONS ON BROADCASTING》 * |
| DAIMING QU等: "Multi-Block Joint Optimization for the Peak-to-Average Power Ratio Reduction of FBMC-OQAM Signals", 《IEEE TRANSACTIONS ON SIGNAL PROCESSING》 * |
| 吴垒: "一种低复杂度降低FBMC OQAM峰均值比的PTS双层搜索算法", 《科学技术与工程》 * |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109951194A (en) * | 2019-01-30 | 2019-06-28 | 华中科技大学 | A kind of data transmission method |
| CN112995085A (en) * | 2021-02-08 | 2021-06-18 | 重庆邮电大学 | GFDM carrier system optimization method based on FW-CCDF algorithm |
| CN115225443A (en) * | 2022-06-28 | 2022-10-21 | 苏州大学 | Carrier cyclic shift method and cyclic shift optical filter bank multi-carrier system |
| CN115225443B (en) * | 2022-06-28 | 2023-08-25 | 苏州大学 | Carrier cyclic shift method and cyclic shift optical filter bank multi-carrier system |
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