CN108631600A - Double dual two-way interior phase-shifting control methods of active bridging parallel operation minimum reflux power - Google Patents

Double dual two-way interior phase-shifting control methods of active bridging parallel operation minimum reflux power Download PDF

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CN108631600A
CN108631600A CN201810477531.8A CN201810477531A CN108631600A CN 108631600 A CN108631600 A CN 108631600A CN 201810477531 A CN201810477531 A CN 201810477531A CN 108631600 A CN108631600 A CN 108631600A
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switching tube
phase shift
voltage
drive signal
output
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CN108631600B (en
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张兴
高帅
赵文广
郭华越
王付胜
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Hefei University of Technology
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Hefei University of Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses double active dual two-way interior phase-shifting control methods of bridging parallel operation minimum reflux power.It is transmitted in invariable power, compared with dual phase shift modulation, dual two-way interior phase shift modulation, which has, inhibits outer phase shift duty ratio to disturb the advantage that internal phase shift duty ratio influences, so that control system is more stablized, transimission power is more steady.This method is to propose a kind of minimum reflux Poewr control method on the basis of dual two-way interior phase shift modulation.This method can find reflux power optimized operating point and effectively improve the efficiency of converter to which reflux power be greatly lowered when exporting different capacity by automatic adjustment.Therefore, for relatively dual phase shift modulation, the method for the present invention is more suitably applied in double systems of the active bridging parallel operation as energy transmission unit, especially requires control stability high occasion.Foreground is very extensive, easy to spread.

Description

Double dual two-way interior phase-shifting control methods of active bridging parallel operation minimum reflux power
Technical field
The invention belongs to the two-way DC converter energy transmission technologies of electrical engineering field, and in particular to double active bridgings The dual two-way interior phase-shifting control method of parallel operation minimum reflux power.
Background technology
Double active bridge (Dual Active Bridge, DAB) converters have to and fro flow of power, high power density, low Cost, high reliability and efficient feature.It is increasingly used in high-power energy transmission.Common modulator approach has Tradition phase-shifting expands phase shift, dual phase shift, triple phase shifts.For different modulator approaches, all exist back in energy transport The problem of flowing power, i.e. the ac output voltage U when primary side H bridgesabWith inductive current iLWhen direction is opposite, the energy that is stored in inductance Amount flows back into input voltage U1The power of side, this part is reflux power Q.
Reflux power Q directly affects the efficiency of transmission of double active bridging parallel operations.Therefore, minimum reflux power how is realized Operation receives more and more attention.This existing scientific paper has done this deep theory analysis, also there is the work of practical application Cheng Fangfa.Currently, for the optimization of DAB reflux power is primarily directed to different modulation.Such as application for a patent for invention 《A kind of DC-DC converter of reload buffer device and the method for reducing reflux power》(107911028 A of CN) and patent of invention Shen Please《Isolation type bidirectional DC converter minimum reflux power phase-shifting control method》(CN 106981992 A).
Wherein, 107911028 A of Chinese invention patent application prospectus CN are disclosed in 13 days April in 2018《One The DC-DC converter of kind reload buffer device and the method for reducing reflux power》Reduce reflux under phase shift modulation aiming at expanding The method of power, has the following disadvantages：
Although reflux power optimized control 1, is realized, using expansion phase shift modulation method, primary side H bridge output waves Shape is three level, and secondary side H bridge output waveforms are two level, i.e., former secondary side H bridge voltages transition status is different, and control system is not easy reality It is existing.
2, it expands phase shift modulation and only introduces interior phase shifting angle in the side H bridges of transformer, with the control of dual phase shift modulation Degree of freedom is identical, but compared to dual phase shift modulation, expands phase shift modulation not there is only asymmetry, and dynamic property compared with Difference.
106981992 A of Chinese invention patent application prospectus CN are disclosed in 25 days July in 2017《Isolated form Two-way DC converter minimum reflux power phase-shifting control method》Aiming at the side for reducing reflux power under dual phase shift modulation Method has the following disadvantages：
Although 1, realizing reflux power optimized control, this modulator approach is when invariable power transmits, outer phase shift Duty ratio D2Small variation will produce interior phase shift duty ratio D1Larger variation causes control system unstable.Therefore, the tune The not applicable occasion high to stability requirement of method processed.
2, using dual phase shift modulation, the small variation of outer phase shift duty ratio at light load will produce prodigious surge current, Switching tube IGBT can be damaged when serious.
Entitled " Novel Dual-Phase-Shift Control With Bidirectional Inner Phase Shifts for a Dual-Active-Bridge Converter Having Low Surge Current and Stable Power Control, X.Liu, Senior Member, IEEE, Z.Q.Zhu, Fellow, IEEE, David A.Stone, Martin P.Foster, W.Q.Chu, Iain Urquhart, and James Greenough,《Power Electronics, IEEE Transactions on》, vol.32, No.5pp.4095-5106,2017 (" have low surge current and firm power Double active dual two-way interior phase shifting controls of bridging parallel operation of control ",《IEEE journals-power electronics periodical》, 2017 volume 32 Page 4095~5106) article solve the problems, such as above-mentioned dual phase shift invariable power transmission in stability of control system, still How when exporting different capacity realize minimum reflux Power operation do not refer to also.
A kind of double typical application scenarios of active bridging parallel operation be exactly can source router, as energy transmission unit in system In play the role of energy two-way transmission and stable DC busbar voltage.For this application scenario, double active bridging parallel operation controls The stability of system processed seems most important.The reduction of reflux power plays an important role to improving system effectiveness.Therefore, if Meter meets the minimum reflux power control that dual two-way interior phase shift modulation requires and is of great significance to improving system effectiveness.This hair Bright method solves the problems, such as it is how to realize minimum reflux power when exporting different capacity based on dual two-way interior phase shift modulation Operation.
Invention content
The purpose of the present invention is on the basis of existing dual two-way interior phase shift modulation method, further solve output not The problem of with minimum reflux Power operation is realized when power, to make the reflux power of double active bridging parallel operations be greatly lowered, And realize that reflux Power Theory value is zero in certain power bracket.
To solve the technical problem of the present invention, used technical solution is：A kind of double active bridging parallel operation minimum refluxs The topological structure of the dual two-way interior phase-shifting control method of power, double active bridging parallel operations involved by this control method includes direct current Voltage source, an input capacitance Ci, a primary side H bridge, a phase shift inductance L, a high frequency transformer, secondary side H bridges, one A output capacitance CoWith a load resistance R；The primary side H bridges are by four switching tube IGBT, four anti-paralleled diodes and four A parasitic capacitance composition, four switching tube IGBT are denoted as switching tube IGBTS respectively1, switching tube IGBTS2, switching tube IGBTS3, open Close pipe IGBTS4, four anti-paralleled diodes are denoted as D respectively1、D2、D3、D4, four parasitic capacitances are denoted as C respectively1、C2、C3、C4； The pair side H bridges are made of four switching tube IGBT, four anti-paralleled diodes and four parasitic capacitances, four switching tube IGBT It is denoted as switching tube IGBTS respectively5, switching tube IGBTS6, switching tube IGBTS7, switching tube IGBTS8, four anti-paralleled diodes point D is not denoted as it5、D6、D7、D8, four parasitic capacitances are denoted as C respectively5、C6、C7、C8；
The direct voltage source and input capacitance CiPrimary side H bridge direct-flow input ends, the exchange of primary side H bridges are connected to after in parallel Output end a points are connected to one end of phase shift inductance L, and the other end of phase shift inductance L is connected to the Same Name of Ends of high frequency transformer primary side a1, the different name end b of high frequency transformer primary side1It is connect with primary side H bridge ac output end b points；The Same Name of Ends c of transformer secondary1With pair Side H bridge ac input end c points connection, the different name end d of transformer secondary1It is connect with secondary side H bridge ac input ends d points, output electricity Hold CoIt is parallel-connected to secondary side H bridge DC output ends with load resistance R；
The control method includes the following steps：
Step 1：Sampling and outputting voltage U2, input voltage U1, output current i2, load current io；
Step 2：Output power P, and output power perunit value p are acquired in the following way：
P=U2×i0
P=P/PB
In formula, PBOn the basis of power, PB=nU1Un/ (8fL), n are the no-load voltage ratio of high frequency transformer, n=1, UnFor output voltage Rated value, f are switching frequency, f=1/Ts,TsIt is switch periods, L is phase shift inductance；
Step 3, the output power perunit value p and critical output power p obtained according to step 2maxRelationship, determining double has The interior phase shift duty ratio D of source bridging parallel operation1,
If p ＜ pmax,
If p >=pmax,
In formula,K is voltage conversion ratio, and the voltage conversion ratio k is defined as input voltage U1 With output voltage U2With the ratio of high frequency transformer no-load voltage ratio n products,And 0<k≤1；
Step 4, double active bridging parallel operation output voltage U step 1 sampling obtained2With outer voltage given value U*It makes the difference Voltage error signal Δ U is obtained, voltage error signal Δ U input PI controllers 1 are obtained into inner ring given value i2 *, then by inner ring Given value i2 *With output current average valueCurrent error signal Δ I is made the difference to obtain, current error signal Δ I is inputted into PI controllers 2 obtain outer phase shift duty ratio D2；
Step 4.1, first by the given value U of outer voltage*Obtained output voltage U is sampled with step 12It makes the difference to obtain voltage Error signal Δ U, Δ U=U*-U2, then using voltage error signal Δ U as the input of PI controllers 1, obtain inner ring given value i2 *；The PI controllers 1 are pi controller, transmission function GPI1(s)Expression formula it is as follows：
Wherein, s is Laplace operator, kp1For 1 ratio term coefficient of PI controllers, ki1Term system is integrated for PI controllers 1 Number；
Step 4.2, inner ring given value i step 4.1 obtained2 *Subtract output current average valueObtain current error letter Number Δ I, expression formula are as follows：
In formula,For output current average value,M is sampling number, i2mFor output current i2The m times Sampled value；
Step 4.3, current error signal Δ I step 4.2 obtained obtains outer phase shift as the input of PI controllers 2 Duty ratio D2；The PI controllers 2 are pi controller, PI controller transfer functions GPI2(s)Expression formula it is as follows：
Wherein, kp2For 2 ratio term coefficient of PI controllers, ki2For 2 integral item coefficient of PI controllers；
Step 5, the interior phase shift duty ratio D obtained according to step 31The outer phase shift duty ratio D obtained with step 42, and enable D1、 D2Meet following three conditions simultaneously：
0≤D1≤D2/2
0≤D1≤1
0≤D2≤1
According to dual two-way interior phase shift modulation method, with switching tube IGBTS1Drive signal Q1On the basis of, generate respectively with Switching tube IGBTS1, switching tube IGBTS2, switching tube IGBTS3, switching tube IGBTS4, switching tube IGBTS5, switching tube IGBTS6、 Switching tube IGBTS7, switching tube IGBTS8Corresponding drive signal Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8, drive each switching tube IGBT so that output voltage U2It maintains to stablize.
Preferably, the particular content of dual two-way interior phase shift modulation method described in step 5 includes：
(1) the switching tube IGBTS of primary side H bridges1, switching tube IGBTS2, switching tube IGBTS3, switching tube IGBTS4Driving Signal Q1、Q2、Q3、Q4With the switching tube IGBTS of secondary side H bridges5, switching tube IGBTS6, switching tube IGBTS7, switching tube IGBTS8's Drive signal Q5、Q6、Q7、Q8Frequency is identical, switching tube IGBTS1With switching tube IGBTS2Complementation conducting, switching tube IGBTS3With open Close pipe IGBTS4Complementation conducting, switching tube IGBTS5With switching tube IGBTS6Complementation conducting, switching tube IGBTS7With switching tube IGBTS8Complementation conducting；
(2) switching tube IGBTS4Drive signal Q4Lag behind switching tube IGBTS1Drive signal Q1, switching tube IGBTS3 Drive signal Q3Lag behind switching tube IGBTS2Drive signal Q2, lag time is TΔ1,
(3) switching tube IGBTS8Drive signal Q8It is ahead of switching tube IGBTS5Drive signal Q5, switching tube IGBTS7 Drive signal Q7It is ahead of switching tube IGBTS6Drive signal Q6, the leading time is identical as the lag time in aforementioned (2), I.e. the leading time is also TΔ1,
(4) switching tube IGBTS5Drive signal Q5Lag behind switching tube IGBTS1Drive signal Q1, switching tube IGBTS6 Drive signal Q6Lag behind switching tube IGBTS2Drive signal Q2, lag time is TΔ2,
Double active dual two-way interior phase-shifting control methods of bridging parallel operation minimum reflux power disclosed by the invention, based on double On the basis of the two-way interior phase shift modulation of weight, it can realize that minimum reflux Power operation, advantage are specific when exporting different capacity It is embodied in：
1, on the basis of dual two-way interior phase shift modulation so that can realize minimum reflux power when output different capacity Operation, especially in output power perunit value p<Critical output power pmaxWhen, theory reflux power is zero.In output power perunit Value p >=critical output power pmaxWhen, meet and minimum reflux Power operation may be implemented under conditions of demanded power output.
2, dual two-way interior phase shift modulation itself, which has, inhibits outer phase shift duty ratio D2The interior phase shift duty ratio D that disturbed belt comes1 The problem of fluctuating widely.Therefore, there is better vulnerability to jamming in stable state transimission power so that the stability of control system carries It is high.
3, for relatively dual phase shift modulation, the method for the present invention is more suitably applied to double active bridging parallel operations and is passed as energy In the system of defeated unit, high occasion especially is required to double active bridging parallel operation control stabilities, foreground is very extensive, is easy to It promotes.
Description of the drawings
Fig. 1 is double active bridge converter topology schematic diagrames.
Fig. 2 is dual phase shift modulation schematic diagram.
Fig. 3 is the dual two-way interior phase shift modulation schematic diagram that the present invention uses.
Fig. 4 is the equal output powers perunit value p line charts based on dual two-way interior phase shift modulation.
Fig. 5 is the equal reflux power perunit value q line charts based on dual two-way interior phase shift modulation.
Fig. 6 is that the method for the present invention meets inside and outside phase shift duty ratio trajectory diagram when minimum reflux Power operation.
Fig. 7 is the control structure figure of the method for the present invention.
Fig. 8 is the comparison figure of two methods reflux power perunit value q.
Fig. 9 is the analogous diagram of power waveform M when load is 32 Ω when not using the method for the present invention.
Figure 10 is the analogous diagram of power waveform M when load is 32 Ω when using the method for the present invention.
Figure 11 is the analogous diagram of power waveform M when load is 27 Ω when not using the method for the present invention.
Figure 12 is the analogous diagram of power waveform M when load is 27 Ω when using the method for the present invention.
Figure 13 is the output voltage U of the method for the present invention2Oscillogram.
Figure 14 inside and outside phase shift change in duty cycle figures when being based on power of the present invention switching.
Figure 15 is phase shift change in duty cycle figure in the outer phase shift duty ratio disturbance of dual phase shift modulation is lower.
Figure 16 is phase shift change in duty cycle figure in the outer phase shift duty ratio disturbance of dual two-way interior phase shift modulation is lower.
Specific implementation mode
Fig. 1 is double active bridge converter topology schematic diagrames according to the present invention.As seen from Figure 1, involved by this control method And the topological structures of double active bridging parallel operations include direct voltage source, an input capacitance Ci, a primary side H bridge, a shifting Phase inductance L, a high frequency transformer, secondary side H bridges, an output capacitance CoWith a load resistance R.
The primary side H bridges are made of four switching tube IGBT, four anti-paralleled diodes and four parasitic capacitances, and four are opened It closes pipe IGBT and is denoted as switching tube IGBTS respectively1, switching tube IGBTS2, switching tube IGBTS3, switching tube IGBTS4, four inverse parallels Diode is denoted as D respectively1、D2、D3、D4, four parasitic capacitances are denoted as C respectively1、C2、C3、C4；The pair side H bridges are switched by four Pipe IGBT, four anti-paralleled diodes and four parasitic capacitance compositions, four switching tube IGBT are denoted as switching tube IGBTS respectively5、 Switching tube IGBT S6, switching tube IGBTS7, switching tube IGBTS8, four anti-paralleled diodes are denoted as D respectively5、D6、D7、D8, four A parasitic capacitance is denoted as C respectively5、C6、C7、C8。
The direct voltage source and input capacitance CiPrimary side H bridge direct-flow input ends, the exchange of primary side H bridges are connected to after in parallel Output end a points are connected to one end of phase shift inductance L, and the other end of phase shift inductance L is connected to the Same Name of Ends of high frequency transformer primary side a1, the different name end b of high frequency transformer primary side1It is connect with primary side H bridge ac output end b points；The Same Name of Ends c of transformer secondary1With pair Side H bridge ac input end c points connection, the different name end d of transformer secondary1It is connect with secondary side H bridge ac input ends d points, output electricity Hold CoIt is parallel-connected to secondary side H bridge DC output ends with load resistance R.
Related electric parameter setting when the present invention is implemented is as follows：Input voltage U1=400V, output voltage rated value Un= 400V, output voltage U2Stablized in 400V, i.e. U by the control of outer voltage average output current inner ring2=Un, voltage conversion ratio k =1, phase shift inductance L=120 μ H, input capacitance Ci=110 μ F, output capacitance Co=110 μ F, load resistance R=32 Ω.
Control method of the present invention includes sampling and outputting voltage U2, input voltage U1, output current i2And load current io, steps are as follows：
Step 1：Sampling and outputting voltage U2, input voltage U1, output current i2, load current io。
Step 2：Output power P, and output power perunit value p are acquired in the following way：
P=U2×i0
P=P/PB
In formula, PBOn the basis of power, PB=nU1Un/ (8fL), n are the no-load voltage ratio of high frequency transformer, n=1, UnFor output voltage Rated value, f are switching frequency, f=1/Ts,TsIt is switch periods, L is phase shift inductance.
In the present embodiment, phase shift inductance L=120 μ H, input voltage U1=400V, output voltage rated value Un=400V, Switching frequency f=20kHz, then PB=8333w, p=P/8333.
Dual phase shift modulation is with dual two-way interior phase shift modulation principle referring to Fig. 2, Fig. 3, wherein UabIt is the exchange of primary side H bridges Output voltage, UcdIt is secondary side H bridge AC-input voltages, iLIt is inductive current.The method of the present invention uses dual two-way interior phase shift tune Principle processed meets 0≤D at the same time1≤D2/2,0≤D1≤1,0≤D2Under conditions of≤1, with PBOn the basis of power, obtain its output Power perunit value p expression formulas are p=-2 [3D1 2+D1(2-4D2)+2D2(D2- 1)], reflux power perunit value q expression formulas are Based on the present embodiment, Fig. 4 gives the equal output powers mark based on dual two-way interior phase shift modulation The one value p line charts, all point output power perunit value p on the same line are identical；Fig. 5 gives based on dual two-way interior phase shift tune The equal power perunit value q line charts that flow back of system, all the points reflux power perunit value q on the same line are identical.In addition output power Perunit value p, reflux power perunit value q increase with the direction of arrow in figure.
Step 3, the output power perunit value p and critical output power p obtained according to step 2maxRelationship, determining double has The interior phase shift duty ratio D of source bridging parallel operation1,
If p ＜ pmax,
If p >=pmax,
In formula,K is voltage conversion ratio, and the voltage conversion ratio k is defined as input voltage U1 With output voltage U2With the ratio of high frequency transformer no-load voltage ratio n products,And 0<k≤1.
In the present embodiment, voltage conversion ratio k=1, then：
Step 4, the double active bridging parallel operation output voltage U obtained according to step 1 sampling2With outer voltage given value U*It does Difference obtains voltage error signal Δ U, and voltage error signal Δ U input PI controllers 1 are obtained inner ring given value i2 *, then will be interior Ring given value i2 *With output current average valueCurrent error signal Δ I is made the difference to obtain, by the I input PI controls of current error signal Δ Device 2 obtains outer phase shift duty ratio D2。
Step 4.1, first by the given value U of outer voltage*Obtained output voltage U is sampled with step 12It makes the difference to obtain voltage Error signal Δ U, Δ U=U*-U2, then using voltage error signal Δ U as the input of PI controllers 1, obtain inner ring given value i2 *；The PI controllers 1 are pi controller, transmission function GPI1(s)Expression formula it is as follows：
Wherein, s is Laplace operator, kp1For 1 ratio term coefficient of PI controllers, ki1Term system is integrated for PI controllers 1 Number；
Step 4.2, inner ring given value i step 4.1 obtained2 *Subtract output current average valueObtain current error letter Number Δ I, expression formula are as follows：
In formula,For output current average value,M is sampling number, i2mFor output current i2M Secondary sampled value；
Step 4.3, current error signal Δ I step 4.2 obtained obtains outer phase shift as the input of PI controllers 2 Duty ratio D2；The PI controllers 2 are pi controller, PI controller transfer functions GPI2(s)Expression formula it is as follows：
Wherein, kp1For 1 ratio term coefficient of PI controllers, ki1For 1 integral item coefficient of PI controllers, kp2Compare for PI controllers 2 Item coefficient, ki2For 2 integral item coefficient of PI controllers.
In the present embodiment, outer voltage given value U*=400V, kp1=0.00312, ki1=5.2, kp2=0.0096, ki2=96.15.The interior phase shift duty ratio D obtained by step 31The outer phase shift duty ratio D obtained with step 42Meet：If output Power perunit value D2=2D1, theoretically reflux power is zero at this time；If output power perunit value D2=0.5D1+0.5.Referring to attached drawing 6, meet for the method for the present invention interior when minimum reflux Power operation Outer phase shift duty ratio trajectory diagram.
Step 5, the interior phase shift duty ratio D obtained according to step 31The outer phase shift duty ratio D obtained with step 42, and enable D1、 D2Meet following three conditions simultaneously：
0≤D1≤D2/2
0≤D1≤1
0≤D2≤1
According to dual two-way interior phase shift modulation method, with switching tube IGBTS1Drive signal Q1On the basis of, generate respectively with Switching tube IGBTS1, switching tube IGBTS2, switching tube IGBTS3, switching tube IGBTS4, switching tube IGBTS5, switching tube IGBTS6、 Switching tube IGBTS7, switching tube IGBTS8Corresponding drive signal Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8, drive each switching tube IGBT so that output voltage U2It maintains to stablize.
Wherein, the particular content of the dual two-way interior phase shift modulation method includes：
(1) the switching tube IGBTS of primary side H bridges1, switching tube IGBTS2, switching tube IGBTS3, switching tube IGBTS4Driving Signal Q1、Q2、Q3、Q4With the switching tube IGBTS of secondary side H bridges5, switching tube IGBTS6, switching tube IGBTS7, switching tube IGBTS8's Drive signal Q5、Q6、Q7、Q8Frequency is identical, switching tube IGBTS1With switching tube IGBTS2Complementation conducting, switching tube IGBTS3With open Close pipe IGBTS4Complementation conducting, switching tube IGBTS5With switching tube IGBTS6Complementation conducting, switching tube IGBTS7With switching tube IGBTS8Complementation conducting.
(2) switching tube IGBTS4Drive signal Q4Lag behind switching tube IGBTS1Drive signal Q1, switching tube IGBTS3 Drive signal Q3Lag behind switching tube IGBTS2Drive signal Q2, lag time is TΔ1,
(3) switching tube IGBTS8Drive signal Q8It is ahead of switching tube IGBTS5Drive signal Q5, switching tube IGBTS7 Drive signal Q7It is ahead of switching tube IGBTS6Drive signal Q6, the leading time is identical as the lag time in aforementioned (2), I.e. the leading time is TΔ1,
(4) switching tube IGBTS5Drive signal Q5Lag behind switching tube IGBTS1Drive signal Q1, switching tube IGBTS6 Drive signal Q6Lag behind switching tube IGBTS2Drive signal Q2, lag time is TΔ2,
The control structure figure of the method for the present invention is as shown in Figure 7.
Fig. 8 is the comparison figure of two methods reflux power perunit value q.Optimization method of the present invention is used in the present embodiment With the comparison figure for the power perunit value q that do not flowed back using optimization method of the present invention, hence it is evident that it can be seen that using optimization method of the present invention Afterwards, reflux power has obtained good inhibition.
The advantages of the method for the present invention is not compared to the method for the present invention is used is specifically observed below by emulation.Pass through emulation It is verified, Fig. 9 is the analogous diagram of power waveform M when load is 32 Ω when not using the method for the present invention, wherein below horizontal axis Part be exactly the power that flows back.Figure 10 is the analogous diagram of power waveform M when load is 32 Ω when using the method for the present invention, and correspondence is attached A points in Fig. 6, output power perunit value p is 0.6, because A points are less than critical transimission power pmax, so theoretical reflux power Q is Zero.Apparent can be seen that is optimized using the method for the present invention reflux power.At a time load switching, Figure 11 is not adopt With the analogous diagram of power waveform M when load is 27 Ω when the method for the present invention.Figure 12 is loaded as 27 Ω when using the method for the present invention When power waveform M analogous diagram, B points in corresponding diagram 6, because B points are more than critical transimission power pmax, while being output power mark The point of contact of one value p=0.71 lines and reflux power perunit value q=0.0012 lines, the power Q that theoretically flows back are small compared with other points.Pass through The comparison of Figure 11 and Figure 12 can be seen that reduces reflux power using minimum reflux Poewr control method proposed by the present invention.
Referring to Figure 13, under the control of outer voltage average output current inner ring, output voltage can be tieed up when different capacity switches It is fixed to keep steady.It is inside and outside phase shift duty ratio dynamic changing process during switching at runtime referring to Figure 14.As can be seen that after stablizing Inside and outside phase shift duty ratio meets the relationship of theory analysis.
Figure 15, Figure 16 are respectively dual phase shift modulation and the dual two-way interior phase shift modulation of the invention used in output power When perunit value p=0.1, interior phase shift duty ratio D1With outer phase shift duty ratio D2The oscillogram of variation gives outer phase shift in steady operation point Duty ratio D2Small disturbance Δ D2So that interior phase shift duty ratio generates disturbance Δ D1, hence it is evident that as can be seen that this hair in stable state The dual two-way interior external phase shift duty ratio D of phase shift modulation method of bright use2Disturbed belt come interior phase shift duty ratio D1Fluctuation Problem has good inhibiting effect.

Claims (2)

1. a kind of double active dual two-way interior phase-shifting control methods of bridging parallel operation minimum reflux power, which is characterized in that this control The topological structure of double active bridging parallel operations involved by method includes direct voltage source, an input capacitance Ci, a primary side H Bridge, a phase shift inductance L, a high frequency transformer, secondary side H bridges, an output capacitance CoWith a load resistance R；Institute It states primary side H bridges to be made of four switching tube IGBT, four anti-paralleled diodes and four parasitic capacitances, four IGBT points of switching tubes Switching tube is not denoted as itSwitching tubeSwitching tubeSwitching tubeFour two poles of inverse parallel Pipe is denoted as D respectively1、D2、D3、D4, four parasitic capacitances are denoted as C respectively1、C2、C3、C4；The pair side H bridges are by four switching tubes IGBT, four anti-paralleled diodes and four parasitic capacitance compositions, four switching tube IGBT are denoted as switching tube respectively Switching tubeSwitching tubeSwitching tubeFour anti-paralleled diodes are denoted as D respectively5、D6、D7、D8, Four parasitic capacitances are denoted as C respectively5、C6、C7、C8；
The direct voltage source and input capacitance CiPrimary side H bridge direct-flow input ends, the exchange output of primary side H bridges are connected to after in parallel End a points are connected to one end of phase shift inductance L, and the other end of phase shift inductance L is connected to the Same Name of Ends a of high frequency transformer primary side1, high The different name end b of frequency power transformer primary side1It is connect with primary side H bridge ac output end b points；The Same Name of Ends c of transformer secondary1With secondary side H bridges Ac input end c points connect, the different name end d of transformer secondary1It is connect with secondary side H bridge ac input ends d points, output capacitance CoWith Load resistance R is parallel-connected to secondary side H bridge DC output ends；
The control method includes the following steps：
Step 1：Sampling and outputting voltage U2, input voltage U1, output current i2, load current io；
Step 2：Output power P, and output power perunit value p are acquired in the following way：
P=U2×i0
P=P/PB
In formula, PBOn the basis of power, PB=nU1Un/ (8fL), n are the no-load voltage ratio of high frequency transformer, n=1, UnIt is specified for output voltage Value, f is switching frequency, f=1/Ts,TsIt is switch periods, L is phase shift inductance；
Step 3, the output power perunit value p and critical output power p obtained according to step 2maxRelationship, determine double active bridges The interior phase shift duty ratio D of converter1,
If p ＜ pmax,
If p >=pmax,
In formula,K is voltage conversion ratio, and the voltage conversion ratio k is defined as input voltage U1With it is defeated Go out voltage U2With the ratio of high frequency transformer no-load voltage ratio n products,And 0<k≤1；
Step 4, double active bridging parallel operation output voltage U step 1 sampling obtained2With outer voltage given value U*It makes the difference to obtain Voltage error signal Δ U input PI controllers 1 are obtained inner ring given value i by voltage error signal Δ U2 *, then inner ring is given Value i2 *With output current average valueCurrent error signal Δ I is made the difference to obtain, current error signal Δ I input PI controllers 2 are obtained To outer phase shift duty ratio D2；
Step 4.1, first by the given value U of outer voltage*Obtained output voltage U is sampled with step 12It makes the difference to obtain voltage error Signal delta U, Δ U=U*-U2, then using voltage error signal Δ U as the input of PI controllers 1, obtain inner ring given value i2 *； The PI controllers 1 are pi controller, transmission function GPI1(s)Expression formula it is as follows：
Wherein, s is Laplace operator, kp1For 1 ratio term coefficient of PI controllers, ki1For 1 integral item coefficient of PI controllers；
Step 4.2, inner ring given value i step 4.1 obtained2 *Subtract output current average valueObtain current error signal Δ I, expression formula are as follows：
In formula,For output current average value,M is sampling number, i2mFor output current i2It adopts for the m times Sample value；
Step 4.3, current error signal Δ I step 4.2 obtained obtains outer phase shift duty as the input of PI controllers 2 Compare D2；The PI controllers 2 are pi controller, PI controller transfer functions GPI2(s)Expression formula it is as follows：
Wherein, kp2For 2 ratio term coefficient of PI controllers, ki2For 2 integral item coefficient of PI controllers；
Step 5, the interior phase shift duty ratio D obtained according to step 31The outer phase shift duty ratio D obtained with step 42, and enable D1、D2Together When meet following three conditions：
0≤D1≤D2/2
0≤D1≤1
0≤D2≤1
According to dual two-way interior phase shift modulation method, with switching tubeDrive signal Q1On the basis of, generate respectively with open Guan GuanSwitching tubeSwitching tubeSwitching tubeSwitching tubeSwitching tubeSwitching tubeSwitching tubeCorresponding drive signal Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8, driving Each switching tube IGBT so that output voltage U2It maintains to stablize.
2. double active dual two-way interior phase-shifting control methods of bridging parallel operation minimum reflux power according to claim 1, It is characterized in that, the particular content of dual two-way interior phase shift modulation method described in step 5 includes：
(1) switching tube of primary side H bridgesSwitching tubeSwitching tubeSwitching tubeDriving Signal Q1、Q2、Q3、Q4With the switching tube of secondary side H bridgesSwitching tubeSwitching tubeSwitching tubeDrive signal Q5、Q6、Q7、Q8Frequency is identical, switching tubeWith switching tubeComplementation conducting, switch PipeWith switching tubeComplementation conducting, switching tubeWith switching tubeComplementation conducting, switching tubeWith switching tubeComplementation conducting；
(2) switching tubeDrive signal Q4Lag behind switching tubeDrive signal Q1, switching tube Drive signal Q3Lag behind switching tubeDrive signal Q2, lag time is TΔ1,
(3) switching tubeDrive signal Q8It is ahead of switching tubeDrive signal Q5, switching tube's Drive signal Q7It is ahead of switching tubeDrive signal Q6, the leading time is identical as the lag time in aforementioned (2), i.e., Leading time is also TΔ1,
(4) switching tubeDrive signal Q5Lag behind switching tubeDrive signal Q1, switching tube Drive signal Q6Lag behind switching tubeDrive signal Q2, lag time is TΔ2,
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CN110719030A (en) * 2019-08-27 2020-01-21 河北工业大学 Dual phase-shift modulation method for isolated bidirectional full-bridge DC-DC converter
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CN111416523B (en) * 2020-04-17 2021-07-30 合肥科威尔电源系统股份有限公司 Soft charging control system and method for double-active-bridge DC/DC converter
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CN113037097B (en) * 2021-04-29 2022-03-25 常熟理工学院 Modulation control method of resonant double-active-bridge converter
CN113179024A (en) * 2021-05-12 2021-07-27 福州大学 Discrete iteration prediction control model of three-phase-shift double-active full-bridge direct-current converter
CN114157160A (en) * 2021-12-06 2022-03-08 西安西电电力系统有限公司 Converter based on three active bridges and control method thereof

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