CN108390567B - Zero-voltage switch Boost circuit and control method thereof - Google Patents
Zero-voltage switch Boost circuit and control method thereof Download PDFInfo
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- CN108390567B CN108390567B CN201810294727.3A CN201810294727A CN108390567B CN 108390567 B CN108390567 B CN 108390567B CN 201810294727 A CN201810294727 A CN 201810294727A CN 108390567 B CN108390567 B CN 108390567B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
- H02M1/34—Snubber circuits
- H02M1/342—Active non-dissipative snubbers
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention provides a Boost circuit of a zero voltage switch and a control method thereof.A rectification circuit of a main power circuit is connected with an auxiliary resonance circuit in series, when a main power switch tube is switched off, the zero voltage conduction of the auxiliary switch tube is realized by using the current of a Boost inductor, then the resonance of a resonance capacitor and the resonance inductor is used for realizing the rapid increase of the current of the resonance inductor and promoting the current of the resonance inductor to be larger than the current of the Boost inductor, and the follow current of the resonance inductor is performed by using a diode which is connected with the resonance capacitor in parallel, so as to ensure that the voltage of the resonance capacitor cannot be reversed and the current of the resonance inductor cannot be rapidly reduced after the current reaches the maximum value. When the auxiliary switching tube is turned off, the zero voltage switching-on of the main switching tube is realized by utilizing the difference value of the resonance current and the Boost inductive current.
Description
Technical Field
The invention relates to a power electronic circuit, in particular to a zero-voltage switch Boost circuit and a control method thereof.
Background
A conventional power supply block diagram is shown in fig. 1, in which a bridge rectifier circuit 11 converts an AC input into a DC voltage and supplies the DC voltage to a Boost converter 20, the Boost converter provides a power factor correction function to meet an industry standard or simply converts a voltage with a large fluctuation into a stable voltage or a voltage range with a small variation range, and a DC/DC converter at a later stage converts an output voltage of the Boost converter into a voltage required by a load and performs an isolation function. Normally, the AC input range is 85-265 VAC, and the voltage stabilizing value of the Boost converter is 400V or the voltage stabilizing range is 200-400V. The narrower the output voltage range of the front-stage Boost circuit is, the simpler the design of the rear-stage DC/DC converter is, and the better the performance can be achieved.
A conventional Boost converter 20 is shown in fig. 2, when the main switch 22 is turned on by the control circuit 26, one end of the inductor 21 is short-circuited to ground through the main switch 22, and the other end of the inductor 21 is connected to the power supply, so that the input voltage Vin will increase the current in the inductor 21. Meanwhile, during the on-time of the main switch 22, the rectifier diode 23 is reversely biased to be in an off-state, and the output filter capacitor 24 supplies power to the load. When the main switch 22 is turned off by the control circuit 26, the inductor current cannot change abruptly, and the energy stored in the inductor 21 during the on time of the main switch 22 can be supplied to the load through the rectifier diode 23. The output filter capacitor 24 maintains the output voltage substantially constant. The on-time and off-time of the main switch 22 are determined by the control circuit 26 to ensure that the output voltage is a certain set voltage value.
With the development and progress of power electronic technology, power electronic circuits are being developed to have higher frequencies and smaller sizes. Due to the improvement of the working frequency, the power module can use smaller devices and has smaller volume. For the conventional Boost converter 20, there is switching loss during the switching of the main switching tube 22, and when the inductor current is continuous, there is reverse recovery loss in the rectifier diode 23, so that the high frequency operation will cause a significant increase in the switching loss of the conventional Boost converter 20 and a significant decrease in the module efficiency, and due to the increase in the converter loss and the decrease in the volume, the module will generate heat severely, and the reliability is significantly reduced. Zero voltage switching converters can greatly reduce switching losses, and thus, zero voltage switching converters are attracting more and more attention.
An existing Boost circuit for realizing ZVS is a synchronous rectification Boost circuit shown in a figure 6-1, PWM control is adopted, a working sequence waveform is shown in a figure 6-2, negative excitation of a Boost inductor is realized by using output voltage and a synchronous rectification diode, a main switching tube ZVS is realized by using negative inductive current, and the condition for realizing the working process is that the circuit works in a DCM mode, namely, the inductive current is zero-crossed. The circuit is suitable for occasions with low power, the negative current is obviously increased under light load, and the light load efficiency is not high.
Fig. 7 shows a control block diagram of a synchronous rectification Boost converter in another typical conventional control method, which includes detecting a negative current of a Boost inductor, an input voltage Vin, and an output voltage Vout for control, where Vout is detected to control output voltage stability, Vin is detected to set a minimum value of a negative current of the Boost inductor, and the negative current of the Boost inductor is detected to control turn-off of a synchronous rectification diode, which is PFM control. The working frequency is higher during light load, and the light load efficiency is lower; the working frequency is higher when the high voltage and light load are carried, and the high voltage and light load efficiency is lower.
Disclosure of Invention
Therefore, the invention provides a Boost circuit of a zero-voltage switch and a control method thereof, which are used for solving the problem of overlarge loss of a high-frequency working switch, solving the problem of reverse recovery of an inductive current continuous rectifier diode and solving the problem of EMI (electro-magnetic interference) generated by hard switching. Meanwhile, in order to improve the light load efficiency, the invention also provides a light load control method so as to further improve the overall efficiency of the Boost converter. And the control method automatically adapts to DCM (current discontinuous mode) and CCM (current continuous mode) operating modes.
A zero voltage switch Boost circuit comprises a Boost inductor 31, a main switch tube 32, a rectifier diode 33, an output filter capacitor 34, a control circuit 36 and a zero voltage switch circuit 40;
one end of the boost inductor 31 is connected with the input voltage +, the other end of the boost inductor 31 is connected with the drain electrode of the main switching tube 32, the source electrode of the main switching tube 32 is connected with the input voltage-, and the grid electrode of the main switching tube 32 is connected with one output end of the control circuit; the output voltage Vout at the two ends of the output filter capacitor 34 supplies power to the rear-stage load; the control circuit 36 generates a feedback voltage signal according to the output voltage Vout and adjusts the duty ratio of the main switching tube 32 according to the feedback voltage signal; the input end of the zero voltage switch circuit 40 is connected with the other end of the boost inductor 31, the output end of the zero voltage switch circuit 40 is connected with the anode of the rectifier diode 33, and the control end of the zero voltage switch circuit 40 is connected with the other output end of the control circuit; the cathode of the rectifier diode 33 is connected to the anode of the output filter capacitor 34.
Preferably, the zero-voltage switch Boost circuit further includes a CS current detection circuit, an input end of the CS current detection circuit is connected to a source electrode of the main switching tube 32, and is configured to detect a current of the source electrode of the main switching tube 32; and the output end of the CS current detection circuit is connected with the control circuit.
Preferably, the zero-voltage switching circuit 40 includes a resonant inductor 41, an auxiliary switching tube 42, and a resonant capacitor 44, wherein one end of the resonant inductor 41 is used as the input end of the zero-voltage switching circuit 40, and the other end of the resonant inductor 41 is used as the output end of the zero-voltage switching circuit 40; the source of the auxiliary switch tube 42 is connected to one end of the resonant inductor 41, the drain of the auxiliary switch tube 42 is connected to the anode of the resonant capacitor 44, and the cathode of the resonant capacitor 44 is connected to the other end of the resonant inductor 41; the gate of the auxiliary switch tube 42 serves as the control terminal of the zero voltage switch circuit 40.
Preferably, the zero-voltage switching circuit 40 further includes an auxiliary diode 43, a cathode of the auxiliary diode 43 is connected to an anode of the resonant capacitor 44, and an anode of the auxiliary diode 43 is connected to a cathode of the resonant capacitor 44.
Preferably, the control circuit controls the main switch tube 32 and the auxiliary switch tube 42 in a complementary driving manner.
Preferably, the main switch tube 32 and the auxiliary switch tube 42 are MOS tubes or IGBTs, and the auxiliary diode 43 is a schottky diode.
A control method of a zero-voltage switch Boost circuit comprises the following steps: the CS current detection circuit detects the peak current of the main switching tube 32, when the peak current is reduced to a set reference value, the minimum peak current is kept from being reduced under control, and when the peak current of the main switching tube 32 has a trend of being reduced continuously due to the fact that the input voltage is increased or the load is reduced continuously, the working frequency of the main switching tube 32 is reduced to stabilize the output of the Boost circuit; and when the working frequency of the main switching tube 32 reaches the minimum working frequency, the frequency hopping operation is entered.
A zero-voltage switching synchronous rectification Boost circuit comprises a Boost inductor 31, a main switching tube 32, an output filter capacitor 34, a synchronous rectification switching tube 81 and a zero-voltage switching circuit 40;
one end of the boost inductor 31 is connected with the input voltage +, the other end of the boost inductor 31 is connected with the drain electrode of the main switching tube 32, the source electrode of the main switching tube 32 is connected with the input voltage-, and the grid electrode of the main switching tube 32 is connected with one output end of the control circuit; the output voltage Vout at the two ends of the output filter capacitor 34 supplies power to the rear-stage load; the control circuit 36 generates a feedback voltage signal according to the output voltage Vout and adjusts the duty ratio of the main switching tube 32 according to the feedback voltage signal; the input end of the zero voltage switch circuit 40 is connected with the drain electrode of the main switch tube 32, the output end of the zero voltage switch circuit 40 is connected with the source electrode of the synchronous rectification switch tube 81, and the control end of the zero voltage switch circuit 40 is connected with the other output end of the control circuit; the drain of the synchronous rectification switch tube 81 is connected to the positive electrode of the output filter capacitor 34, and the gate of the synchronous rectification switch tube 81 is connected to the third output terminal of the control circuit.
Preferably, the zero-voltage switching circuit 40 includes a resonant inductor 41, an auxiliary switching tube 42, and a resonant capacitor 44, wherein one end of the resonant inductor 41 is used as the input end of the zero-voltage switching circuit 40, and the other end of the resonant inductor 41 is used as the output end of the zero-voltage switching circuit 40; the source of the auxiliary switch tube 42 is connected to one end of the resonant inductor 41, the drain of the auxiliary switch tube 42 is connected to the anode of the resonant capacitor 44, and the cathode of the resonant capacitor 44 is connected to the other end of the resonant inductor 41; the gate of the auxiliary switch tube 42 serves as the control terminal of the zero voltage switch circuit 40.
Preferably, the main switch 32 and the auxiliary switch 42 are driven complementarily, and the auxiliary switch 42 and the synchronous rectification switch 81 are driven synchronously.
Preferably, the zero-voltage switching circuit 40 further includes an auxiliary diode 43, a cathode of the auxiliary diode 43 is connected to an anode of the resonant capacitor 44, and an anode of the auxiliary diode 43 is connected to a cathode of the resonant capacitor 44.
In terms of the circuit, the invention is realized by connecting an auxiliary resonance circuit in series in a rectifying circuit of a main power circuit, when a main power switch tube is switched off, realizing zero voltage conduction of the auxiliary switch tube by using the current of a Boost inductor, then realizing rapid increase of the current of a resonance inductor by using the resonance of the resonance capacitor and the resonance inductor and promoting the current of the resonance inductor to be larger than the current of the Boost inductor, and using a diode connected with the resonance capacitor in parallel to follow current of the resonance inductor to ensure that the voltage of the resonance capacitor cannot be reversed and the current of the resonance inductor cannot be rapidly reduced after reaching the maximum value. When the auxiliary switching tube is turned off, the zero voltage switching-on of the main switching tube is realized by utilizing the difference value of the resonance current and the Boost inductive current.
In terms of control, the zero voltage Boost circuit can simply adopt complementary drive to realize the zero voltage switching-on function of the main switching tube and the auxiliary switching tube, and in the simple control realization, only the output voltage needs to be sampled to control the conduction time of the main switching tube. The voltage stress before the auxiliary switch tube is conducted is very small, so that the auxiliary switch tube can be immediately conducted after the main tube is disconnected, namely the dead time can be very short; however, the voltage stress before the main switching tube is conducted is Vout, and the voltage stress needs a certain time to be pumped to zero, so that a proper dead time needs to be left between the turn-off of the auxiliary switching tube and the conduction of the main switching tube.
In light load control, in order to improve the efficiency of the zero voltage Boost circuit in light load, the invention provides a method for realizing frequency reduction control on the basis of complementary control. When the peak current is reduced to a certain degree, the minimum peak current is kept from being reduced in control, namely the minimum peak current control, namely the output of the converter is stabilized by reducing the working frequency of the switching tube when the load is reduced continuously, and a frequency hopping (Burst) working mode is entered when the working frequency reaches the minimum working frequency.
Compared with the prior art, the invention has the following beneficial effects:
(1) the ZVS operation is not limited by the working mode, and the ZVS of the main switching tube and the auxiliary switching tube can be realized in a CCM mode and a DCM mode;
(2) the application is simple;
(3) the current of the rectifier diode is naturally turned off in a zero-crossing way, so that the problem of reverse recovery does not exist;
(4) the light-load frequency reduction work can be easily realized under the complementary drive, and the light-load efficiency is higher;
(5) the realization of ZVS does not affect the current of the Boost inductor, the current of the Boost inductor does not cross zero, and the ZVS can be used for PFC control;
(6) when the zero-voltage switching-on circuit is applied to a synchronous rectification Boost circuit, the Boost inductor can realize zero-voltage switching-on of a main switching tube without negative excitation.
Drawings
FIG. 1 is a block diagram of a conventional power supply;
fig. 2 is a schematic diagram of a conventional diode-rectified Boost converter;
fig. 3 is a circuit schematic and control block diagram of embodiment 1 of a zero voltage Boost converter circuit according to the present invention;
fig. 4 is a diagram of the operation mode of embodiment 1 of the zero-voltage Boost converter according to the present invention;
fig. 5 is an operating waveform of zero voltage Boost converter embodiment 1 according to the present invention;
fig. 6-1 is a block diagram of a conventional synchronous rectification Boost converter and its control;
FIG. 6-2 is a timing diagram illustrating control of the synchronous rectification Boost converter shown in FIG. 6-1;
fig. 7 is a block diagram of a conventional synchronous rectification Boost converter with another control method and a control method thereof;
fig. 8-1 is a circuit schematic diagram and a control block diagram of embodiment 2 of the zero voltage Boost circuit according to the present invention;
fig. 8-2 is a schematic diagram of a frequency variation curve of embodiment 2 of the zero-voltage Boost circuit according to the present invention;
fig. 9 is a schematic circuit diagram of embodiment 3 of the zero voltage Boost circuit according to the present invention;
fig. 10 is a schematic circuit diagram of the zero voltage Boost circuit embodiment 4 according to the present invention;
Detailed Description
First embodiment
Fig. 3 is a schematic diagram 30 of an embodiment 1 of a zero-voltage switching Boost circuit according to the present invention, which is similar to a conventional Boost circuit, where the zero-voltage switching Boost circuit 30 includes a Boost inductor 31, a main switching tube 32, a rectifier diode 33, an output filter capacitor 34, and a control circuit 36, and two ends of the output filter capacitor 34 output voltages Vout to power a load 35; the control circuit 36 generates a feedback voltage signal according to the output voltage Vout and adjusts the duty ratio of the main switching tube 32 according to the feedback voltage signal; one end of the boost inductor 31 is connected with the input voltage +, the other end of the boost inductor 31 is connected with the drain of the main switching tube 32, the source of the main switching tube 32 is connected with the input voltage-, and the gate of the main switching tube 32 is connected with one output end of the control circuit. Different from the conventional Boost circuit, the zero voltage switch Boost circuit 30 further includes a zero voltage switch circuit 40, an input end of the zero voltage switch circuit 40 is connected to the other end of the Boost inductor 31, an output end of the zero voltage switch circuit is connected to an anode of the rectifier diode 33, and a control end of the zero voltage switch Boost circuit is connected to the other output end of the control circuit.
The zero-voltage switching circuit 40 comprises a resonant inductor 41, an auxiliary switching tube 42, an auxiliary diode 43 and a resonant capacitor 44, wherein one end of the resonant inductor 41 is connected with the other end of the boosting inductor 31, the other end of the resonant inductor 41 is connected with the anode of the rectifier diode 33, and the cathode of the rectifier diode 33 is connected with the anode of the output filter capacitor 34; the source of the auxiliary switch tube 42 is connected to one end of the resonant inductor 41, the drain of the auxiliary switch tube 42 is connected to the anode of the resonant capacitor 44 and the cathode of the auxiliary diode 43, respectively, and the cathode of the resonant capacitor 44 is connected to the anode of the auxiliary diode 43 and to the other end of the resonant inductor 41.
Ds1 and Cs1 in FIG. 3 are parasitic diodes and parasitic capacitances of the main switching tube 32, respectively, and do not exist in an actual circuit; similarly, Ds2 and Cs2 are parasitic diodes and parasitic capacitances of the auxiliary switching tube 42, respectively.
The main switch tube 32 and the auxiliary switch tube 42 are all-control semiconductor switches;
preferably, the main switch tube 32 and the auxiliary switch tube 42 are MOS tubes shown in fig. 3;
preferably, the main switching tube 32 and the auxiliary switching tube 42 are IGBTs;
preferably, the main switching tube 32 and the auxiliary switching tube 42 are SiC MOS tubes or GaN MOS tubes;
preferably, the auxiliary diode 43 is a schottky diode.
Fig. 4 shows the main operation mode of the switch in the embodiment 1 of the present invention, and fig. 5 shows the main waveforms of the switch in the embodiment 1 of the present invention, and the operation waveforms are briefly described with reference to the operation mode.
Mode1(t 0-t 1): at the time of t0, the auxiliary switching tube 42 is in an off-off state, the main switching tube 32 is switched from an on-state to an off-state, and since the inductor current cannot change suddenly, the current of the resonant inductor 41 can be considered to be unchanged in a short time, and a part of the current of the boost inductor 31 charges the drain-source junction capacitor Cs1 of the main switching tube 32, so that Vds1 rises rapidly; another portion of the current discharges the auxiliary switch 42 drain-source junction capacitor Cs2, causing Vds2 to drop rapidly to 0;
mode2(t 1-t 2): at time t1, the drain-source junction capacitor Cs2 of the auxiliary switch tube 42 is discharged to 0V, the body diode Ds2 of the auxiliary switch tube 42 is turned on, a part of the current of the boost inductor 31 continues to charge the drain-source junction capacitor Cs1 of the main switch tube 32, the other part charges the resonant capacitor 44(Cr) through the body diode Ds2 of the auxiliary switch tube 42, and meanwhile, the voltage VCr of the resonant capacitor 44 is added across the resonant inductor 41 to excite the resonant inductor, that is, the drain-source junction capacitor Cs1 of the main switch tube 32 is connected in parallel with the resonant capacitor 44(Cr) and then resonates with the resonant inductor 41;
mode3(t 2-t 3): at the time t2, the auxiliary switching tube 42 is turned on at zero voltage, which does not affect the ongoing resonance process, at the time t3, the voltage of the resonance capacitor 44(Cr) resonates to 0V, and the current of the resonance inductor 41 reaches the maximum value;
mode4(t 3-t 4): during this time, the auxiliary diode 43 is turned on, and the current of the resonant inductor 41 freewheels with the auxiliary switch tube 42 through the auxiliary diode 43 and remains substantially unchanged;
mode5(t 4-t 5): at the time t4, the auxiliary switching tube 42 is turned off, a part of the current of the resonant inductor 41 charges the drain-source junction capacitor Cs2 of the auxiliary switching tube 42, and the other part of the current discharges the drain-source junction capacitor Cs1 of the main switching tube 32, that is, the drain-source junction capacitor Cs1 of the main switching tube 32 is connected in parallel with the drain-source junction capacitor Cs2 of the auxiliary switching tube 42 and then resonates with the resonant inductor 41;
mode6(t 5-t 6), at the time of t5, the drain-source voltage Vds2 of the auxiliary switch tube 42 rises to Vout, the drain-source extreme voltage Vds1 of the main switch tube 32 is reduced to 0V, the body diode Ds1 of the main switch tube 32 is conducted, the voltage added to the two ends of L r is-Vout, i L r is linearly reduced, the voltage added to the two ends of L p is Vin, and i L p is linearly increased;
when the Mode7(t 6-t 7) is at the time of t6, the main switch tube 32 is conducted at zero voltage, the previous working process is not influenced, i L r continuously linearly decreases, i L p continuously linearly increases, and the current flowing through the main switch tube 32 becomes positive current until i L p > i L r;
mode8(t 7-t 8), wherein at the time of t7, the current of the resonant inductor 41 is linearly reduced to 0, the rectifier diode 33 is turned off at zero current, the drain-source junction capacitor Cs2 of the auxiliary switch tube 42 is connected in series with the resonant capacitor 44(Cr) and then resonates with L r, at the time of t8, the drain-source voltage Vds2 of the auxiliary switch tube 42 resonates to 0V, and the current of the resonant inductor 41 reaches the negative minimum value;
mode9(t 8-t 9), at the time of t8, the diode Ds2 of the auxiliary switch tube 42 is conducted, the resonant capacitor 44(Cr) and L r are in series resonance, at the time of t9, the current of the resonant inductor 41 resonates to 0, and the voltage of the resonant capacitor reaches a value of a relatively stable value;
mode10(t 9-t 10) is that after the resonant capacitor voltage reaches a relatively stable value, L r resonates with the auxiliary switch tube 42 drain-source junction capacitor Cs2 by a small amplitude, where it is ignored and does not appear in the typical operating waveform, and at t10, the main switch tube 32 switches from the on-state to the off-state again, and another cycle begins.
Second embodiment
Fig. 8-1 shows a schematic diagram and a control block diagram of a second embodiment of the present invention, which is different from the first embodiment in that a CS current detection circuit is added between the source of the main switch tube 32 and the control circuit.
The embodiment is mainly embodied in light load control, the output voltage Vout is sampled to control the stability of the output voltage, and the peak current of the main switching tube is sampled to realize the light load control. When the load is reduced, the peak current of the main switching tube is reduced, and when the load is reduced to a certain degree, the circuit enters a DCM mode to work. When the peak current is reduced to a certain degree, the minimum peak current is kept from being reduced in control, namely the minimum peak current control, namely the output of the converter is stabilized by reducing the working frequency of the switching tube when the load is reduced continuously, and the Burst working mode is entered when the working frequency reaches the minimum working frequency. Fig. 8-2 is a schematic diagram of the corresponding frequency control variation curve.
Third embodiment
Fig. 9 shows a schematic diagram of a third embodiment according to the present invention, that is, the zero-voltage switching circuit 40 of the present invention is also applicable to a Boost circuit for synchronous rectification, and differs from embodiment 1 in that the rectifying diode 33 is replaced by a synchronous rectifying switching tube 81, the input terminal of the zero-voltage switching circuit 40 is connected to the drain terminal of the main switching tube 32, the output terminal is connected to the source terminal of the synchronous rectifying switching tube 81, and the drain terminal of the synchronous rectifying switching tube 81 is connected to the positive terminal of the output filter capacitor 34. In addition, the present embodiment further includes a control circuit 86, the control circuit 86 outputs three driving signals to control the switching of the main switching tube 32, the auxiliary switching tube 42 and the synchronous rectification switching tube 81, wherein the main switching tube 32 and the auxiliary switching tube 42 are driven complementarily, and the auxiliary switching tube 42 and the synchronous rectification switching tube 81 are driven synchronously.
The working principle of the present embodiment can refer to the working principle of embodiment 1, and is not described in detail here. It is especially noted that zero voltage switching-on of the main switch tube and the synchronous rectifier switch tube can be realized when the current of the Boost inductor 31 is continuous (the current does not zero), and negative current is generated by negative excitation of the Boost inductor under the action of output voltage when the current of the Boost inductor 31 is discontinuous (the current does zero), under which the negative excitation current of the Boost inductor and the current of the resonant inductor act simultaneously to extract the drain-source junction capacitance charge of the main switch tube 32 when the auxiliary switch tube and the synchronous rectifier switch tube are switched off, so that the realization of the zero constant voltage of the main switch tube is not influenced.
Fourth embodiment
Fig. 10 shows a schematic diagram of a fourth embodiment according to the present invention, which is different from embodiment 1 in that an auxiliary diode 43 connected in parallel with a resonant capacitor is omitted, and complementary driving control is also adopted, and when the current of the Boost inductor is continuous, this embodiment is consistent with the working principle of embodiment 1, and zero voltage turn-on of the main switch tube and the auxiliary switch tube can also be realized, and will not be described in detail here.
The above disclosure is only specific examples of the present invention, but the present invention is not limited thereto, and those skilled in the art should make modifications to the present invention without departing from the core idea of the present invention, and fall within the protection scope of the claims of the present invention.
Claims (4)
1. The utility model provides a zero voltage switch Boost circuit, can realize under complementary drive's the circumstances that frequency reduction, frequency hopping obtain the zero voltage of main switch tube and auxiliary switch tube open simultaneously, contains Boost inductance 31, main switch tube 32, rectifier diode 33, output filter capacitor 34 and control circuit 36 which characterized in that: also includes a zero voltage switch circuit 40 and a CS current detection circuit;
one end of the boost inductor 31 is connected with the input voltage +, the other end of the boost inductor 31 is connected with the drain electrode of the main switching tube 32, the source electrode of the main switching tube 32 is connected with the input voltage-, and the grid electrode of the main switching tube 32 is connected with one output end of the control circuit; the output voltage Vout at the two ends of the output filter capacitor 34 supplies power to the rear-stage load; the control circuit 36 generates a feedback voltage signal according to the output voltage Vout and adjusts the duty ratio of the main switching tube 32 according to the feedback voltage signal; the input end of the zero voltage switch circuit 40 is connected with the other end of the boost inductor 31, the output end of the zero voltage switch circuit 40 is connected with the anode of the rectifier diode 33, and the control end of the zero voltage switch circuit 40 is connected with the other output end of the control circuit; the cathode of the rectifier diode 33 is connected with the anode of the output filter capacitor 34; the input end of the CS current detection circuit is connected with the source electrode of the main switching tube 32 and is used for detecting the current of the source electrode of the main switching tube 32; the output end of the CS current detection circuit is connected with the control circuit;
the zero voltage switching circuit 40 comprises a resonant inductor 41, an auxiliary switching tube 42, a resonant capacitor 44 and an auxiliary diode 43, wherein one end of the resonant inductor 41 is used as the input end of the zero voltage switching circuit 40, and the other end of the resonant inductor 41 is used as the output end of the zero voltage switching circuit 40; the source of the auxiliary switch tube 42 is connected to one end of the resonant inductor 41, the drain of the auxiliary switch tube 42 is connected to the anode of the resonant capacitor 44, and the cathode of the resonant capacitor 44 is connected to the other end of the resonant inductor 41; the grid electrode of the auxiliary switch tube 42 is used as the control end of the zero-voltage switch circuit 40; the cathode of the auxiliary diode 43 is connected to the anode of the resonant capacitor 44, and the anode of the auxiliary diode 43 is connected to the cathode of the resonant capacitor 44.
2. A zero voltage switching Boost circuit according to claim 1, characterized in that: the control circuit controls the main switch tube 32 and the auxiliary switch tube 42 in a complementary driving mode.
3. A zero voltage switching Boost circuit as claimed in claim 2, wherein: the main switch tube 32 and the auxiliary switch tube 42 are MOS tubes or IGBTs, and the auxiliary diode 43 is a schottky diode.
4. A control method using the zero-voltage switching Boost circuit of any one of claims 1 to 3, characterized by:
the CS current detection circuit detects the peak current of the main switching tube 32, when the peak current is reduced to a set reference value, the minimum peak current is kept from being reduced under control, and when the peak current of the main switching tube 32 has a trend of being reduced continuously due to the fact that the input voltage is increased or the load is reduced continuously, the working frequency of the main switching tube 32 is reduced to stabilize the output of the Boost circuit; and when the working frequency of the main switching tube 32 reaches the minimum working frequency, the frequency hopping operation is entered.
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| Application Number | Priority Date | Filing Date | Title |
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| CN201810294727.3A CN108390567B (en) | 2018-04-04 | 2018-04-04 | Zero-voltage switch Boost circuit and control method thereof |
| PCT/CN2019/070642 WO2019192234A1 (en) | 2018-04-04 | 2019-01-07 | Zero voltage switching boost circuit and control method therefor |
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| CN201810294727.3A CN108390567B (en) | 2018-04-04 | 2018-04-04 | Zero-voltage switch Boost circuit and control method thereof |
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| CN108390567B true CN108390567B (en) | 2020-07-17 |
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| CN108390567B (en) * | 2018-04-04 | 2020-07-17 | 广州金升阳科技有限公司 | Zero-voltage switch Boost circuit and control method thereof |
| CN108768365B (en) * | 2018-08-20 | 2024-01-16 | 珠海格力电器股份有限公司 | Change-over switch conversion and control circuit |
| CN109347317A (en) * | 2018-11-07 | 2019-02-15 | 广州金升阳科技有限公司 | A kind of no-voltage pfc converter |
| CN109768705B (en) * | 2019-01-30 | 2020-11-27 | 钰泰半导体南通有限公司 | Control method for realizing low quiescent current in switching buck converter |
| CN111585425A (en) * | 2019-08-21 | 2020-08-25 | 杰华特微电子（杭州）有限公司 | Power device driving method for switching circuit, driving circuit and switching circuit |
| CN113131735B (en) * | 2021-02-05 | 2021-11-19 | 华源智信半导体(深圳)有限公司 | PFC circuit and control method thereof |
| CN113098256B (en) * | 2021-03-11 | 2023-02-24 | 深圳市博茂智信科技有限公司 | Power factor correction circuit and method for realizing soft switching |
| CN113890314B (en) * | 2021-09-28 | 2023-06-09 | 力源科技有限公司 | Control method of switching power supply and switching power supply |
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| CN108390567A (en) | 2018-08-10 |
| WO2019192234A1 (en) | 2019-10-10 |
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