CN108063605A - The method of radio-frequency filter and tuned radio frequency wave filter - Google Patents
The method of radio-frequency filter and tuned radio frequency wave filter Download PDFInfo
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Abstract
The invention discloses the methods of radio-frequency filter and tuned radio frequency wave filter.Radio frequency (RF) wave filter includes：Resonant element is coupled together forming at least one subband between stopband and transmission zero with multiple transmission zeros corresponding with each frequency of resonant element by multiple resonant elements of the signal transmission path arrangement with the signal transmission path output and input, along between outputting and inputting and multiple non-resonant elements, the plurality of non-resonant elements.The non-resonant elements include being selectively introducing at least one reflection zero in stopband to create at least one variable non-resonant elements of passband in selected subband in a sub-band.Wherein, stopband is in microwave frequency range.
Description
The application is the applying date for 31 days, Application No. 201410854568X December in 2014, and invention and created name is：
The divisional application of the application for a patent for invention of the radio-frequency filter of low-loss adjustable.
Cross reference to related applications
The application is that the part for the U.S. Patent Application Serial Number 13/282,289 submitted on October 26th, 2011 is continued
Application, U.S. Patent Application Serial Number 13/282,289 are showing of submitting on December 2nd, 2010 to be issued as U.S. Patent number 8,
The continuation application of 063,714 U.S. Patent Application Serial Number 12/959,237, U.S. Patent Application Serial Number 12/959,237
Be submit on November 17th, 2009 show the U.S. Patent Application Serial Number 12/620 for being issued as U.S. Patent number 7,863,999,
455 continuation application, U.S. Patent Application Serial Number 12/620,455 are showing of submitting on June 27th, 2008 to be issued as the U.S.
The continuation application of the U.S. Patent Application Serial Number 12/163,814 of the patent No. 7,639,101, U.S. Patent Application Serial Number
12/163,814 requires the priority for the U.S. Provisional Patent Application Serial No. 60/937,462 submitted on June 27th, 2007 simultaneously
And be submit on November 17th, 2006 show the U.S. Patent Application Serial Number 11/ for being issued as U.S. Patent number 7,719,382
561,333 part continuation application, this application are all incorporated herein by reference.
Technical field
Present invention relates in general to microwave circuit and more particularly to microwave band-pass filter.
Background technology
Electrical filter has had long been used for the processing of electric signal.Specifically, this electrical filter is used to by making expectation
Signal frequency by, while block or other undesirable signal frequencies of decaying, it is desired to be selected from input signal
Signal frequency.Wave filter substantially may be logically divided into some classifications, including low-pass filter, high-pass filter, bandpass filter,
And bandstop filter, instruction by wave filter selectivity by frequency type.In addition, wave filter can be divided by type as bar
Special Butterworth, Chebyshev, anti-Chebyshev and elliptic filter, instruction wave filter are provided compared with preferable frequency response
Band shape frequency response (frequency cutoff characteristics) type.
The type of usually used wave filter depends on desired use.In communication applications, bandpass filter usually by with
In cellular basestation and other telecommunication apparatus, to filter out or block all frequency bands in addition to one or more predefined frequency bands
In RF signals.For example, this wave filter is usually used in the front end of receiver can be damaged with filtering out in base station or telecommunication apparatus
Receiver module noise and other unwanted signals.The band logical of clear definition is directly placed in receiver antenna input
Wave filter, by a variety of adverse effects caused by the usual high reject signal eliminated by the frequency near desired signal frequency.
Because the placement that the wave filter is inputted in receiver antenna, insertion loss must be very low, so as not to noise-reduction coefficient.Big
In most wave filter technologies, realize that low insertion loss needs the corresponding compromise of filter steepness or selectivity aspect.
In commercial telecommunications applications, it is usually desirable to passband as small as possible is filtered out using narrow band filter, so that solid
Fixed frequency spectrum can be divided into the frequency band of number as big as possible, so as to increase the actual use that can be fitted in fixed frequency spectrum
The number at family.With steeply rising for wireless communication, this filtering should provide the selection of height in increasingly unfavorable frequency spectrum
Property (ability for distinguishing the signal separated out by small frequency differential) and the susceptibility ability of weak signal (receive).It is most especially important
Be for modeling the 800MHz-900MHz scopes of cellular communication and the 1,800MHz-2 for personal communication service (PCS),
The frequency range of 200MHz scopes.
What the present invention was most interested in is in military (for example, RADAR), communication and electronic intelligence (ELINT), with such as existing
In the commercial field of communications applications (including honeycomb), (that is, surveyed for high quality factor Q in microwave and the RF application of wide scope
Measure the ability of storage energy, so as to negatively correlated with its power consumption or loss), low insertion loss, tunable wave filter
Demand.In numerous applications, filter for receiver must it is tunable with select desired frequency or capture interference signal frequency.
Therefore, if insertion loss is very low, the first non-linear element in receiver antenna and receiver (is typically low noise
Amplifier or frequency mixer) between introduce linear, tunable bandpass filter, provide wide scope RF microwave systems it is aobvious
Write advantage.
For example, in commercial applications, PCS can be used 1,800MHz-2, if the frequency range of 200MHz is divided into
Dry relatively narrow frequency band (A-F bands), in any given area, only its subset can be used by telecom operators.Therefore, for can be by
It is beneficial with the base station of any selected subset op and handheld unit in these frequency bands to reconfigure.As another
Embodiment, in RADAR system, no matter from nearby source or high amplitude interference signal from interference unit can be with " with open arms "
Desensitization receiver or with the intermodulation of high amplitude clutter signal levels and provide decoy instruction.Therefore, in highdensity signal environment
In, RADAR alarm systems often become completely unavailable, and in this case, frequency hopping will be useful.
It is general to build microwave filter using two circuit structure blocks：Effectively store a frequency f0The energy at place
Multiple resonators；And the electromagnetic energy between coupled resonators is to form multistage or multipole coupler.For example, quadrupole filters
Device may include four resonators.The intensity of given coupler is determined by its reactance (that is, inductance and/or capacitance).Coupler
Relative intensity determines that the shape of wave filter and the topological structure of coupler determine that wave filter performs band-pass function still with resistance
Function.Resonant frequency f0Generally determined by the inductance and capacitance of each resonator.It is designed for conventional wave filter, filtering
The frequency of device effectively (active) is determined by the resonant frequency for forming the resonator of wave filter.Each resonator must have non-
Often low internal resistance, so that the response of wave filter is sharp and highly selective due to described above.It is wanted for low-resistance
Size smaller and the cost for seeking more resonators for promoting given technology are lower.
Typically, due to Conventional filters size and cost by with realize it needed for resonator number it is linear
Increase, so the number for being designed as making the resonator needed for realization definite shape by solid frequency wave filter minimizes.Such as half
In the case of conductor device, filter construction (such as high-temperature superconductor (HTS), the microelectromechanical systems of lithographic definition
(MEMS) those and in thin film bulk acoustic wave resonator (FBAR) wave filter) the conventional combination of comparison or dielectric filter scaling
This size and cost it is how insensitive.
The method for being currently used for design tunable optic filter follows the same procedure described above with respect to solid frequency wave filter.
Therefore, they cause very efficient, effective and simple circuit, i.e. they cause to realize that given wave filter response institute is necessary
Simplest circuit.In existing tunable technology, all resonant frequencies of wave filter are adjusted with the frequency of tuning filtering device
Rate.Such as, if it is desired to increase the working band 50MHz of device, then the resonant frequency of all narrow band filters must increase
Add 50 MHz.Although this prior art generally successfully adjusts frequency band, resistance is inevitably introduced to by it
In resonator, so as to adversely increase the insertion loss of wave filter.
It although can be in the case where not introducing notable resistance to resonator, by each humorous in Mechanical Moving wave filter
The HTS plates to shake on device tune HTS wave filters to change its resonant frequency, but this technology is inherently slow (in the amount of second
Grade) and need relatively large three-dimensional tuning structures.Insertion loss can be reduced in the design of so-called switched filter；
However, these designs still introduce significant waste between switch time and need additional resonator.For example, pass through
Set two wave filters and a pair of single-pole double-throw switch (SPDT) (SP2T) selected between wave filter that can reduce filter system
Insertion loss, so as to effectively reduce tuning range demand, but increase by two factors resonator number and draw from switch
Enter loss.The loss of filter system can be further reduced by introducing more switches and wave filter, but it is each additional
Wave filter will need with the former equal number of resonator of wave filter, and more losses will be introduced by required switch.
Therefore, there is still a need for provide the bandpass filter that can be quickly tuned under the insertion loss of reduction.
The content of the invention
According to the first aspect of the invention, a kind of radio frequency wave filter is provided, including：Signal transmission path, signal transmission
Path, which has, to be output and input；Multiple resonant elements, signal transmission path of multiple resonant elements along between outputting and inputting
Arrangement；And resonant element is coupled together having and resonant element to be formed by multiple non-resonant elements, multiple non-resonant elements
The stopband of at least one subband between the corresponding multiple transmission zeros of each frequency and transmission zero of part, wherein, this is non-
Resonant element includes at least one variable non-resonant elements, which is used in the stopband
A few reflection zero is inside selectively introducing to create passband in a subband at least one subband, wherein,
The stopband is in microwave frequency range.
According to another aspect of the invention, a kind of method for tuning above-mentioned RF wave filters is provided, including removing each tune
The part of humorous element, so as to change the frequency of each resonant element.
According to another aspect of the invention, a kind of method for tuning above-mentioned RF wave filters is provided, including：Measure RF filtering
The response of device is to generate one group of measurement data；One group of measurement data is analyzed to extract one or more wave filter design parameters
To optimize；Optimize the one or more wave filter design parameter and it is expected wave filter response to realize；Based on what is optimized
One or more wave filter design parameters generate tuning scheme；And by changing one at least one non-resonant elements
A non-resonant elements, to be moved along the selectively moved corresponding reflection zero of the stopband in the selected subband of the subband
The passband is moved to tune the RF wave filters.
According to another aspect of the invention, a kind of radio frequency (RF) wave filter is provided.RF wave filters include have input and
The signal transmission path of output, along between outputting and inputting signal transmission path arrangement multiple resonant elements and will be humorous
Multiple non-resonant elements that the element that shakes is coupled.Resonant element is coupled to be formed to have to correspond to resonant element
At least one subband between the stopband and transmission zero of multiple transmission zeros of each frequency of part.Non-resonant elements have
The susceptance value at least one reflection zero in stopband, to create passband in the subband at least one subband.
Non-resonant elements include being selectively introducing at least one reflection zero in stopband to create in a subband
Build at least one variable non-resonant elements of passband.In one embodiment, multiple subbands are provided, in such case
Under, variable non-resonant elements can be used for logical to be created in selected subband in a sub-band along stopband displacement reflection zero
Band.Passband can have dramatically different bandwidth in selected subband.In another embodiment, variable disresonance member
Part is used in stopband internal shift at least another reflection zero, to create another passband in another subband in a sub-band.
For example, variable non-resonant elements there can be for example adjustable susceptance, and one or more can be included
Variable condenser, low loss switching (loss-loss switch), varactor and switched capacitor.In an embodiment party
In formula, although resonant element may be employed in the form of any structure of desired frequency resonance, each resonant element bag
Include thin film lumped element structure (e.g., for example, high-temperature superconductor (HTS)).
RF wave filters further comprise being configured to receiving operating temperature and the operating temperature based on reception adjust it is variable non-
The electric controller of resonant element, so as to be moved along the selectively moved reflection zero of stopband in selected subband in a sub-band
Dynamic passband.In one embodiment, electric controller is configured for adjusting variable non-resonant elements with the selectivity in stopband
Ground introduces reflection zero, to create passband in a subband.For example, each non-resonant elements can have the coupling that is connected in parallel to each other
Connect the multiple capacitors for forming condenser network and at least one switch for being coupled at least one capacitor.Then can match somebody with somebody
Electric controller is put for selectively including or excluding at least one capacitor of condenser network by Operation switch to change
The capacitance of condenser network and change the reactance of each non-resonant elements, so as in stopband selectively moved reflection zero with
The mobile passband in selected subband.
Electric controller can be configured to adjust variable non-resonant elements, so as to selectively moved anti-along stopband
Zero point is penetrated, so that passband is back to the nominal design location (nominal as-designed location) in frequency range.
In such a case, it is possible to electric controller is configured to the operating temperature received adjusts at least one resonant element, so as to
Along the transmission zero of the selectively moved each frequency corresponding to resonant element of stopband, so that passband is back to frequency model
Enclose interior nominal design location.
In one embodiment, RF wave filters further comprise the temperature sensor for being configured to measurement operating temperature,
In this case, electric controller is configured to receive to the operating temperature of temperature sensor measurement.RF wave filters can be wrapped further
Memory is included, storage includes corresponding respectively to multiple reference work temperature of different operating temperatures and multiple adjust is set
Group look-up table.In this case, electric controller is configured to compare multiple in the operating temperature and look-up table measured
Reference work temperature, selection correspond to the group that the adjusting of the reference work temperature of the operating temperature closest to measurement is set, with
And the group set according to the adjustment adjusts variable non-resonant elements.
By reading the described in detail below of preferred embodiment, of the invention other and further aspect and feature
It will be apparent from, which is intended to show that rather than limits the present invention.
Description of the drawings
Attached drawing shows the design and practicability of the preferred embodiment of the present invention, wherein, identical reference number refers to
Identical element.Cited hereinabove and other advantages and purpose of the present invention how are obtained in order to better understand, will be passed through
Provided with reference to only certain exemplary embodiments of this invention be briefly described above the present invention be discussed in greater detail, particular implementation is shown
Go out in the accompanying drawings.It should be appreciated that these attached drawings only describe the exemplary embodiment of the present invention, therefore it should not be considered limiting this
The scope of invention will describe and explain the present invention, in the accompanying drawings by using attached drawing using additional feature and details：
Fig. 1 is the block diagram of tunable radio frequency (RF) wave filter constructed according to embodiment of the present invention.
Fig. 2 is the graph responded using the modeling frequency of the exemplary Wide stop bands of 8 resonant elements.
Fig. 3 is the graph of the frequency response of Fig. 2, wherein, passband is introduced in the subband of stopband.
Fig. 4 a to Fig. 4 g are the graphs of the frequency response of Fig. 2, wherein, introduced in the selected subband of stopband
Passband.
Fig. 5 a to Fig. 5 d are the graphs of the frequency response of Fig. 2, wherein, stopband frequency displacement and in displacement
Passband is introduced at each position of the subband of stopband
Fig. 6 is to show while the transmission zero of the frequency response of shift map 2 is to extend the stopband in Fig. 4 a to Fig. 4 g
The graph of the scope of the passband introduced in selected subband.
Fig. 7 a to Fig. 7 f are the graphs responded using the modeling frequency of the exemplary Wide stop bands of 9 resonant elements,
In, passband is introduced in the selected subband of stopband to cover the frequency range of personal communication service (PCS)；
Fig. 8 is the transmission zero for the frequency response for showing independent transfer Fig. 7 a to Fig. 7 f to adapt in the selected of stopband
The graph of the passband introduced in subband；
Fig. 9 a to Fig. 9 f are the graphs of the modeling frequency response of Fig. 2, wherein, draw in the selected subband of stopband
Multiple passbands are entered；
Figure 10 is the block diagram of the tunable RF filter constructed according to another implementation of the invention.
Figure 11 be the wave filter of Figure 10 modeling frequency response graph, wherein, displacement stopband subband
Each position at introduce passband；
Figure 12 is the coupling value of the non-resonant elements in the tunable RF filter shown for Figure 10 compared with Figure 11
Passband frequency displacement variation graph；
Figure 13 a to Figure 13 d show that the circuit of the tunable RF filter of Fig. 1 represents；
Figure 14 is to show to be used for the form for modeling the components values of the RF wave filters of Figure 14 under three kinds of filter status；
Figure 15 a to Figure 15 c are the circuit realization figures of the tunable RF filter of Fig. 1, and various wave filter shapes have been shown in particular
State and corresponding frequency response；
Figure 16 a to Figure 16 c are the graphs of frequency response of the RF wave filters of Figure 14 under three states；
Figure 17 is the tuning for the RF wave filters for showing Figure 14 compared with the graph of the insertion loss of wave filter；
Figure 18 is to compare the insertion loss of the RF wave filters of Figure 14 when being tuned to identical frequency range compared with routine
The graph of the insertion loss of wave filter；
Figure 19 is to compare the insertion loss of the wave filter of Fig. 1 when being tuned to identical frequency range compared with switching regulator
The graph of the insertion loss of wave filter；
Figure 20 is two resonators more constructed according to the invention, four resonators and six resonator tunable optic filters
Frequency response and the graph of the frequency response of standard band-pass filter；
Figure 21 shows that another circuit of the tunable RF filter of Fig. 1 represents；
Figure 22 shows the coupling matrix that the circuit of Figure 21 represents；
Figure 23 a to Figure 23 c are the graph of the frequency response of the RF wave filters of Figure 21 and corresponding coupling matrix；
Figure 24 is graphically illustrated for tuning the coupling moment of Figure 23 a to Figure 23 c of the RF wave filters of Figure 21
The graph of coupling value in battle array；
Figure 25 is the graph for another group of coupling value that graphics mode is shown available for the RF wave filters for tuning Figure 21；
Figure 26 is the graph for the another group of coupling value that graphics mode is shown available for the RF wave filters for tuning Figure 21；
Figure 27 is the plan view layout of a resonator in the tunable RF filter of Fig. 1, has been shown in particular to adjust
The tuning fork of humorous resonator；
Figure 28 is the plan view layout of a resonator in the tunable RF filter of Fig. 1, has been shown in particular to adjust
The trimming strip of humorous resonator；And
Figure 29 is the block diagram of the tunable RF filter constructed according to embodiment of the present invention.
Specific embodiment
With reference to figure 1, tunable radio frequency constructed according to the invention (RF) wave filter 10 will now be described.In the implementation shown
In mode, RF wave filters 10 are that have in desired frequency range, such as 800MHz-900MHz or 1,800MHz-2,220MHz
The bandpass filter of interior tunable passband.In a typical scene, RF wave filters 10 are placed on the desired frequency of refusal
In the front end of receiver (not shown) after the wide pass filter of energy outside rate scope.RF wave filters 10 generally comprise
With input 14 and output 16 signal transmission path 12, along signal transmission path 12 arrange multiple nodes 17, respectively from
The multiple resonance branch 19 and the multiple non-resonant branches 21 extended respectively from node 17 that node 17 extends.The RF wave filters 10
It is multiple (this between further comprising between input 14 and output 16 and being specifically coupled in resonance branch 19 and be grounded
In the case of, four) resonant element 18, for adjust the frequency of resonant element 18 multiple tuned cells 20, by resonant element
The 18 multiple non-resonant elements 22 being coupled together, four non-resonant elements 22 therein are coupled in non-resonant branches 21 and connect
Between ground.RF wave filters 10 further comprise being configured as tuning RF wave filters 10 to the electricity of the selected narrowband in frequency range
Controller 24.
Signal transmission path 12 can include the physical transmission lines that non-resonant elements 22 directly or indirectly couple, still
In alternative embodiment, without using physical transmission lines.In the embodiment as shown, resonant element 18 includes lump
Element electrical component, such as inductor and capacitor, and particularly, including thin-film lumped structures, such as planar spiral structures, sawtooth
Shape serpentine configuration, single coil structure and two coil configuration.This structure may include thin film epitaxial high temperature superconductor (HTS), should
Thin film epitaxial high temperature superconductor is patterned to form capacitor and inductor on low dielectric loss substrate.U.S. Patent number 5,
616,539 elaborate that the further detail below of high temperature superconductor lumped element filters is discussed, are fully incorporated in by quoting
This.
In the embodiment as shown, resonant element 18 is by susceptance BRIt represents and non-resonant elements 22 is by susceptance BNTable
Show, non-resonant elements 22 and 18 coupled in parallel of resonant element, and admittance inverter J is coupled between resonant element 18.Anharmonic
The selected non-resonant elements shaken in element 22 can change, and any remaining non-resonant elements in non-resonant elements 22 are still
It is fixed.
As will be described in more detail below, thus it is possible to vary non-resonant elements 22 are with substantially in entire frequency range
Tune passband, if it is desired, only slightly adjust, with adapt to and/or the opposite segments of travel frequency scope in passband.With this
Kind mode, due to being the main device that non-resonant elements 22 rather than resonant element 18 are used as to tuning filtering device 10, so filter
The insertion loss of ripple device 10 significantly reduces.That is, because adjusting the sensitive resonant element of loss more notable than adjusting of non-resonant elements 22
The contribution of the loss of 18 pairs of wave filters 10 is less, so middle compared with prior art be used as using resonant element for tuning filtering
The wave filter of the main device of device 10, wave filter 10 will be with less losses.Further, since slightly adjust very much resonance
The frequency of element 18, if any, the tuned speed of wave filter 10 becomes faster.
RF wave filters 10 realize the above by introducing the narrow passband of the selection area with Wide stop bands.That is, although adopt
It is used as bandpass filter with RF wave filters 10, but is coupled together resonant element 18 actually by non-resonant elements 22
(not being to create passband), but the transmission zero with each frequency corresponding to resonant element 18 is created (in such case
Under, be four) Wide stop bands response.Then electric controller 24 adjusts non-resonant elements 22 to introduce and shift along stopband
Reflection zero is with the mobile narrow passband in desired frequency range.Electric controller 24 can also be adjusted humorous by tuned cell 20
It shakes the frequency of element 18, carrys out Optimal Filter response to move transmission zero along frequency range.In the embodiment shown
In, the electric controller 24 of the memory (not shown) of the value including being used to store non-resonant elements 22 is for realizing passband in frequency
The desired locations of rate scope are necessary.
This technology is described with reference to the various exemplary filter responses modeled according to following equation：Wherein, S11It is the input reflection coefficient of wave filter, S21It is just
To transmission coefficient, s is normalized frequency, and F and P are that (wherein, N is the number of resonant element for the N rank multinomials of broad sense complex frequency s
Mesh), and ε is constant of the definition equal to return loss.Since molecule has N ranks, so coefficient S11And S21In each energy
It is enough that there is up to N zero point.Work as coefficient S11、S21When all there is all N number of zero points, it is believed that wave filter response is complete ellipse
Circle.In " Microstrip Filters for RF/Microwave Application, " Jia-Shen G. Hong and
The further detail below of discussion modeling filter is elaborated in M.J.Lancaster, Wiley-Interscience 2001.According to
Normalized frequency s=iw can be mapped to actual frequency by following equation：Wherein, f is actual frequency,
fcBe centre frequency and BW be wave filter bandwidth.In " Microwave Filters, Impedance-Matching
Networks,and Coupling Structures,”G.Matthaei,L.Young and E.M.T.Jones,McGraw-
It elaborates to discuss that normalized frequency is converted to the further detail below of actual frequency in Hill (1964).
Fig. 2 shows illustrative wide bandstop filter response, is modeled using 8 resonant elements, so as to each
8 (illustrating only 6) corresponding transmission zero 30 is created at resonant element frequencies (such as in the right side view of Fig. 2 most preferably to show
Go out) to form stopband 32, and create 8 (illustrating only 6) and fall reflection zero 34 outside the stopband 32 (as in Fig. 2
In left side view best seen from).In this specific example, transmission zero 30 be located in normalized frequency scope-
1.05th, at -0.75, -0.45, -0.15,0.15,0.45,0.75 and 1.05, have so as to create between -1.05 and 1.05
Normalized frequency scope stopband.As shown in the right side view of Fig. 2, wave filter response is included between transmission zero 30
7 " bounces " being located at respectively in region 36 at -0.90, -0.60, -0.30,0.0,0.30,0.60 and 0.90.Therefore, one
As for, bandstop filter includes N number of transmission zero (correspond to N number of resonant element), at most N number of reflection zero and N-1
Beat region 36.
It is worth noting that, by the way that at least one reflection zero 34 is displaced to stopband 32 (that is, by adjusting disresonance
The value of element) can be as shown in Figure 2 region 36 in any one bounce (hereinafter referred to as " subband ") form passband.Example
Such as, Fig. 3 shows illustrative wave filter response, wherein, 4 reflection zeros 34 are introduced in the stopband of Fig. 2, with
Passband 38 is created (that is, at 0) in center sub-band 36 (4).Reflection zero 34 can be shifted along stopband 32 (that is, to pass through
Adjust the value of non-resonant elements), so as to create passband 38 in a selected subband 36.I.e., it is possible to it is shifted along stopband 32
Passband 38 of the reflection zero 34 between " jump " subband 36.
For example, Fig. 4 a to Fig. 4 g show illustrative wave filter response, wherein, it is anti-in 32 internal shift of stopband 4
0. 34 are penetrated selectively to create passband 38 at the center of all 7 subbands 36.That is, successively with reference to figure 4a to Fig. 4 g, passband
38 jump to the second subband 36 (2) (Fig. 4 b) from the first subband 36 (1) (Fig. 4 a), jump to the 3rd subband 36 (3) (Fig. 4 c),
The 4th subband 36 (4) (Fig. 4 d) is jumped to, jumps to the 5th subband 36 (5) (Fig. 4 e), jumps to the 6th subband 36 (6) (figure
4f) and finally jump to the 7th subband 36 (7) (Fig. 4 g).Therefore, in the embodiment as shown, the center of passband 38 can
To jump between -0.90, -0.60, -0.30,0.0,0.30,0.60 and 0.90.It should be noted that although Fig. 4 a extremely scheme
The order of 4g means that passband 38 jumps between adjacent subband 36, but passband 38 can non-adjacent subband 36 it
Between jump, for example, jumping to the 5th subband 36 (5) from the second subband 36 (2).
When passband 38 can jump discretely to cover desired frequency range between sub-bands 36, transmission zero 30
Can from their nominal position simultaneously uniform movement (that is, the frequency by adjusting resonant element) to shift entire stopband 32,
And therefore passband 38 is in normalized frequency range.Therefore, can from the center of subband 36 (that is, -0.90, -0.60, -
0.30th, 0.0,0.30,0.60 and 0.90) mobile passband 38 so that it covers the continuum of expected frequency range.Therefore, if
All transmission zeros can shift +/- 0.15 from their nominal position, and (that is, resonant element tunes +/- 0.15 frequency together
Rate scope), then each passband 38 shown in Fig. 4 a to Fig. 4 g by cover from -1.05 to 1.05 normalized frequency scope
15%.
By way of example, if it is desired to which the center of passband 38 is at -0.20, then passband 38 can be located in
In 3rd subband 36 (3) (at the center -0.30 of Fig. 4 c), and nominal position of the transmission zero 30 from them can be made
Displacement 0.10, so that passband 38 from -0.30 is moved to -0.20.If it is desire to the center of passband 38 is at 0.85, then can be with
Passband 38 is located in the 7th subband 36 (7) (at the center of Fig. 4 g 0.90), and transmission zero 30 from it can be made
Nominal position displacement -0.05 so that passband 38 from 0.90 is moved to 0.85.
It is shown although passband 38 is positioned as the center in subband 36 in Fig. 4 a to Fig. 4 g, it can be in stopband 32
Reflection zero 34 (that is, the value by adjusting non-resonant elements) is shifted, with the selectively mobile passband in selected subband 36
38.It in such a case, it is possible to which passband 38 is made to jump between sub-bands 36, and moves in subband 36, is used for so as to reduce
Adjust the amount for the transmission zero 30 that passband 38 is covered needed for the continuum of desired frequency range.For example, Fig. 5 a to Fig. 5 d show
Go out the illustrative wave filter response on center sub-band 36 (4), wherein, make all transmission zeros 30 from their mark
Claim displacement 0.05 (that is, by the way that the frequency of resonant element 18 is made to increase by 0.05), and make reflection zero from the nominal of them
Position incrementally shifts 0.05 (that is, by adjusting non-resonant elements 22).
Specifically, with reference to figure 5a to Fig. 5 d transmission zero is made to shift 0.05 from their nominal position successively, thus will
Passband 38 from 0 (Fig. 5 a) is displaced to 0.05 (Fig. 5 b).Then, after constant transmissions 0. 30, reflection zero 34 from them is made
Nominal position incrementally shift 0.05, by passband 38 from the center of subband 36 (4) (0.05 in Fig. 5 b)) be moved to subband
The position of the central right 0.05 (0.10 in Fig. 5 c) of 36 (4) is then moved to the central right 0.10 of subband 36 (4)
The position of (0.15 in Fig. 5 d).
Although this mode may destroy the symmetry of the attenuation slope of bandpass filter, in this case, it
Reduce needed for transmission zero 30 displacement, therefore, the tuning range of resonant element is reduced to 5% from 15%, with obtain with
Reflection zero 34 is not in the identical tuning range of the situation of 36 internal shift of subband.As a result, further reduce the loss of wave filter.
It although note that theoretically can be in the whole internal shift transmission zero 30 of subband 36, in this case, in nothing
It needing under resonant elements tuned, each passband 38 can about cover the 15% of entire stopband 32, but in fact, due to reflection
0. 34, close to transmission zero 30, dramatically increase so as to the loss of wave filter.For this reason, it is preferred that with reflection zero 34
Shift transport 0. 30 together, in the case of without significantly loss passband 38 to be allowed to be moved in entire frequency range.
For example, with reference to figure 6, in the range of compared with their nominal position (being shown by horizontal dotted line) +/- 0.05
Shift transport 0. 30, any position passband 38 being located in -1.05 to 1.05 nominal frequency range (such as pass through
Represented by oblique dotted line).When the frequency of passband 38 is moved to 1.05 from -1.05, reflection zero 34 jumps to down from a subband 36
One subband 36, reflection zero 34 are shifted along subband 36 in the range of +/- 0.10, and transmission zero 30 is +/- 0.05
In the range of shift, the total size between jump is 0.30.
Specifically, in the beginning of tuning range, transmission zero 30 is initially positioned at the nominal position compared with them
- 0.05 (that is, -1.05, -0.75, -0.45, -0.15,0.15,0.45,0.75,1.05) at, by the first subband 36 (1)
Center be placed in -0.95 place, in this case, reflection zero 34 is initially positioned at compared in the first subband 36 (1)
Their -0.10 place of nominal position, -1.05 places are placed in by passband 38.While transmission zero 30 is fixed, it can incite somebody to action
Reflection zero 34 in first subband 36 (1) is displaced to their nominal position so that passband 38 be moved to from-1.05-
0.95.While reflection zero 34 is fixed, then transmission zero 30 can be made to be shifted compared with their nominal position
0.05, the center of the first subband 36 (1) is made to be moved to -0.85, so that passband is moved to -0.85 from -0.95.It will pass
While defeated zero point is fixed again, reflection zero 34 can be made to shift 0.10 compared with their nominal position, so that passband
- 0.75 is displaced to from -0.85.
Once passband 38 reaches -0.75, then reflection zero 34 will jump to the second subband 36 from the first subband 36 (1)
(2), and so transmission zero 30 will shift -0.05 again compared with their nominal position, make the second subband 36 (2)
Center be moved to -0.65, in this case, reflection zero 34 will be initially positioned at the nominal position compared with them -
At 0.10, to keep passband 38 at -0.75.Then transmission zero 30 and reflection zero 34 are with above with respect to the first subband 36
(1) the same way movement coordinated with each other of description, so that passband 38 from -0.75 is moved to -0.45.Once passband 38 reaches-
0.45, then reflection zero 34 will jump to the 3rd subband 36 (3) from the second subband 36 (2), and so on, until passband 38
Reach 1.05.
Although RF wave filters 10 are being described as that narrow passband can be tuned in the continuum of desired frequency range above
(i.e., it is possible to reconfiguring RF wave filters in a continuous manner), but RF wave filters can be reconfigured in a discrete fashion
10 so that passband 38 can be discretely located in the center of selected band region.For example, PCS application in, pass through by
Narrow passband is located at the frequency band selected in these frequency bands, can be reconfigured for RF wave filters 10 in six A-F frequency bands
Any one operation.
Fig. 7 a to Fig. 7 f are shown corresponding to the different exemplary filters for reconfiguring state of six kinds of RF wave filters
Response.In this case, the wave filter of modeling is each with being located to create with nine transmission zeros 30 (only showing seven)
The stopband 32 of eight subbands 36 between a transmission zero 30 and with can be displaced in stopband 32 in six subbands 36
In selected subband in create passband 38 seven reflection zeros 34.Therefore, RF wave filters can be reconfigured for
A bands (Fig. 7 a), D bands (Fig. 7 b), B bands (Fig. 7 c), E bands (Fig. 7 d), F bands (Fig. 7 e) or the C bands (Fig. 7 f) of PCS communication protocols
Operation.As shown in the figure, the width of the passband 38 in subband 36 is different, determined by the interval of adjacent transmission zeroes 30.Specifically
Ground, the width of A, B and C band are about 2.5 times of the width of D, E and F band.
Note that because in this reconfigurable embodiment, it need not be in the continuum of desired frequency range
Interior mobile passband 38, but passband 38 is designed it is sufficiently wide to cover desired frequency range, so without shift transport zero
30 are put to extend the scope of passband 38.Moreover, as shown in Fig. 8, make transmission zero 30 from their nominal position independent transfer with
Improve for 38 vacating space of passband or in addition fade performance.For example, make second and the 3rd transmission zero 30 (2), 30 (3) each other
Think 34 vacating space of reflection zero that A takes away from movement；Make the 4th and the 5th transmission zero 30 (4), 30 (5) remote each other
From the mobile reflection zero vacating space thought B and taken, the 7th and the 8th transmission zero 30 (7), 30 (8) is made to move away from each other
Dynamic 34 vacating space of reflection zero to be taken for C；The third and fourth transmission zero 30 (3), 30 (4) is made to move away from each other
Think 34 vacating space of reflection zero that D takes, the 5th and the 6th transmission zero 30 (5), 30 (6) is made to move away from each other with
34 vacating space of reflection zero taken for E；And the 6th and the 7th transmission zero 30 (6), 30 (7) is made to move away from each other
Think 34 vacating space of reflection zero that F takes.
Although above-mentioned technology is described as to introduce single passband 38 (that is, passband one at a time) in stopband 32, can
To introduce multiple passbands in stopband 32.For example, Fig. 9 a to Fig. 9 f show illustrative wave filter response, wherein, exist
Stopband 32 internal shift, two groups of four reflection zeros 34 are logical selectively to create two at the center of Xuan Ding a pair of of subband 36
Band 38 (1), 38 (2).That is, successively with reference to figure 9a to Fig. 9 f, passband 38 (1), 38 (2) are introduced into second and the 3rd subband 36
(2), in 36 (3) (Fig. 9 a), it is introduced in the 3rd and the 5th subband 36 (3), 36 (5) (Fig. 9 b), is introduced to the third and fourth son
In band 36 (3), 36 (4) (Fig. 9 c), it is introduced in second and the 4th subband 36 (2), 36 (4) (Fig. 9 d), is introduced to second and
It (Fig. 9 e) and is introduced in six subbands 36 (2), 36 (6) in second and the 5th subband 36 (2), 36 (5) (Fig. 9 f).
Referring now to Figure 10 and Figure 11, for explaining variable non-resonant elements (for coupling value) and obtained narrow
The purpose of correlation between the value of movement of the passband in Wide stop bands will describe basic tunable optic filter 50.Such as Figure 10
Shown, RF wave filters 50 are generally comprised between input 54 and the signal transmission path 52, input 54 and the output 56 that export 56
Multiple (in this case, two) resonant elements 58 and multiple non-resonant elements for being coupled together resonant element 58
62.Tuned cell can be used to adjust to the frequency of resonant element 58 and electric controller (not shown) can be tuned
The narrowband selected in RF wave filters 50 to frequency range.It is identical with wave filter 10 shown in FIG. 1, the resonant element of wave filter 50
58 by susceptance BRIt represents and non-resonant elements 62 is by susceptance BNExpression and 58 coupled in parallel of resonant element and admittance inverter
J coupled in parallel is between resonant element 58.Selected non-resonant elements (in this case, susceptance B in non-resonant elements 22N)
It can change, and the remaining non-resonant elements (in this case, admittance inverter J) in non-resonant elements 22 are kept fixed.
Wave filter 50 is modeled to create exemplary filter responses as shown in figure 11.By the frequency of two resonant elements 58
Rate and therefore two transmission zeros 70 be set in 0.95GHz and 1.05GHz, so as to create have 0.95GHz with
The stopband (not shown) of normalized frequency scope between 1.05GHz.In this case, because only that two resonant elements
58, so single subband 76 is located at the center 1.00GHz between transmission zero 70.Therefore, only introduce and along stopband
Reflection zero (not shown) is shifted with the mobile passband 78 (five positions for showing passband 78) in single subband 76.
If Figure 11 and Figure 12 are further illustrated, variable non-resonant elements 66 can be adjusted and (be referred to as B in fig. 12N
(L) and BN(S)) to move the nominal frequency of the about 1.00GHz of passband 78 by changing their coupling value.Specifically, lead to
It will be with the non-resonant elements B of load-side with 78 frequencyN(L) percentage coupling value increase and the disresonance of mains side member
The B of partN(S) percentage coupling value reduces and reduces and (move to left) and the non-resonant elements B with load-sideN(L) percentage
Rate coupling value reduces and the non-resonant elements B of mains sideN(S) percentage coupling value increases and increases.
With reference to figure 13a to Figure 13 c, the non-resonant elements 22 of the wave filter 10 of Fig. 1 can be replaced with actual component, are made
Wave filter 10 can be modeled and realize by obtaining.As depicted in fig. 13 a, first by circuit reduction be using only non-resonant elements 22 again
Configure the required composition component of wave filter 10.In this case, tuned cell 20 is not the weight for simulating (modeling) wave filter 10
Necessary to new configuration, therefore removed during it is represented from the circuit of Figure 13 a.As illustrated in fig. 13b, actual circuit has been used
The piecemeal component that the circuit of Figure 13 a represents is substituted in component.Electricity container is replaced by BNThe non-resonant elements 22 of expression, electricity consumption
Capacitive pin network replaces the non-resonant elements 22 represented by J, and is replaced with capacitor-inductor combination in parallel by BRTable
The resonant element 20 shown.The circuit that the circuit expression of Figure 13 b is further reduced to Figure 13 c represents, thus it is possible to vary its anharmonic
Element 22 shake to realize reconfiguring for wave filter 10.
Use the wave filter 10 of actual circuit component values analogous diagram 13c.Polynomial equation modeling from the above discussion
The circuit of Figure 13 c, except that components values are related to polynomial coefficient.As discussed above, there are four humorous for the tool of wave filter 10
Shake element 18, and therefore, there are four transmission zeros and three subbands being formed between them for tool in its frequency response.Cause
This, capacitor non-resonant elements of one group of adjusting in the circuit of Figure 13 c represents in three class values that can be according to Figure 14
Wave filter 10 with the passband that jumps between three subbands, is placed in the one kind selected in three kinds of states by 22 value.According to figure
The circuit of 13d represents each capacitor in the circuit expression of modeling Figure 13 c.Specifically, each capacitor C is expressed as having
Have and variable condenser CdFixed capacity device C in parallel0With with variable condenser CdThe electricity of the resistor R (representing switch) of series connection
Road.
Referring now to Figure 15 a to Figure 15 c, can will be used by adjusting the non-resonant elements selected in non-resonant elements 22
The wave filter 10 of basic framework shown in Figure 13 c is reconfigured between one kind of three kinds of states.As shown in the figure, wave filter
10 all frequency responses have four transmission zeros 30 of the frequency for corresponding to four resonant elements 18 and are formed at transmission
Three subbands 36 between 0. 30.Therefore, three subbands 36 it is each in can create passband 38 to support to amount to three kinds
Different states：Passband 38 is created into the left state in the first subband 36 (1)；Passband 38 is created in the second subband 36
(2) intermediate state in；With passband 38 is created to the right state in the 3rd subband 36 (3).
As shown in the figure, there are three capacitor C in parallel for each tool of non-resonant elements 221-C3, wherein with each adaptive switched
Two capacitor C of the outside of capacitance1And C2With promoting to switch S1And S2Resistance loss resistor R1And R2Series connection.Therefore,
Pass through closure switch S2And S3It can be by capacitor C1And C2Including switching S in circuit and by independent open1And S2From
Capacitor C is excluded in circuit1And C2.Thus, it is supposed that capacitor C1-C3With equal value, each non-resonant elements 22 can be with
There are three one selected in value for tool：C1(S1、S2All be not closed), C2+C3(switch S1、S2In a closure) or C1+C2
+C3(switch S1、S2It is all closed).Switch S1And S2Can be any suitable low loss switching, for example, low-loss GaAs is switched.
Alternately, can use and be capable of other variable elements of capacitance value, as variable condenser, GaAs varactors,
Or switched capacitor.
It has been determined that when non-resonant elements 22 have the value determined by the on off state shown in Figure 15 a, passband
38 can be placed into the first subband 36 (1) (left state)；When non-resonant elements 22 have as the switch shape shown in Figure 15 b
During the value that state determines, it is placed into the second subband 36 (2) (intermediate state)；And when non-resonant elements 22 have by Figure 15 c
During the value that shown on off state determines, it is placed into the 3rd subband 36 (3) (intermediate state).It can use special in the U.S.
Sharp patent application serial numbers 11/289,463, disclosed in entitled " Systems and Methods for Tuning Filters "
Parameter extraction and analytical technology carry out tuning filtering device 10, this is expressly incorporated by quoting.For purposes of illustration,
Adjacent light bulb, which has been shown, with the switch of closure state lights (coloring), and the light bulb adjacent with the switch of opening state
Extinguishing (not colouring) has been shown.Although wave filter 10 is described as only having in subband 36 for Figure 15 a to Figure 15 c
Between jump the ability of passband 38, but in order to which passband 38 can move in selected subband 36, more opened by addition
Powered-down container can increase the precision (resolution) of circuit.Moreover, because passband 38 to be located in the center of subband 36,
So no tuned cell shows to couple with resonant element 18.
Referring now to Figure 17, the frequency range for being showing along 770MHz to 890MHz tunes simulation filter shown in Figure 13 c
Device 10 is to minimize insertion loss.In this situation, by adjusting non-resonant elements 22 so that passband 38 is in subband 36
Jump (as shown in Figure 16 a to Figure 16 c) and changes the frequency of resonant element 18 with the mobile passband 38 in subband 36 between the heart
(that is, covering the frequency range between the center of subband 36) carrys out tuning filtering device 10.As shown in the figure, from the 3rd subband 36 (3)
Center (show) to be moved to passband 38 at the left side 850MHz of the 3rd subband 36 (3) at 890MHz in Figure 15 c, filter
The insertion loss of device 10 is increased to about -1.5dB from about -0.2dB.Once reaching 850MHz, passband 38 is from the 3rd subband 36
(3) center (being shown in Figure 15 b) of the second subband 36 (2) is jumped to, so as to which insertion loss is reduced to from about -1.5dB
About -0.25dB.Then passband 38 is moved to a left side for the second subband 36 (2) at the center 850MHz of the second subband 36 (2)
At the 810MHz of side, the insertion loss of wave filter 10 is increased to about -1.5dB from about -0.25dB.Once reaching 810MHz, lead to
Band 38 jumps to the center (showing in fig. 15 a) of the first subband 36 (1) from the second subband 36 (2), insertion loss from about-
1.5dB is reduced to about -0.7dB.Then passband 38 is moved to the first son at the center 810MHz of the first subband 36 (1)
At the left side 770MHz of band 36 (1), the insertion loss of wave filter 10 is increased to about -1.9dB from about -0.7dB.Therefore, may be used
To be appreciated that, by moving passband along frequency range, wave filter 10 can cover 770MHz to 890MHz frequency ranges
Four corner, while jump to minimize insertion loss between sub-bands 36.
Use the modeling parameters shown in Figure 15, it has already been proven that, compared with using only resonant element 18, when using anharmonic
When the element 22 that shakes carrys out tuning filtering device, insertion loss significantly reduces in a certain frequency range.For example, as shown in figure 18, work as tune
The frequency of non-resonant elements 22 and resonant element 18 is saved in frequency range 770MHz to 890MHz during tuning filtering device 10,
The insertion loss of the worst case of wave filter 10 is than only adjusting the frequency of resonant element to be tuned in identical frequency range
The about low 8dB of insertion loss of wave filter 10 during wave filter 10.
And have confirmed, the wave filter 10 of the parameter model as shown according to Figure 15, which has, is substantially less than the prior art
In switched filter tunable technology insertion loss.For example, as shown in figure 19, when adjust variable non-resonant elements with
The frequency of resonant element is with during tuning filtering device 10, the insertion of wave filter 10 is damaged in the frequency range of 770MHz to 890MHz
Consumption is substantially less than the insertion loss of the switched filter tuned in same frequency range (it is assumed that small insertion loss comes from
In addition switch, and adjust the frequency of resonant element with cover switching between total tune scope half).
Although thinking that the insertion loss of bandpass filter increases with the increase of resonant element number note that conventional,
Have confirmed insertion loss not with the number of resonant element used in the wave filter using designing technique described herein
Increase and increase.For example, as shown in figure 20, the frequency range of 750GHz to 950GHz is depicted and uses skill described herein
2 resonators, 4 resonators and 6 resonator filter designs and study plot the wave filter design of art.It is as shown in the figure, immediate humorous
Shake element Q- and the most insertion loss of the number of non-resonant elements-cause.
It should be noted that the value for changing coupled in series to the non-resonant elements 22 of resonant element 18 can slightly change
Transmission zero.In order to provide wave filter optimal performance, preferably these transmission zeros will not be moved unintentionally.
Specifically, as shown in figure 21, circuit reduction is extremely reconfigured into wave filter 10 using only non-resonant elements 22 again
Necessary composition component.In this case, tuned cell 20 is not that reconfiguring for modeling wave filter 10 is necessary,
Therefore removed during it is represented from the circuit of Figure 21.
In the embodiment as shown, there are four by susceptance BR(specifically, B1 R、B2 R、B3 RAnd B4 R) represent resonance
Element 18 and 15 non-resonant elements 22, can be arranged as by susceptance BN(specifically, BS N、B1 N、B2 N、B3 N、B4 NWith
BL N) six non-resonant elements 22 (1) (also referred to as NRN- ground connection (shunting non-resonant elements)) for representing, by admittance inverter J
(specifically, J01、J12、J23、J34And J45) represent five non-resonant elements 22 (2) (also referred to as NRN-NRN (series connection it is non-
Resonant element)) and four by admittance inverter J (specifically, J1、 J2、J3And J4) represent non-resonant elements 22 (3) (
Referred to as NRN- resonators (resonator coupling).Non-resonant elements 22 (1), 22 (2) coupled in parallel to each resonant element 18, together
When non-resonant elements 22 (3) coupled in series to each resonant element 18.Selected non-resonant elements 22 can change, with former
What remaining non-resonant elements 22 is kept fixed.In the embodiment as shown, coupled in series to resonant element 18 disresonance
Element 22 (that is, non-resonant elements 22 (3)) (when realizing in actual solution, tends to " raise " resonance frequency
Rate) it is kept fixed.
It should be noted that use acoustic resonator such as surface acoustic wave (SAW), thin film bulk acoustic wave resonator (FBAR),
MEMS (MEMS) resonator is realized in the design of resonant element 18, electrical or mechanical coupling element can be used as to realize
Non-resonant elements 22.In such a case, it is possible to advantageously, realize non-resonant elements 22 (3) be used as electromechanical transducer with
The non-resonant elements 22 (3) and sound wave resonance element 18 for allowing circuit are kept fixed, while also allow disresonance member is used only
Part 22 (1), 22 (2) are used for electronic tuning.
Figure 22 shows that the coupling matrix of wave filter 10 represents.As shown in the figure, node S, 1-4, L and 5-8 (Figure 20 institutes
Showing) left side and node S, NRN1-NRN4 (disresonance node) for representing in matrix, L and resonance node R 1-R4 is in matrix
The upside of expression.Similary as shown in figure 22, the coupling value between node is the susceptance value of resonant element 18 and non-resonant elements 22
With admittance inverter value.
Filter shown in analogous diagram 21 is come with the passband 38 that jumps between the center of subband 36 using different groups of the coefficient of coup
Ripple device represents.Specifically, Figure 23 a to Figure 23 c show illustrative wave filter response (coupling matrix table corresponding with them
Show), wherein, four reflection zeros 34 at the center of all three subbands 36 in 32 internal shift of stopband selectively to create
Build passband 38.That is, successively with reference to figure 23a to Figure 23 c, passband 38 jumps to the second subband from the first subband 36 (1) (Figure 23 a)
36 (2) (Figure 23 b) then jump to the 3rd subband 36 (3) (Figure 23 c).Therefore, the center of passband 38 nominal frequency-
0.80th, jump between 0.0 and 0.80.Represented from the matrix of corresponding Figure 23 a to Figure 23 c it will be seen that, series coupled it is non-
Resonant element 22 (3) (that is, J1-J4) susceptance value be fixed on -1, while the non-resonant elements 22 (1) of parallel coupled, 22 (2)
Admittance inverter value changes with the passband that jumps between sub-bands 36.These values are jumped between the three nominal frequencies with passband 38
Variation (and unchanged) illustrate show in fig. 24.As shown in the figure, the non-resonant elements 22 (1) of parallel coupled, 22 (2)
(that is, J01、J12、J23、J34、J45、B1 N、B2 N、B3 NAnd B4 N) value change, and the non-resonant elements 23 (3) of series coupled are (i.e.,
J1、J2、J3And J4) value keep constant.
As discussed above with respect to Fig. 4 a to Fig. 4 g, can jump discretely to cover between sub-bands 36 in passband 38
While covering desired frequency range, transmission zero can be made (that is, humorous by adjusting from their nominal position movement simultaneously
Shake the frequency of element) to shift entire stopband 32, therefore in normalized frequency scope internal shift passband 38.Accordingly, with respect to figure
23a to Figure 23 c can make passband 38 from the center of subband 36 (that is, -0.80,0.0 and 0.80) movement to cover expected frequency
The continuum of scope.Therefore, if all transmission zeros 30 can be made (that is, to make from their nominal position displacement +/- 0.40
Resonant element tunes +/- 0.40 frequency range together), then each passband 38 shown in Figure 23 a to Figure 23 c will cover from-
The 33% of 1.20 to 1.20 normalized frequency scope.
While passband 38 to be located in the center of subband 36 shown in Figure 23 a to Figure 23 c, reflection zero can be made
Point 34 is in 32 internal shift of stopband (that is, the value by adjusting non-resonant elements), selectively to be moved in selected son very small 36
Passband 38.In such a case, it is possible to passband 38 is made to jump and be moved in each subband 36 between sub-bands 36, so as to
It reduces and adjusts passband 38 to cover the amount of the transmission zero 30 needed for the continuum of desired frequency range.For example, Figure 25 is illustrated
Show the variation that the value of non-resonant elements 22 is moved with passband 38 in the continuum of -1.0 to 1.0 nominal frequency range
(unchanged).
Note that the coupling values listed of Figure 25 and the coupling value that Figure 24 is listed it is entirely different and it is therefore to be understood that
It is that there are more than one coupling matrixs (that is, coupling matrix does not have unique solution) for each wave filter.For example, Figure 26 figures
It is another that solution shows that the value of non-resonant elements 22 is moved with passband 38 in the continuum of -1.0 to 1.0 nominal frequency range
One group of variation (unchanged).
By the performance characteristic of further analysis filter, such as Power Processing, intermodulation or insertion loss, can drive from
It realizes in the coupling matrix group of same filter function and selects preferable coupling matrix.Such as in co-pending patent application sequence
Number 12/163,837 (attorney number STI-008), entitled " Electrical Filters with Improved
Intermodulation Distortion, " demonstrated in, it such as can be with from the S parameter at the input/output terminal of measurement
Find out, the minor variations of filter internal structure can generate filter termination in the case where not changing filter function
Its whole is expressly incorporated in this by the enhancing of energy feature by quoting.It can be by U.S. Patent Application Serial Number 12/163,837
Disclosed in technology, including change transmission zero order be applied in filter circuit disclosed in the present application.
As it is above succinctly described in, using parameter extraction and analytical technology, then change a non-resonant elements 22 with
Passband 38 is selectively shifted in selected subband 36 can be with tuning filtering device 10.It specifically, can be under expected operating temperature
Wave filter 10 is operated to determine a variety of initial or preset adjustment performance characteristics.For example, HTS wave filters can be operated under 77 degree of K,
And it measures.For example, may then pass through Network Analyzer carries out parameter extraction.It is, for example, possible to use the S ginsengs of measurement
Number response (for example, return loss) determine with the relevant many kinds of parameters of wave filter (for example, resonant frequency and/or resonator with
The coupling value of resonator).Next, it for example, can be responded by computer optimization wave filter.Then, the wave filter of extraction is special
Difference between property and the filter characteristic of optimization can be determined and be used to provide for tuning scheme.It then can basis
The tuning scheme tuning filtering device.In numerous embodiments, for example, can by select the capacitor of open or close into
Row tuning, so that dsm controller 24 adjusts passband 38 in selected subband 36.Once tuning filtering device, so that it may
To check wave filter.For example, wave filter can be operated under its operating temperature again and measures it, to determine wave filter
New capability feature.If the performance characteristic newly tuned such as frequency response and/or S parameter response are acceptable, then can be with
The wave filter is packed for operation.
For high-performance planar filters another tunable technology be directed to use with one or more being capable of tuning filtering device
Tuned cell.For example, with reference to figure 27, the tuned cell in the form of tuning fork 40,42 can be arranged in and 18 phase of resonant element
With substrate 44 on, in the case of showing, tuned cell goes out the form of the half-wave long structure of shape using spiral into-spiral.
For purposes of illustration, as shown in Figure 1, although complete wave filter can include multiple resonant elements 18, in figure 27
Illustrate only a resonant element 18.In multi-resonator planar filter, each resonant element 18 can have tuning fork 40,
42.For example, by rule modification be coupled to tuning fork 40,42 resonant element 18 frequency can from substrate 44 remove tuning fork 40,
42 part, so as to show transmission zero corresponding with the frequency of resonant element 18 along stopband 32 compared with reflection zero 34.
In the case of multiple resonant elements 18 are tuned, the frequency of resonant element 18 can be changed with along the same shift of frequency range
Stopband 32 and passband 38.Tuning fork 40,42 is coupled to the one of resonant element 18 by a series of capacitor 46 of configurations at an angle to each other
End.
Alternately, tuning fork 40,42 can be coupled directly to resonant element 18.However, if tuning fork is connected directly to
Series capacitor design can be reduced tuning sensitivity to about the 10% of the sensitivity that can be seen that by resonator.The drop
Low sensitivity can be supported to tune using such as mechanical device (such as diamond bow pen) by hand.It can be under the microscope
The manual line is carried out with diamond bow pen.The device of alternative line tuning fork 40,42, such as laser scribing can also be used
The Line tool, focused ion beam or photoetching.Under any circumstance, in order to change the capacitance of filter circuit, physics can be passed through
It disconnects (for example, line) part tuning fork 40,42 and carrys out tuned resonator 18.
For accuracy and it is easy to tune, tuning fork 40,42 can include rough graduated scale 48 and finely divided scale 50 respectively
To provide the convenience of line, for rough and fine tune.The graduated scale 48,50 can be related to tuning scheme.Although it shows
Two tuning forks 40,42, but according to desired tuning range and tuning resolution ratio, any number of tuning fork can be used.
Technology based on parameter extraction can be used for the coupling for judging wave filter and resonant frequency and be drawn for providing
The scheme of line tuning fork.In this way, in the case of without any expensive tool, the filtering for realizing point-device tuning is provided
Device designs.
It, as shown in figure 28, can be by the tuned cell and resonant element in the form of trimming strip 52 as another embodiment
Part 18 is arranged on identical substrate 44.Trimming strip 52 is located at for example by the resonator edge of trim (that is, being disconnected with circuit)
To reduce the shunt capacitance of resonant element 18.Trimming strip 52 can have make wave filter resonant frequency shift it is different known
The centrifugal pump of amount, and the amount can be configured to binary system ordered series of numbers.
For example, on each resonant element 18, wave filter can have that there are four can make resonant frequency with binary system ordered series of numbers
The trimming strip 52 of (such as 1500KHz, 800KHz, 400KHz, 200kHz and 100KHz) displacement.In the embodiment as shown,
It provides with different size of seven trimming strips 52.Specifically, as trim (trimming), trimming strip 52 (1) causes humorous
Shake element 18 1500KHz frequency displacement；When with usually, trimming strip 52 (2) causes the frequency displacement of the 800KHz of resonant element 18；When
With usually, trimming strip 52 (3) causes the frequency displacement of the 400KHz of resonant element 18；When with usually trim, piece 52 (4) causes resonance
The frequency displacement of the 200KHz of element 18；And when with usually, each trimming strip 52 (5) -56 (7) causes resonant element 18
The frequency displacement of 100KHz.Therefore, as one embodiment, if needing 670KHz's according to a tuning scheme resonant element 18
Frequency displacement, then trimming strip 52 (2), trimming strip 52 (3) (200KHz) and trimming strip 52 (5) -56 (7) can be removed from substrate 44
In one.
In U.S. Patent Application No. 12/330,510, entitled " Systems and Methods for Tuning
It describes in Filters " and is discussed in further detail using tuning fork and trimming strip tuned resonator, by quoting its whole
It is hereby incorporated by.
It can use based on the technology of parameter extraction to judge the coupling of wave filter and resonant frequency and instruction is provided
The trimming strip 52 from resonator edge disconnection or trim is needed, to generate correct tuning filtering device.
Referring now to Figure 29, another tunable RF filter constructed according to the invention will now be described.RF wave filters 100
The variation of operating temperature can be compensated by dynamic tuning, otherwise the temperature change can cause passband 38 to be similar to Figure 11
The move mode of shown passband 78 is unintentionally moved from its nominal design location in frequency range.That is, operating temperature
Variation causes resonant element 18 and the coupling value of non-resonant elements 22 (that is, first in RF wave filters 100 from their nominal value
Begin at a temperature of tuning, the reactance of element) variation.For example, at the working temperature, the reactance of non-resonant elements 22 often changes
10 ° can change ± 1%.Therefore, RF wave filters 100 can be with the reactance of dynamic regulation resonant element 18 and non-resonant elements 22
So that passband 38 is back to its nominal position in frequency range.
RF wave filters 100 are similar with the RF wave filters 10 shown in Figure 13 a, except RF wave filters 100 also comprise electric control
Device 124, temperature sensor 126 and memory 128.It is identical with electric controller 24 shown in FIG. 1, electric controller 124 is configured
To adjust non-resonant elements 22 to introduce reflection zero and it is made to shift to move in desired frequency range along stopband 32
Narrow passband 38 is moved, and the frequency of resonant element 18 can be further adjusted by tuned cell (not shown) with along frequency
Scope movement transmission zero is responded with Optimal Filter.It is different from electric controller 24, electric controller 124 is configured to dynamic
Resonant element 18 and non-resonant elements 22 are adjusted to compensate the variation of operating temperature.
For this purpose, electric controller 124 obtains the measurement of current operating temperature from temperature sensor 126, visited from memory 128
It asks look-up table, and resonant element 18 and non-resonant elements 22 is adjusted based on look-up table.Specifically, look-up table includes multiple ginsengs
Examine operating temperature (for example, it can be with ° K distributions from -20 ° of K to 100 of 10 ° of increment) and corresponding to each reference work temperature
One group of adjusting set.Every group of adjusting sets the reactance of one resonant element 18 of control or a non-resonant elements 22.One group of allusion quotation
The adjusting of type is set will be including controlling the adjusting of multiple resonant elements 18 and non-resonant elements 22 to set.
Electric controller 124 will adjust to set by electric signal is applied to resonant element 18 and non-resonant elements 22, so that logical
The mode for being back to its nominal position in frequency range with 38 adjusts their reactance.Specifically, electric controller relatively measures
Operating temperature and look-up table in reference work temperature, selection corresponds to the reference work of operating temperature that best match measures
One group of adjusting for making temperature sets and sets adjusting resonant element 18 and non-resonant elements 22 according to one group of selected adjusting
Reactance.
In a preferred embodiment, it is similar with the tunable technology shown in Fig. 5 a to Fig. 5 d, so that selected subband 36 returns
The mode for being back to its nominal position frequency range Nei adjusts resonant element 18, and so that passband 38 is back to selected son
Method with 36 its interior nominal positions adjusts non-resonant elements 22.It alternately, can be subband 36 not to be made to be back to frequency
In the range of the mode of its nominal position adjust resonant element 18 or do not adjust, in such a case, it is possible to not make to lead to
The mode that its nominal position selected subband 36 Nei is back to 38 adjusts non-resonant elements 22.In the case of any,
Passband 38 will be made to be back to its nominal position in frequency range.
The property set is adjusted by the mechanism depending on being used to adjust resonant element 18 and non-resonant elements 22.For example, such as
The each resonant element 18 of fruit and non-resonant elements 22 include capacitor and switch in parallel, to form variable condenser network,
In order to passband 38 is located in the frequency of its nominal position or the resolution ratio provided as close possible to look-up table in frequency range
The mode of nominal position in the range of rate changes the reactance of each resonant element 18 or non-resonant elements 22, then every group of adjusting
Instruction can be included by setting opens to include each capacitor in condenser network or be closed which switch to arrange for which switch
Except the data of each capacitor in circuit.Therefore, in this case, for each operating temperature measured, look-up table will
With for the setting of the switch status of each resonant element 18 and the switched capacitor of non-resonant elements 22.By by wave filter
100 are determined at a temperature of each reference work and using above-mentioned parameter extraction and analytical technology for resonant element
The adjusting of part 18 and non-resonant elements 22 is set, it may be determined that the adjusting in look-up table is set.
Note that as shown in Figure 15 a to Figure 15 c, open or close compensation non-resonant elements 18 temperature change and
Joining capacitor can be included at least some shunt capacitors of the mobile passband 38 between different subbands 36.Further
Ground, although being described as including setting only for the adjusting of a subband 36 by look-up table, look-up table can include pair
It is set in the adjusting of multiple subbands 36.In this case, the adjusting of particular sub-band 36 therein is currently located at for passband 38
Setting can be used to passband 38 be moved to its nominal position in frequency range in response to temperature change.
While there have shown and described that the specific embodiment of the present invention it should be appreciated that described above
The present invention is not intended to be limited in these embodiments.To those skilled in the art it is apparent that in the essence without departing from the present invention
God can make a variety of change and modification under conditions of scope.For example, the present invention have far beyond with input with it is defeated
The application of the wave filter gone out, and the present invention specific embodiment can be used to form duplexer, multiplexer, channel device,
Reactance switch etc., wherein, use low-loss selective circuit.Therefore, it is contemplated that covering to fall by claim
Replacement, modification and equivalent in the spirit and scope of the present invention of restriction.
Claims (56)
1. a kind of radio frequency wave filter (10), including：
Signal transmission path (12), the signal transmission path have input (14) and output (16)：
Multiple resonant elements (18), the multiple resonant element along it is described input (14) and it is described export (16) between it is described
Signal transmission path (12) is arranged；And
The resonant element (18) is coupled together forming tool by multiple non-resonant elements (22), the multiple non-resonant elements
Have between multiple transmission zeros (30) corresponding with each frequency of the resonant element (18) and the transmission zero (30)
At least one subband (36) stopband (32), wherein, the non-resonant elements (22) include at least one variable disresonance
Element (22), at least one variable non-resonant elements are used in the stopband (32) be selectively introducing to one few
Reflection zero (34) in a subband at least one subband (36) create passband (38), wherein, the stopband
(32) in microwave frequency range.
2. RF wave filters (10) according to claim 1, wherein, at least one subband (36) includes multiple subbands
(36)。
3. RF wave filters (10) according to claim 2, wherein, at least one variable non-resonant elements (22) are used
In shifting at least one reflection zero (34) along the stopband (32) with multiple selected sons in the subband (36)
The passband (38) is created with interior.
4. RF wave filters (10) according to claim 3, wherein, the passband (38) is in the multiple selected subband (36)
It is interior that there is different bandwidth.
5. RF wave filters (10) according to claim 2, wherein, at least one variable non-resonant elements (22) are used
It is created at least another reflection zero (34) of the stopband (32) internal shift with another subband in the subband (36) is interior
Another passband (38).
6. RF wave filters (10) according to claim 1, wherein, at least one variable non-resonant elements (22) are used
In along the stopband (32) shift at least one reflection zero (34) in one subband (36) selectively
The mobile passband (38).
7. RF wave filters (10) according to claim 1, wherein, at least one reflection zero (34) includes multiple anti-
Penetrate zero point (34).
8. RF wave filters (10) according to claim 1, wherein, at least one variable non-resonant elements (22) bag
Include multiple variable non-resonant elements (22).
9. RF wave filters (10) according to claim 1, further comprise at least one tuned cell (20), it is described at least
One tuned cell is configured as changing the frequency of at least one resonant element (18).
10. RF wave filters (10) according to claim 9, wherein, at least one tuned cell (20) is configured as
Change the frequency of at least one resonant element (18), with along the stopband (32) compared with it is described it is at least one reflection zero
Point (34) shifts the transmission zero (30) corresponding with each frequency of at least one resonant element (18).
11. the RF wave filters (10) according to wooden fork profit requires 9, wherein, at least one tuned cell includes multiple tunings
Element, the multiple tuned cell are configured as changing the frequency of the resonant element (18) with along the same shift of frequency range
The stopband (32) and the passband (38).
12. RF wave filters (10) according to claim 1, wherein, at least one variable non-resonant elements (22)
With adjustable susceptance.
13. RF wave filters (10) according to claim 1, wherein, at least one variable non-resonant elements (22)
Including at least one in the following：Variable condenser, low loss switching, varactor and switched capacitor.
14. RF wave filters (10) according to claim 1, wherein, each in the resonant element (18) is including thin
Film lumped element configuration.
15. RF wave filters (10) according to claim 14, wherein, the thin film lumped element structure includes high-temperature superconductor
Body (HTS).
16. RF wave filters (10) according to claim 1, further comprise controller (24), the controller is configured
The electric signal of at least one variable non-resonant elements (22) is adjusted for generation.
17. RF wave filters (10) according to claim 1, wherein, each in the resonant element (18) includes sound
Wave resonator.
18. RF wave filters (10) according to claim 1, wherein, the multiple non-resonant elements (22) include with it is described
Resonant element (18) is distinguished more than first a non-resonant elements (22 (1)) of coupled in parallel and is distinguished with the resonant element (18)
A non-resonant elements (22 (3)) more than the second of coupled in series, wherein, a non-resonant elements (22 (1)) more than described first include institute
State at least one variable non-resonant elements (22), at least one variable non-resonant elements are used to not change described the
In the case of any one more than two in a non-resonant elements (22 (3)), introduce to selection domestic animal in the stopband (32) it is described extremely
A few reflection zero (34).
19. RF wave filters (10) according to claim 1, wherein, at least one variable non-resonant elements (22)
In each have and be connected in parallel to each other coupling to form multiple passive reactive elements (C of passive reactance circuit1-C3) and coupling
To the passive reactive elements (C1-C3) at least one at least one switch (S1-S2), wherein, it is described it is at least one can
The reactance of each in the non-resonant elements (22) of change is configured as by operating at least one switch (S1-S2) with choosing
The passive reactance circuit is made to selecting property to include or not include at least one passive reactive elements (C1-C3) described to change
The reactance of passive reactance circuit and be changed, so as to adjust at least one reflection zero (34) compared with the transmission zero
(30) position.
20. RF wave filters (10) according to claim 19, wherein, the passive reactive elements (C1-C3) in each
It is capacitor, and the passive reactance circuit is condenser network.
21. RF wave filters (10) according to claim 20, wherein, at least one switch (S1-S2) opened including first
Close (S1) and second switch (S2), and wherein, each at least one variable non-resonant elements (22) includes that
This coupled in parallel is to form the three of condenser network capacitor (C1-C3), the condenser network, which has, is coupled to the first switch
(S1) the first capacitor (C1) and be coupled to the second switch (S2) the second capacitor (C2)。
22. RF wave filters (10) according to claim 1, further comprise controller (24), the controller is configured
At least one switch (S is operated for generation1-S2) to change the reactance of at least one variable non-resonant elements (22)
Electric signal.
23. RF wave filters (10) according to claim 1 is wherein, the microwave frequency range is 800-900MHz.
24. RF wave filters (10) according to claim 1, wherein, the microwave frequency range is 1,800-2,200MHz.
25. RF wave filters (10) according to claim 1, wherein, the multiple resonant element (18) is arranged in substrate
(44) on, the RF wave filters (10) further comprise being arranged on the substrate (44) and being electrically coupled to respectively at least one
At least one tuned cell (40,42,52) of the resonant element (18), wherein, at least one tuned cell (40,42,
52) part for each tuned cell in is configured as removing to change each resonant element (18) from the substrate (44)
Frequency.
26. RF wave filters (10) according to claim 25, wherein, at least one tuned cell (40,42,52) bag
Include multiple tuned cells (40,42,52), the multiple tuned cell be configured as changing the frequency of the resonant element (18) with
Along frequency range with stopband described in shift (32) and the passband (38).
27. RF wave filters (10) according to claim 25, wherein, the part of each tuned cell (40,42,52)
It is configured as removing from the substrate (44) via laser, diamond line, focused ion beam or photoetching.
28. RF wave filters (10) according to claim 25, wherein, each tuned cell (40,42,52) includes one
A or multiple trimming strips (52), one or more of trimming strips can be removed to reduce the bypass of each resonant element (18)
Capacitance.
29. RF wave filters (10) according to claim 28, wherein, one or more of trimming strips (52) include connection
Trimming strip (52) array on the edge of each resonant element (18).
30. RF wave filters (10) according to claim 29, wherein, the size and position that trimming strip (52) array has
Put be configured to provide to limit the two of the shunt capacitance element of the varying dimensions of tuning range and minimum tuning resolution ratio into
Array processed.
31. RF wave filters (10) according to claim 25, wherein, each tuned cell (40,42,52) includes sound
It pitches (40,42), the tuning fork is configured as by trim reducing the shunt capacitance of each resonant element (18).
32. RF wave filters (10) according to claim 1 further comprise electric controller (124), the electric controller quilt
It is configured to receive the operating temperature of the RF wave filters and is adjusted based on the operating temperature received described at least one variable
Non-resonant elements (22), so as to along the selectively moved at least one reflection zero (34) of the stopband (32) with
The mobile passband (38) in one subband (36).
33. RF wave filters (10) according to claim 32, further comprise temperature sensor (126), the temperature passes
Sensor is configured as measuring the operating temperature, wherein, the electric controller (124) is configured as from the temperature sensor
(126) measured operating temperature is received.
34. RF wave filters (10) according to claim 32 further comprise the memory for storing look-up table, the lookup
Table includes the multiple reference work temperature for corresponding respectively to the different operating temperatures and multiple groups for adjusting setting, wherein,
The electric controller (124) is configured as the multiple reference work temperature in measured operating temperature and the look-up table
Degree is compared, and selects what the adjusting corresponding with the reference work temperature closest to measured operating temperature was set
Group, and according to the group adjusting at least one variable non-resonant elements (22) for adjusting and setting.
35. RF wave filters (10) according to claim 32, wherein, the electric controller (124) is configured as adjusting institute
State at least one variable non-resonant elements, so as to along the stopband (32) it is selectively moved it is described it is at least one reflection zero
Point (34), so that the passband (38) is back to the nominal design location in frequency range.
36. go through the RF wave filters (10) stated according to claim 35, wherein, the electric controller is configured as based on being received
Operating temperature adjusts at least one resonant element in the resonant element (18), thus along the stopband (32) selectively
The mobile transmission zero (30) corresponding with each frequency of at least one resonant element (18), so that the passband
(38) nominal design location being back in the frequency range.
37. a kind of method for tuning RF wave filters (10) according to claim 25, including removing each tuning member
The part of part (40,42,52), so as to change the frequency of each resonant element (18).
38. according to the method for claim 37, wherein, the part of each tuned cell (40,42,52) is from the base
Plate (44) removes, so as to the frequency of changing each resonant element (18) and along the stopband (32) compared with it is described extremely
A few reflection zero (34) shifts the transmission zero (30) corresponding with the frequency of each resonant element (18).
39. according to the method for claim 37, wherein, the part of each tuned cell (40,42,52) is from the base
Plate (44) removes, so as to the frequency of changing each resonant element (18) and along the stopband (32) compared with it is described extremely
A few reflection zero (34) shifts the transmission zero (30) corresponding with the frequency of each resonant element (18).
40. according to the method for claim 37, wherein, the part of each tuned cell (40,42,52) is via sharp
Light, diamond line, focused ion beam or photoetching are removed from the substrate (44).
41. according to the method for claim 37, wherein, each tuned cell (40,42,52) includes one or more
Trimming strip (52), one or more of trimming strips are removed to reduce the shunt capacitance of each resonant element (18).
42. rod is according to the method described in claim 41, wherein, one or more of trimming strips (52) include being connected to described each
Trimming strip (52) array on the edge of a resonant element (18).
43. according to the method for claim 42, wherein, the size and position that trimming strip (52) array has are set
Into the binary array of the shunt capacitance element for the varying dimensions for providing to limit tuning range and minimum tuning resolution ratio.
44. according to the method for claim 37, wherein, each tuned cell (40,42,52) include tuning fork (40,
42), the tuning fork by trim to reduce the shunt capacitance of each resonant element (18).
45. a kind of method for tuning RF wave filters (10) according to claim 1, including：
The response of the RF wave filters (10) is measured to generate one group of measurement data；
One group of measurement data is analyzed to optimize to extract one or more wave filter design parameters；
Optimize one or more of wave filter design parameters and it is expected wave filter response to realize；
Tuning scheme is generated based on the one or more wave filter design parameters optimized；And
By changing a non-resonant elements at least one non-resonant elements (22), to be selected along the stopband (32)
Selecting property mobile phase answer reflection zero (34) so as in the selected subband of the subband (36) the mobile passband (38) adjust
The humorous RF wave filters (10).
46. the method according to claim 11, wherein, described in the expectation operating temperature measurement in the RF wave filters (10)
The response of RF wave filters (10).
47. according to the method for claim 45, wherein, one or more of wave filter design parameters include resonator frequency
One or two in the coupling value of rate resonator and resonator.
48. according to the method for claim 45, wherein, one non-resonant elements (22) use electric controller (124)
To change.
49. the sunlight method according to claim 45, wherein, one non-resonant elements (22) have be connected in parallel to each other coupling with
Form multiple capacitor (C of condenser network1-C3) and be coupled to the capacitor (C1-C3) at least one at least one
A switch (S1-S2), wherein, the reactance of the non-resonant elements (22) is by operating at least one switch with selectively
The condenser network is made to include or not include at least one capacitor (C1-C3) changing the capacitance of the condenser network and
Change, so that the selectively moved reflection zero (34) is with the mobile institute in selected subband (36) in the stopband (32)
State passband (38).
50. a kind of method for tuning RF wave filters (10) according to claim 1, wherein, the stopband (32), which limits, adjusts
Humorous scope, the described method includes：
The RF wave filters (10) are configured from first frequency configuration modification for second frequency, wherein, the RF wave filters (10)
There is first group of passband in the tuning range limited by the stopband (32) when in first frequency configuration
(38) characteristic, and wherein, the RF wave filters (10) have when in second frequency configuration in the stopband
(32) different second group passband (38) characteristic in tuning range.
51. the method according to claim 11, wherein, first group of passband (38) characteristic and second group of passband
(38) characteristic has different centre frequencies.
52. the method according to claim 11, wherein, first group of passband (38) characteristic and second group of passband
(38) characteristic has different bandwidth.
53. the method according to claim 11, wherein, first group of passband (38) characteristic and second group of passband
(38) characteristic has the discontinuous passband (38) of different number.
54. the method according to claim 11, wherein, by least one reflection described in the stopband (32) internal shift
Zero point (34), the RF wave filters (10) are revised as the second frequency configuration from the first frequency with tawny daylily.
55. method according to claim 54, wherein, the stopband (32) has multiple transmission zeros (30), and its
In, displacement of at least one reference zero in frequency is more than displacement of the transmission zero (30) in frequency.
56. according to the method for claim 50, wherein, the RF wave filters (10) are being repaiied from first frequency configuration
When being changed to the second frequency configuration, the insertion loss of the RF wave filters (10) is minimized.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
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| US14/214,249 US8922294B2 (en) | 2006-11-17 | 2014-03-14 | Low-loss tunable radio frequency filter |
| US14/214,249 | 2014-03-14 | ||
| CN201410854568.XA CN104917479B (en) | 2007-06-27 | 2014-12-31 | The radio-frequency filter of low-loss adjustable |
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| CN201410854568.XA Division CN104917479B (en) | 2007-06-27 | 2014-12-31 | The radio-frequency filter of low-loss adjustable |
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| CN112087218A (en) * | 2020-08-27 | 2020-12-15 | 中国科学技术大学 | Continuous adjustable dual-band-stop filter based on surface acoustic wave resonator |
| CN114221101A (en) * | 2018-12-14 | 2022-03-22 | 康普公司意大利有限责任公司 | Filter with resonators having negative coupling |
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| KR101877883B1 (en) * | 2016-12-30 | 2018-07-13 | 이효윤 | Filter having failure prediction function for removing noise |
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| CN108063605B (en) | 2022-01-18 |
| KR101691264B1 (en) | 2016-12-29 |
| KR20150107585A (en) | 2015-09-23 |
| JP6158780B2 (en) | 2017-07-05 |
| JP2015177542A (en) | 2015-10-05 |
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