CN108039821A - A kind of current stress optimization double Method of Phase-Shift Controlling of double active full-bridge DC-DC converters - Google Patents

A kind of current stress optimization double Method of Phase-Shift Controlling of double active full-bridge DC-DC converters Download PDF

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CN108039821A
CN108039821A CN201711266394.5A CN201711266394A CN108039821A CN 108039821 A CN108039821 A CN 108039821A CN 201711266394 A CN201711266394 A CN 201711266394A CN 108039821 A CN108039821 A CN 108039821A
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msub
mrow
mfrac
converter
phase
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CN108039821B (en
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宋文胜
安峰
杨柯欣
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Southwest Jiaotong University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter

Abstract

The present invention discloses a kind of double Method of Phase-Shift Controlling of current stress optimization of double active full-bridge DC DC converters, including：According to the averaging model of double active full-bridge DC DC converter output voltages, build the state mean space equation of output voltage, then sliding-model control is carried out to the differential term of output voltage in the state mean space equation of output voltage, obtain the predicted value of converter output voltage, with reference to Lagrangian and double power modules of the active full-bridge DC DC converters under dual Phaseshift controlling, interior phase-shift phase of the converter under current stress Optimal Control Strategy is obtainedD 1, evaluation function is built according to prediction output voltage and reference voltageJ, to evaluation functionJDerivation processing is carried out, double active full-bridge DC DC converters is obtained and optimizes the outer phase-shift phase under dual phase shift predictive control strategy in current stressD 2.The method of the present invention has the advantages that dynamic response is fast, efficient, control process is simple and is easy to Digital Implementation, has very strong practicality.

Description

A kind of current stress optimization double Phaseshift controllings of double active full-bridge DC-DC converters Method
Technical field
The present invention relates to the technical field of power electronics, and being specially a kind of electric current of double active full-bridge DC-DC converters should The double Method of Phase-Shift Controlling of power optimization.
Background technology
Double active full-bridge DC-DC converters due to its with power density height, electrical isolation, energy in bidirectional flow and easily Many advantages, such as realizing Sofe Switch, and it is widely used in the technologies such as electric automobile, photovoltaic generation, uninterrupted power source and energy storage neck Domain.
At present, double active full-bridge DC-DC converters have two kinds of common control modes：
Pulse width modulation controlled, this method is simple and is easily achieved, but due to the virtual value of full-bridge inverting output AC voltage Input direct voltage can only be less than, therefore its range of regulation is restricted.Except this, this method controls the dynamic characteristic of downconverter It is poor.
Phaseshift controlling, under the control method, changer system inertia is small, dynamic response is fast and Sofe Switch easy to implement. But be only the phase-shift phase between the square-wave voltage that two H bridges export due to controlled quentity controlled variable in single Phaseshift controlling, and converter master Will be by transformer leakage inductance (or series connection auxiliary induction) come transmission energy.Therefore, when input voltage and output voltage mismatch, The inductive current stress of converter can greatly increase, and excessive current stress can cause transducer loose increase, efficiency to decline very To the damage of switching device.In order to reduce current stress, a variety of current stress optimization methods are suggested, the optimization method proposed Although can effectively reduce current stress, the control structure of optimization method is complex, while the power of converter Control is controlled only by traditional PI to realize, causes the dynamic response of converter slower.
The content of the invention
In view of the above-mentioned problems, it is an object of the invention to provide one kind can solve existing current stress system optimizing control The current stress optimization two-phase of the double active full-bridge DC-DC converters for the problems such as middle dynamic response is slowly and control structure is complicated moves control Method processed.Technical solution is as follows：
A kind of current stress optimization double Method of Phase-Shift Controlling of double active full-bridge DC-DC converters, including：
S1：According to the averaging model of double active full-bridge DC-DC converter output voltages, the shape of structure converter output voltage State mean space equation：
Wherein, C2To export lateral capacitance, UoFor output voltage, f is switching frequency, and L is auxiliary induction, and R is load resistance, UinFor the input voltage of converter, D1、D2Respectively interior phase-shift phase and outer phase-shift phase of the converter under dual Phaseshift controlling；
S2：Sliding-model control is carried out to the state mean space equation of the converter output voltage, and according to discretization The state mean space equation of converter output voltage after processing, is calculated converter and is exported in next controlling cycle The predicted value of voltage：
Wherein, Uo(tk)、Uin(tk)、io(tk) it is respectively tkThe sampling and outputting voltage of moment converter, input voltage and defeated Go out electric current；Uo(tk+1) it is tk+1The converter output voltage that moment is predicted；
S3：According to the power module of Lagrangian and converter under dual Phaseshift controlling, converter is calculated Interior phase-shift phase D under current stress Optimal Control Strategy1：
Wherein, p0For the transimission power of converter, k is voltage conversion ratio；
S4：According to prediction output voltage and reference output voltage structure evaluation function J：
Wherein, Uo *(tk) be converter reference output voltage；
Derivation processing is carried out to evaluation function J, converter is calculated and optimizes dual phase shift PREDICTIVE CONTROL in current stress Outer phase-shift phase D under strategy2：
Wherein, Δ Uo(tk) it is tkThe output voltage of moment converter passes through the output of outer shroud proportional, integral PI controllers Value.
Further, the side of the state mean space equation of double active full-bridge DC-DC converter output voltages is built Method includes：
According to the symmetry of H bridges output voltage and inductive current waveform, in half period, by the working status of converter It is divided into four-stage；For each working status, the state equation of output voltage is established respectively：
Wherein, iL1,iL2,iL3,iL4The average value of inductive current in each stage, T are represented respectivelyhsFor the one of switch periods Half；
According to output voltage in the state equation of four-stage, according to equivalent time average principle, the output electricity is built The state mean space equation of pressure.
Further, the method for the prediction output voltage of acquisition double active full-bridge DC-DC converters is：Using Europe Draw forward approach to carry out discrete processes to the differential term of output voltage in the state mean space equation of converter output voltage, obtain Prediction output voltage of the converter in next controlling cycle.
Further, the converter is obtained outside the optimization that current stress optimizes under dual phase shift predictive control strategy Phase-shift phase
D2Method be：
It is and right with square structure object function of the difference of double active full-bridge DC-DC converter output voltages and reference voltage Object function derivation, it is zero to obtain outer phase-shift phase to make its derivative, and the outer phase-shift phase is compensated, and obtains double active full-bridges The outer phase-shift phase D of DC-DC converter2：
Wherein,a1For intermediate variable, no physics Meaning.
Further, the Lagrangian is defined as：
E=Imax+λ(p-p*)
Wherein, E represents Lagrangian, and λ is Lagrange multiplier, p*For the given power of converter；ImaxFor conversion The current stress perunit value of device.
The beneficial effects of the invention are as follows：The present invention is averaged according to the state of double active full-bridge DC-DC converter output voltages Spatial model, predicts output voltage of the converter in next controlling cycle, and according to prediction output voltage and reference voltage Difference square establish evaluation function J, make its derivative be zero evaluation function J derivations, obtain optimization phase-shift phase.Simultaneously because open The influence of the factors such as pipe tube voltage drop, dead time and control delay is closed, optimization phase-shift phase is compensated, obtains final phase Move controlled quentity controlled variable；And current stress optimal control method proposed by the present invention, for converter load resistance and input voltage Mutation can respond rapidly to；Have the advantages that dynamic response is fast, efficient, control process is simple and is easy to Digital Implementation, have Stronger practicality.
Brief description of the drawings
Fig. 1 is the topology diagram of double active full-bridge DC-DC converters.
Fig. 2 is double active full-bridge DC-DC converters in dual Method of Phase-Shift Controlling (0≤D1≤D2≤ 1) transformer both sides under Voltage and inductive current waveform diagram.
Fig. 3 is double active full-bridge DC-DC converters in dual Method of Phase-Shift Controlling (0≤D2≤D1≤ 1) transformer both sides under Voltage and inductive current waveform diagram.
Fig. 4 is that double active full-bridge DC-DC converters optimize the control under dual phase shift forecast Control Algorithm in current stress Flow chart.
Fig. 5 is voltage electricity when double active full-bridge DC-DC converters start under conventional current stress optimization control method Flow oscillogram.
Fig. 6 is double active full-bridge DC-DC converters when starting under current stress optimizes dual phase shift forecast Control Algorithm Voltage and current waveform.
Fig. 7 is electricity when double active full-bridge DC-DC converters load switching under conventional current stress optimization control method Current voltage oscillogram.
Fig. 8 is loaded in the case where current stress optimizes dual phase shift forecast Control Algorithm for double active full-bridge DC-DC converters and cut Voltage and current waveform when changing.
Fig. 9 is double active full-bridge DC-DC converters when input voltage switches under conventional current stress optimization control method Oscillogram.
Figure 10 is that double active full-bridge DC-DC converters input electricity in the case where current stress optimizes dual phase shift forecast Control Algorithm Oscillogram when crush-cutting changes.
Embodiment
The present invention is described in further details with specific embodiment below in conjunction with the accompanying drawings.The present embodiment is according to Fig. 1 Double active full-bridge DC-DC converters topology diagram, to for double active full-bridge DC-DC converters current stress optimization Dual phase shift forecast Control Algorithm is described in detail.
First, according to the averaging model of double active full-bridge DC-DC converter output voltages, converter output voltage is built State mean space model and its state differential equation.
As shown in Fig. 2, when double active full-bridge DC-DC converters are under dual Phaseshift controlling, phase-shift phase meets 0≤D1≤D2 It is total according to voltage and current waveform of the converter under dual Phaseshift controlling, double active full-bridge converters at this time during≤1 relation Share eight kinds of working statuses.Due to the output voltage of H bridges and the symmetry of inductive current waveform, therefore only need to be in half period It is modeled, its output voltage state equation is：
Wherein, UoFor output voltage, R is load resistance, C2To export lateral capacitance, ThsFor the half of switch periods, iL1、iL2 And iL4The average value for the inductive current being illustrated respectively in the period, D1For the interior phase-shift phase of converter, D2For outer phase-shift phase.
Each differential equation in above-mentioned is merely represented in output voltage and inductive current and load current under the working status Between relation, can represent the differential equation of converter characteristic in whole switch periods to establish, be inscribed when demand obtains each Inductor current value：
Wherein, iL(t0)、iL(t1)、iL(t2)、iL(t3)、iL(t4) it is illustrated respectively in t0、t1、t2、t3、t4When the electricity inscribed Electrification flow valuve；N is transformer voltage ratio；L is auxiliary induction；F is switching frequency；K is voltage conversion ratio.
Further, according to it is each when inscribe inductor current value, obtain double active full-bridge DC-DC converters in each period The average value of interior inductive current：
Convolution (1), formula (2) and formula (3), the state for being derived by double active full-bridge DC-DC converter output voltages are put down Equal space equation：
With reference to figure 3, when phase-shift phase meets 0≤D1≤D2During≤1 relation, it is defeated can ibid to obtain double active full-bridge DC-DC converters Go out the state mean space equation of voltage：
Discrete processes, the letter between structure prediction output voltage and sampling and outputting voltage are carried out to state mean space equation Number relational expression.The differential term of output voltage reflects the variation tendency of output voltage to a certain extent in formula (4), using Euler Forward approach carries out sliding-model control to formula (4) respectively, obtains：
And then obtain double prediction output voltages of the active full-bridge DC-DC converter in next controlling cycle：
Wherein, Uo(tk) represent in tkThe output voltage of moment converter, i.e. sampled voltage；Uo(tk+1) represent according to current The circuit parameter of sample information and converter, predict in tk+1The output voltage of moment converter.
Similarly, according to formula (5), in 0≤D2≤D1The prediction of double active full-bridge DC-DC converter output voltages is obtained under≤1 Value：
With square structure evaluation function of the difference of the predicted value of output voltage and reference value：
The stabilization of double active full-bridge DC-DC converter output voltages in order to control, is derived pre- according to formula (7) and formula (8) Output voltage is surveyed, define the predicted value of output voltage and the difference of reference value square is evaluation function J：
From formula (9), the smaller output voltage for representing converter in subsequent time of evaluation function is closer to reference to electricity Pressure, make it that evaluation function is minimum, obtains its derivation：
Wherein,
Due to actual switch pipe tube voltage drop, dead time and control delay etc. factor influence so that theoretical model with Actual physics model causes the output voltage of converter inaccurate there are deviation, therefore need to add phase-shift phase compensation, and then is used Optimize the outer phase-shift phase D under dual phase shift forecast Control Algorithm in the current stress of double active full-bridge DC-DC converters2：
Wherein, Δ Uo(tk) it is tkThe output voltage of moment converter passes through the output of outer shroud proportional, integral (PI) controller Value.
Similarly, when converter meets 0≤D2≤D1During≤1 relation, obtain being used for the double active full-bridge DC-DC changes of PREDICTIVE CONTROL The outer phase-shift phase D of parallel operation stress optimization2：
Build Lagrangian：With 0≤D1≤D2Exemplified by≤1, defining Lagrangian is：
E=Imax+λ(p-p*)(13)
Wherein, E represents Lagrangian, and λ is Lagrange multiplier, p*For giving for double active full-bridge DC-DC converters Determine power；ImaxFor the current stress perunit value of converter.
Formula (6) and formula (7) are substituted into formula (13), and derivation is carried out to Lagrangian and is obtained：
λ in formula (14) is eliminated, obtains outer phase-shift phase D2With interior phase-shift phase D1Between relational expression：
Convolution (11), formula (12) and formula (15), obtain converter phase shift in the optimization under current stress optimal control Measure D1：
Reference table 1, which show under the criterion of double active full-bridge DC-DC converter operation modes and every kind of mode most Low current stress and the optimal phase-shift phase D calculated1And D2。
Table 1
With reference to figure 4, by input voltage, output voltage and the output current to double active full-bridge DC-DC converters into Row real-time sampling, the state mean space equation of associative transformation device output voltage, predicts it in next controlling cycle Output voltage, and the evaluation function J of output voltage is established, by evaluation function derivation, obtaining optimization phase-shift phase.
Understand that in conventional current stress optimization control algolithm, the output voltage of converter reaches steady with reference to figure 5 and Fig. 6 Determining state needs 323ms；And under control strategy in the present invention, the output voltage of converter reaches stable state and needs only to 44ms, the response of its output voltage is rapid, far smaller than, better than conventional current stress optimization control algolithm.
Understood with reference to figure 7 and Fig. 8, when load resistance is mutated, in conventional current stress optimization control algolithm, output electricity Pressure, which returns to stable state, needs 168ms, and under control strategy in the present invention, load voltage and electric current remain steady Fixed, its dynamic response is rapid.
Understood with reference to figure 9 and Figure 10, when input voltage mutation, in conventional current stress optimization control algolithm, input Voltage needs 379ms to stable state, and under control strategy in the present invention, the output voltage of converter responds rapidly to, and begins Keep stablizing eventually.
The current stress of the present invention optimizes dual phase shift forecast Control Algorithm, for double active full-bridge DC-DC converters It can be responded rapidly to when load resistance and input voltage mutation, with dynamic response is fast, efficient, control process is simple and easy In the Digital Implementation the advantages that, there is very strong practicality.

Claims (5)

  1. A kind of 1. double Method of Phase-Shift Controlling of current stress optimization of double active full-bridge DC-DC converters, it is characterised in that including：
    S1：According to the averaging model of double active full-bridge DC-DC converter output voltages, the state of structure converter output voltage is put down Equal space equation：
    <mrow> <msub> <mi>C</mi> <mn>2</mn> </msub> <mfrac> <mrow> <msub> <mi>dU</mi> <mi>o</mi> </msub> </mrow> <mrow> <mi>d</mi> <mi>t</mi> </mrow> </mfrac> <mo>=</mo> <mfrac> <mrow> <mn>2</mn> <msub> <mi>D</mi> <mn>2</mn> </msub> <mrow> <mo>(</mo> <mn>1</mn> <mo>-</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>)</mo> </mrow> <mo>-</mo> <msubsup> <mi>D</mi> <mn>1</mn> <mn>2</mn> </msubsup> </mrow> <mrow> <mn>4</mn> <mi>f</mi> <mi>L</mi> </mrow> </mfrac> <msub> <mi>U</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> <mo>-</mo> <mfrac> <msub> <mi>U</mi> <mi>o</mi> </msub> <mi>R</mi> </mfrac> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <mn>1</mn> </mrow>
    <mrow> <msub> <mi>C</mi> <mn>2</mn> </msub> <mfrac> <mrow> <msub> <mi>dU</mi> <mi>o</mi> </msub> </mrow> <mrow> <mi>d</mi> <mi>t</mi> </mrow> </mfrac> <mo>=</mo> <mfrac> <mrow> <msub> <mi>D</mi> <mn>2</mn> </msub> <mrow> <mo>(</mo> <mn>2</mn> <mo>-</mo> <mn>2</mn> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>-</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>)</mo> </mrow> </mrow> <mrow> <mn>4</mn> <mi>f</mi> <mi>L</mi> </mrow> </mfrac> <msub> <mi>U</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> <mo>-</mo> <mfrac> <msub> <mi>U</mi> <mi>o</mi> </msub> <mi>R</mi> </mfrac> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>&amp;le;</mo> <mn>1</mn> </mrow>
    Wherein, C2To export lateral capacitance, UoFor output voltage, f is switching frequency, and L is auxiliary induction, and R is load resistance, UinFor The input voltage of converter, D1、D2Respectively interior phase-shift phase and outer phase-shift phase of the converter under dual Phaseshift controlling；
    S2：Sliding-model control is carried out to the state mean space equation of the converter output voltage, and according to sliding-model control The state mean space equation of converter output voltage afterwards, is calculated converter output voltage in next controlling cycle Predicted value：
    <mrow> <msub> <mi>U</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mrow> <mi>k</mi> <mo>+</mo> <mn>1</mn> </mrow> </msub> <mo>)</mo> </mrow> <mo>=</mo> <mfrac> <mrow> <msub> <mi>D</mi> <mn>2</mn> </msub> <mrow> <mo>(</mo> <mn>1</mn> <mo>-</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>)</mo> </mrow> <mo>-</mo> <msubsup> <mi>D</mi> <mn>1</mn> <mn>2</mn> </msubsup> </mrow> <mrow> <mn>2</mn> <msup> <mi>f</mi> <mn>2</mn> </msup> <msub> <mi>LC</mi> <mn>2</mn> </msub> </mrow> </mfrac> <msub> <mi>U</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>-</mo> <mfrac> <mrow> <msub> <mi>i</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> </mrow> <mrow> <msub> <mi>fC</mi> <mn>2</mn> </msub> </mrow> </mfrac> <mo>+</mo> <msub> <mi>U</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <mn>1</mn> </mrow>
    <mrow> <msub> <mi>U</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mrow> <mi>k</mi> <mo>+</mo> <mn>1</mn> </mrow> </msub> <mo>)</mo> </mrow> <mo>=</mo> <mfrac> <mrow> <msub> <mi>D</mi> <mn>2</mn> </msub> <mrow> <mo>(</mo> <mn>2</mn> <mo>-</mo> <mn>2</mn> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>-</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>)</mo> </mrow> </mrow> <mrow> <mn>4</mn> <msup> <mi>f</mi> <mn>2</mn> </msup> <msub> <mi>LC</mi> <mn>2</mn> </msub> </mrow> </mfrac> <msub> <mi>U</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>-</mo> <mfrac> <mrow> <msub> <mi>i</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> </mrow> <mrow> <msub> <mi>fC</mi> <mn>2</mn> </msub> </mrow> </mfrac> <mo>+</mo> <msub> <mi>U</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>&amp;le;</mo> <mn>1</mn> </mrow>
    Wherein, Uo(tk)、Uin(tk)、io(tk) it is respectively tkSampling and outputting voltage, input voltage and the output electricity of moment converter Stream；Uo(tk+1) it is tk+1The converter output voltage that moment is predicted；
    S3：According to the power module of Lagrangian and converter under dual Phaseshift controlling, converter is calculated in electricity Flow the interior phase-shift phase D under stress optimization control strategy1：
    <mrow> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>=</mo> <mrow> <mo>(</mo> <mi>k</mi> <mo>-</mo> <mn>1</mn> <mo>)</mo> </mrow> <msqrt> <mfrac> <mrow> <mn>1</mn> <mo>-</mo> <msub> <mi>p</mi> <mn>0</mn> </msub> </mrow> <mrow> <mn>2</mn> <mrow> <mo>(</mo> <msup> <mi>k</mi> <mn>2</mn> </msup> <mo>-</mo> <mn>2</mn> <mi>k</mi> <mo>+</mo> <mn>3</mn> <mo>)</mo> </mrow> </mrow> </mfrac> </msqrt> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <mn>1</mn> </mrow>
    <mrow> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>=</mo> <mn>1</mn> <mo>-</mo> <msqrt> <mfrac> <mrow> <mo>(</mo> <mi>k</mi> <mo>-</mo> <mn>1</mn> <mo>)</mo> <msub> <mi>p</mi> <mn>0</mn> </msub> </mrow> <mrow> <mn>2</mn> <mrow> <mo>(</mo> <mi>k</mi> <mo>+</mo> <mn>3</mn> <mo>)</mo> </mrow> </mrow> </mfrac> </msqrt> <mo>-</mo> <mfrac> <mrow> <msqrt> <mn>2</mn> </msqrt> <msub> <mi>p</mi> <mn>0</mn> </msub> </mrow> <msqrt> <mrow> <msub> <mi>p</mi> <mn>0</mn> </msub> <mrow> <mo>(</mo> <mi>k</mi> <mo>-</mo> <mn>1</mn> <mo>)</mo> </mrow> <mrow> <mo>(</mo> <mi>k</mi> <mo>+</mo> <mn>3</mn> <mo>)</mo> </mrow> </mrow> </msqrt> </mfrac> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>&amp;le;</mo> <mn>1</mn> </mrow>
    Wherein, p0For the transimission power of converter, k is voltage conversion ratio；
    S4：According to prediction output voltage and reference output voltage structure evaluation function J：
    <mrow> <mi>J</mi> <mo>=</mo> <msup> <mrow> <mo>&amp;lsqb;</mo> <msub> <mi>U</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mrow> <mi>k</mi> <mo>+</mo> <mn>1</mn> </mrow> </msub> <mo>)</mo> </mrow> <mo>-</mo> <msubsup> <mi>U</mi> <mi>o</mi> <mo>*</mo> </msubsup> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>&amp;rsqb;</mo> </mrow> <mn>2</mn> </msup> </mrow>
    Wherein, Uo *(tk) be converter reference output voltage；
    Derivation processing is carried out to evaluation function J, converter is calculated and optimizes dual phase shift predictive control strategy in current stress Under outer phase-shift phase D2：
    <mrow> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>=</mo> <mfrac> <mn>1</mn> <mn>2</mn> </mfrac> <mo>-</mo> <msqrt> <mrow> <mfrac> <mn>1</mn> <mn>4</mn> </mfrac> <mo>-</mo> <mfrac> <mrow> <mn>8</mn> <msub> <mi>fLi</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>+</mo> <mn>2</mn> <msubsup> <mi>D</mi> <mn>1</mn> <mn>2</mn> </msubsup> <msub> <mi>U</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>+</mo> <mn>8</mn> <msup> <mi>f</mi> <mn>2</mn> </msup> <msub> <mi>LC</mi> <mn>2</mn> </msub> <mo>&amp;lsqb;</mo> <msubsup> <mi>U</mi> <mi>o</mi> <mo>*</mo> </msubsup> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>-</mo> <msub> <mi>U</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>+</mo> <msub> <mi>&amp;Delta;U</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>&amp;rsqb;</mo> </mrow> <mrow> <mn>4</mn> <msub> <mi>U</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> </mrow> </mfrac> </mrow> </msqrt> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <mn>0.5</mn> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <mn>1</mn> </mrow>
    <mrow> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>=</mo> <mn>1</mn> <mo>-</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>-</mo> <msqrt> <mfrac> <mrow> <msup> <mrow> <mo>(</mo> <mn>1</mn> <mo>-</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>)</mo> </mrow> <mn>2</mn> </msup> <msub> <mi>U</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>-</mo> <mn>4</mn> <msub> <mi>fLi</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>-</mo> <mn>4</mn> <msup> <mi>f</mi> <mn>2</mn> </msup> <msub> <mi>LC</mi> <mn>2</mn> </msub> <mo>&amp;lsqb;</mo> <msubsup> <mi>U</mi> <mi>o</mi> <mo>*</mo> </msubsup> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>-</mo> <msub> <mi>U</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>+</mo> <msub> <mi>&amp;Delta;U</mi> <mi>o</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> <mo>&amp;rsqb;</mo> </mrow> <mrow> <msub> <mi>U</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> <mo>)</mo> </mrow> </mrow> </mfrac> </msqrt> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <mn>0.5</mn> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>&amp;le;</mo> <mn>1</mn> </mrow>
    Wherein, Δ Uo(tk) it is tkThe output voltage of moment converter passes through the output valve of outer shroud proportional, integral PI controllers.
  2. 2. the double Method of Phase-Shift Controlling of current stress optimization of double active full-bridge DC-DC converters according to claim 1, its It is characterized in that, building the method for the state mean space equation of double active full-bridge DC-DC converter output voltages includes：
    According to the symmetry of H bridges output voltage and inductive current waveform, in half period, the working status of converter is divided into Four-stage；For each working status, the state equation of output voltage is established respectively：
    <mfenced open = "{" close = ""> <mtable> <mtr> <mtd> <mrow> <msub> <mi>C</mi> <mn>2</mn> </msub> <mfrac> <mrow> <msub> <mi>dU</mi> <mi>o</mi> </msub> </mrow> <mrow> <mi>d</mi> <mi>t</mi> </mrow> </mfrac> <mo>=</mo> <mo>-</mo> <msub> <mi>i</mi> <msub> <mi>L</mi> <mn>1</mn> </msub> </msub> <mo>-</mo> <mfrac> <msub> <mi>U</mi> <mi>o</mi> </msub> <mi>R</mi> </mfrac> </mrow> </mtd> <mtd> <mrow> <mi>t</mi> <mo>&amp;Element;</mo> <mo>&amp;lsqb;</mo> <mn>0</mn> <mo>,</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <msub> <mi>T</mi> <mrow> <mi>h</mi> <mi>s</mi> </mrow> </msub> <mo>&amp;rsqb;</mo> </mrow> </mtd> </mtr> <mtr> <mtd> <mrow> <msub> <mi>C</mi> <mn>2</mn> </msub> <mfrac> <mrow> <msub> <mi>dU</mi> <mi>o</mi> </msub> </mrow> <mrow> <mi>d</mi> <mi>t</mi> </mrow> </mfrac> <mo>=</mo> <mo>-</mo> <msub> <mi>i</mi> <msub> <mi>L</mi> <mn>2</mn> </msub> </msub> <mo>-</mo> <mfrac> <msub> <mi>U</mi> <mi>o</mi> </msub> <mi>R</mi> </mfrac> </mrow> </mtd> <mtd> <mrow> <mi>t</mi> <mo>&amp;Element;</mo> <mo>&amp;lsqb;</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <msub> <mi>T</mi> <mrow> <mi>h</mi> <mi>s</mi> </mrow> </msub> <mo>,</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <msub> <mi>T</mi> <mrow> <mi>h</mi> <mi>s</mi> </mrow> </msub> <mo>&amp;rsqb;</mo> </mrow> </mtd> </mtr> <mtr> <mtd> <mrow> <msub> <mi>C</mi> <mn>2</mn> </msub> <mfrac> <mrow> <msub> <mi>dU</mi> <mi>o</mi> </msub> </mrow> <mrow> <mi>d</mi> <mi>t</mi> </mrow> </mfrac> <mo>=</mo> <mo>-</mo> <mfrac> <msub> <mi>U</mi> <mi>o</mi> </msub> <mi>R</mi> </mfrac> </mrow> </mtd> <mtd> <mrow> <mi>t</mi> <mo>&amp;Element;</mo> <mo>&amp;lsqb;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <msub> <mi>T</mi> <mrow> <mi>h</mi> <mi>s</mi> </mrow> </msub> <mo>,</mo> <mrow> <mo>(</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>+</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>)</mo> </mrow> <msub> <mi>T</mi> <mrow> <mi>h</mi> <mi>s</mi> </mrow> </msub> <mo>&amp;rsqb;</mo> </mrow> </mtd> </mtr> <mtr> <mtd> <mrow> <msub> <mi>C</mi> <mn>2</mn> </msub> <mfrac> <mrow> <msub> <mi>dU</mi> <mi>o</mi> </msub> </mrow> <mrow> <mi>d</mi> <mi>t</mi> </mrow> </mfrac> <mo>=</mo> <mo>-</mo> <msub> <mi>i</mi> <msub> <mi>L</mi> <mn>4</mn> </msub> </msub> <mo>-</mo> <mfrac> <msub> <mi>U</mi> <mi>o</mi> </msub> <mi>R</mi> </mfrac> </mrow> </mtd> <mtd> <mrow> <mi>t</mi> <mo>&amp;Element;</mo> <mo>&amp;lsqb;</mo> <mrow> <mo>(</mo> <msub> <mi>D</mi> <mn>1</mn> </msub> <mo>+</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>)</mo> </mrow> <msub> <mi>T</mi> <mrow> <mi>h</mi> <mi>s</mi> </mrow> </msub> <mo>,</mo> <msub> <mi>T</mi> <mrow> <mi>h</mi> <mi>s</mi> </mrow> </msub> <mo>&amp;rsqb;</mo> </mrow> </mtd> </mtr> </mtable> </mfenced>
    <mfenced open = "{" close = ""> <mtable> <mtr> <mtd> <mrow> <msub> <mi>i</mi> <msub> <mi>L</mi> <mn>1</mn> </msub> </msub> <mo>=</mo> <mfrac> <mrow> <msub> <mi>i</mi> <mi>L</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mn>0</mn> </msub> <mo>)</mo> </mrow> <mo>+</mo> <msub> <mi>i</mi> <mi>L</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mn>1</mn> </msub> <mo>)</mo> </mrow> </mrow> <mn>2</mn> </mfrac> </mrow> </mtd> </mtr> <mtr> <mtd> <mrow> <msub> <mi>i</mi> <msub> <mi>L</mi> <mn>2</mn> </msub> </msub> <mo>=</mo> <mfrac> <mrow> <msub> <mi>i</mi> <mi>L</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mn>1</mn> </msub> <mo>)</mo> </mrow> <mo>+</mo> <msub> <mi>i</mi> <mi>L</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mn>2</mn> </msub> <mo>)</mo> </mrow> </mrow> <mn>2</mn> </mfrac> </mrow> </mtd> </mtr> <mtr> <mtd> <mrow> <msub> <mi>i</mi> <msub> <mi>L</mi> <mn>3</mn> </msub> </msub> <mo>=</mo> <mfrac> <mrow> <msub> <mi>i</mi> <mi>L</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mn>2</mn> </msub> <mo>)</mo> </mrow> <mo>+</mo> <msub> <mi>i</mi> <mi>L</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mn>3</mn> </msub> <mo>)</mo> </mrow> </mrow> <mn>2</mn> </mfrac> </mrow> </mtd> </mtr> <mtr> <mtd> <mrow> <msub> <mi>i</mi> <msub> <mi>L</mi> <mn>4</mn> </msub> </msub> <mo>=</mo> <mfrac> <mrow> <msub> <mi>i</mi> <mi>L</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mn>3</mn> </msub> <mo>)</mo> </mrow> <mo>+</mo> <msub> <mi>i</mi> <mi>L</mi> </msub> <mrow> <mo>(</mo> <msub> <mi>t</mi> <mn>4</mn> </msub> <mo>)</mo> </mrow> </mrow> <mn>2</mn> </mfrac> </mrow> </mtd> </mtr> </mtable> </mfenced>
    Wherein, iL1,iL2,iL3,iL4The average value of inductive current in each stage, T are represented respectivelyhsFor the half of switch periods；Root According to output voltage in the state equation of four-stage, according to equivalent time average principle, the state for building the output voltage is put down Equal space equation.
  3. 3. the double Method of Phase-Shift Controlling of current stress optimization of double active full-bridge DC-DC converters according to claim 1,
    It is characterized in that：The method for obtaining the prediction output voltage of double active full-bridge DC-DC converter is：Before Euler Discrete processes are carried out to the differential term of output voltage in the state mean space equation of converter output voltage to method, are converted Prediction output voltage of the device in next controlling cycle.
  4. 4. the double Method of Phase-Shift Controlling of current stress optimization of double active full-bridge DC-DC converters according to claim 1,
    It is characterized in that, obtain the converter optimizes the outer phase-shift phase D under dual phase shift predictive control strategy in current stress2 Method be：
    With square structure object function of the difference of double active full-bridge DC-DC converter output voltages and reference voltage, and to target Function derivation, it is zero to obtain outer phase-shift phase to make its derivative, and the outer phase-shift phase is compensated, and obtains double active full-bridge DC-DC The outer phase-shift phase D of converter2：
    <mrow> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>=</mo> <mfrac> <mn>1</mn> <mn>2</mn> </mfrac> <mo>-</mo> <msqrt> <mrow> <mfrac> <mn>1</mn> <mn>4</mn> </mfrac> <mo>-</mo> <msub> <mi>a</mi> <mn>1</mn> </msub> </mrow> </msqrt> <mo>,</mo> <mn>0</mn> <mo>&amp;le;</mo> <msub> <mi>D</mi> <mn>2</mn> </msub> <mo>&amp;le;</mo> <mn>0.5</mn> </mrow>
    Wherein,a1For intermediate variable.
  5. 5. the double Method of Phase-Shift Controlling of current stress optimization of double active full-bridge DC-DC converter according to claim 1 its It is characterized in that, the Lagrangian is defined as：
    E=Imax+λ(p-p*)
    Wherein, E represents Lagrangian, and λ is Lagrange multiplier, p*For the given power of converter, ImaxFor converter Current stress perunit value.
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