CN107800300B - Multiphase interleaved bidirectional DC converter - Google Patents

Multiphase interleaved bidirectional DC converter Download PDF

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CN107800300B
CN107800300B CN201710880759.7A CN201710880759A CN107800300B CN 107800300 B CN107800300 B CN 107800300B CN 201710880759 A CN201710880759 A CN 201710880759A CN 107800300 B CN107800300 B CN 107800300B
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circuit
voltage
converter
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pwm signal
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CN107800300A (en
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钟小芬
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Zhuhai Ga Future Technology Co ltd
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Tpking Technology Shenzhen Co ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Dc-Dc Converters (AREA)

Abstract

A multiphase interleaved bidirectional dc converter comprising: a high pressure side port; a first protection circuit connected to the high voltage side port; a low pressure side port; a second protection circuit connected to the low voltage side port; the BDC converters are connected between the first protection circuit and the second protection circuit in parallel, wherein the two or more BDC converters can control one or more paths to work simultaneously according to loads; by arranging the plurality of paths of BDC converters which are connected in parallel, a circuit is shared in a forward flow voltage reduction working mode and a reverse flow voltage increase working mode, the device has two purposes, the system volume is reduced, the system weight is lightened, and the system cost is reduced. The working voltage range of the high-voltage side and the low-voltage side is wide, and the method is suitable for different application scenes. The phase management technology can turn off one-phase or several-phase bidirectional DC-DC converters, reduce the loss of no-load or light load and improve the light load efficiency of the system.

Description

Multiphase interleaved bidirectional DC converter
Technical Field
The invention belongs to the technical field of direct current conversion, and particularly relates to a multiphase interleaved bidirectional direct current converter.
Background
With the development of science and technology and society, the demand of bidirectional DC-DC converters in electric vehicles, photovoltaic energy storage systems, bidirectional DC UPS (uninterruptible Power Supply), aviation Power systems and other occasions is gradually increasing. A Bi-directional DC-DC converter (BDC) is a typical "dual-purpose" device, a traditional unidirectional DC-DC converter converts one DC voltage into another DC voltage by boosting and stepping down, and only can transmit energy from one direction to another direction, while the bidirectional DC-DC converter is a dual-quadrant operating device, and can realize bidirectional transmission of energy: energy can flow not only from the input to the output, but also from the output back to the input. The application of the bidirectional DC-DC converter can greatly reduce the volume of a system, reduce the weight of the system, reduce the cost of the system, improve the operation reliability of the system and have important market economic value.
A bidirectional DC-DC converter circuit disclosed in patent literature (publication No. CN 104184323a) includes: the left side and the right side of the LLC resonance full bridge are completely symmetrical, and when a battery with the same voltage is connected to the input side and the output side, bidirectional controllable transmission of energy cannot be realized; for an ideal voltage source circuit scheme, it is not a true bidirectional DC-DC converter; therefore, compared with the traditional LLC circuit, the secondary side power devices such as the resonant inductor and the resonant capacitor are added, extra loss is increased, and the efficiency is low.
Disclosure of Invention
The invention aims to provide a multiphase interleaving bidirectional direct current converter, and aims to solve the problems of high extra loss and low efficiency in a traditional bidirectional DC-DC conversion circuit.
A multiphase interleaved bidirectional dc converter comprising:
a high pressure side port;
a first protection circuit connected to the high voltage side port;
a low pressure side port;
a second protection circuit connected to the low voltage side port; and
two or more paths of BDC converters which are connected in parallel between the first protection circuit and the second protection circuit, wherein the two or more paths of BDC converters can control one or more paths of BDC converters to work simultaneously according to loads;
wherein the BDC converter comprises:
the pre-regulation circuit is connected with the first protection circuit and is used for pre-regulating the output and input voltage;
the clamping circuit is connected with the pre-adjusting circuit and is used for providing a zero voltage switching-on condition of a switch tube in the BDC converter and inhibiting voltage spikes;
the inverting/rectifying circuit is connected with the clamping circuit, inverts the direct current into alternating current when in forward voltage reduction work and rectifies the alternating current into the direct current when in reverse voltage increase work;
the primary winding of the isolation transformer is connected with the inversion/rectification circuit and is provided with a resonant inductor; and
and the rectification/inversion circuit is connected between the secondary winding of the isolation transformer and the second protection circuit, rectifies the alternating current into direct current during forward voltage reduction work, and inverts the direct current into the alternating current during reverse voltage increase work.
Further, the inverter/rectifier circuit is a primary side full bridge controlled by a first PWM signal, the rectifier/inverter circuit is a secondary side full bridge controlled by a second PWM signal, and the first PWM signal is different from the second PWM signal.
Further, the second PWM signal is an associated phase shift signal of the first PWM signal, and a modulation phase of the second PWM signal is in a linear relationship with the first PWM signal.
Further, in the second PWM signal, a rising edge of the driving signal of the leading arm of the secondary-side full bridge is synchronized with a rising edge of the first PWM signal, and a falling edge of the driving signal of the lagging arm of the secondary-side full bridge is synchronized with a falling edge of the first PWM signal.
Further, the clamping circuit comprises a first switching tube and a clamping capacitor, and the first switching tube and the clamping capacitor are connected in series between the positive output end and the negative output end of the pre-adjusting circuit.
Further, the switching frequency of the first switching tube is about twice the switching frequency of the primary side full bridge, and the switching frequency of the primary side full bridge is the same as the switching frequency of the secondary side full bridge.
Further, the pre-conditioning circuit is a non-isolated single-phase or multi-phase interleaved voltage conditioning circuit.
Further, the voltage regulating circuit is a buck circuit when the BDC converter operates in a downstream buck mode, and is a boost circuit when the BDC converter operates in a reverse boost mode.
Further, the inversion/rectification circuit is a push-pull circuit or a current doubling circuit, and the rectification/inversion circuit is a full-wave circuit.
Further, the resonant inductance of the isolation transformer is an external inductance or a parasitic inductance.
The converter shares one circuit in a forward-flow voltage reduction working mode and a reverse-flow voltage increase working mode by arranging a plurality of paths of BDC converters which are connected in parallel, so that the converter has two purposes, the system volume is reduced, the system weight is lightened, and the system cost is reduced. The working voltage range of the high-voltage side and the low-voltage side is wide, and the method is suitable for different application scenes. The phase management technology can turn off one-phase or several-phase bidirectional DC-DC converters, reduce the loss of no-load or light load and improve the light load efficiency of the system. The ultra-high power single module design is realized, the high-voltage side and the low-voltage side share a protection circuit and the like, and the cost and the space are saved.
Drawings
Fig. 1 is a schematic structural diagram of a multiphase interleaved bidirectional dc-dc converter according to a preferred embodiment of the present invention;
FIG. 2 is a schematic diagram of a BDC converter in the multiphase interleaved bi-directional DC converter circuit shown in FIG. 1;
FIG. 3 is an exemplary circuit schematic of a BDC converter in the multiphase interleaved bi-directional DC converter circuit shown in FIG. 1;
FIG. 4 is a diagram of the basic driving timing of the driving signals of the switching tubes when the BDC converter shown in FIG. 3 is operating in a forward buck mode;
FIG. 5 is a simulated waveform of voltage current at each node when the BDC converter shown in FIG. 3 is operating in a forward-current buck mode without an active clamp;
FIG. 6 is a simulated waveform of voltage and current at each node after the BDC converter shown in FIG. 3 is operated in a forward-current buck mode with the addition of an active clamp circuit;
FIG. 7 is a zero voltage turn-off simulation waveform of the primary side full bridge of the BDC converter shown in FIG. 3 operating in a reverse boost mode of operation;
FIG. 8 is a comparison of output currents of two phases of interleaved parallel connection and single phase operation low voltage side in forward voltage reduction mode of the multiphase interleaved bidirectional DC converter shown in FIG. 1;
fig. 9 is a comparison of output currents of the high-voltage side of the single-phase operation and the two-phase parallel connection in the reverse-current boost mode of the multiphase interleaved bidirectional dc converter shown in fig. 1.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.
Referring to fig. 1, the multiphase interleaved bidirectional dc converter in the preferred embodiment of the present invention includes: a high-pressure side port 20, a first protection circuit 30 connected to the high-pressure side port 20, a low-pressure side port 50, and a second protection circuit 40 connected to the low-pressure side port 50; and two or more than two paths (phases) of BDC converters 10, wherein the two or more than two paths of BDC converters 10 are connected in parallel between the first protection circuit 30 and the second protection circuit 40, and can control one or more than two paths to work simultaneously according to the load. The first protection circuit 30 includes at least one of a high-voltage side EMI filter circuit, a surge suppression circuit, and a polarity protection circuit, and the second protection circuit 40 includes at least one of a low-voltage side EMI filter circuit, a surge suppression circuit, and a reverse connection protection circuit. With phase management techniques, one or more phase BDC converters 10 can be turned off under different load conditions, thereby reducing power losses and increasing system efficiency. In the case where the one-phase BDC converter 10 operates, the lowest standby power consumption and no-load loss are achieved.
Referring to fig. 2, each BDC converter 10 includes: a pre-conditioning circuit 101, a clamping circuit 102, an inverter/rectifier circuit 103, an isolation transformer 104, and a rectifier/inverter circuit 105.
The pre-regulation circuit 101 is connected with the first protection circuit 30 and is used for pre-regulating the output and input voltage; a clamp circuit 102 is connected to the preconditioning circuit for providing a zero voltage turn-on condition of the switching tubes in the BDC converter 10 and suppressing voltage spikes; the inversion/rectification circuit 103 is connected with the clamping circuit 102, the inversion/rectification circuit 103 inverts the direct current into the alternating current when the BDC converter 10 works in a forward flow voltage reduction mode, and the inversion/rectification circuit 103 rectifies the alternating current into the direct current when the BDC converter 10 works in a reverse flow voltage increase mode; the primary winding of the isolation transformer 104 is connected with the inversion/rectification circuit 103 and has a resonant inductor Lr; the rectifying/inverting circuit 105 is connected between the secondary winding of the isolation transformer 104 and the second protection circuit 40, the rectifying/inverting circuit 105 rectifies the alternating current into the direct current when the BDC converter 10 operates in a forward voltage reduction mode, and the rectifying/inverting circuit 105 inverts the direct current into the alternating current when the BDC converter 10 operates in a reverse voltage increase mode. In the BDC converter 10, the inverter/rectifier circuit 103 and the rectifier/inverter circuit 105 achieve ripple cancellation through phase shift control techniques of different phases, and reduce ripple current on a low-voltage side or a high-voltage side, thereby reducing the size of the filter, reducing the current stress of the filter capacitor, and prolonging the service life of the filter capacitor. And the design of an ultra-large power single module is realized by connecting multiphase BDC in parallel in a staggered manner.
Specifically, the preconditioning circuit 101 is a non-isolated single phase or multi-phase interleaved voltage regulation circuit. The voltage regulator circuit is a buck circuit when the BDC converter 10 operates in forward buck mode, and is a boost circuit when the BDC converter 10 operates in reverse boost mode. For example, the voltage regulating circuit is a Buck-Boost circuit. The clamp circuit 102 may be implemented by an N-channel MOSFET top clamp, a P-channel MOSFET bottom clamp, or any other type of clamp circuit. The inverter/rectifier circuit 103 may be a full bridge circuit or a push-pull circuit. In order to cooperate with different inversion/rectification circuits, the primary side of the isolation converter 104 may be a single-turn or a center tap, and the secondary side may be a single-turn or a center tap. The resonant inductance (leakage inductance) Lr of the transformer can be realized by an external inductance or a parasitic inductance of the transformer, and the inductance can be connected in series with the primary side of the transformer or the secondary side of the transformer. The inverter/rectifier circuit 105 may be a full-bridge circuit or a full-wave circuit.
Referring to fig. 3, in a preferred embodiment of the BDC converter 10, the clamp circuit 102 is formed by an upper clamp circuit of active clamp, the inverter/rectifier circuit 103 is formed by a primary side full bridge, the isolation transformer 104 is formed by a high frequency isolation transformer, and the rectifier/inverter circuit is formed by a secondary side full bridge. The inverting/rectifying circuit 103 and the rectifying/inverting circuit 105 have dual functions, when the BDC converter 10 works in a downstream voltage reduction state, the pre-adjusting circuit 101 is composed of a synchronous rectifying Buck voltage reduction circuit, the inverting/rectifying circuit 103 realizes an inverting function of converting direct current into high-frequency alternating current, and the rectifying/inverting circuit 105 realizes a rectifying function of converting high-frequency alternating current into direct current; in addition, when the BDC converter 10 operates in the reverse-current step-up state, the rectifying/inverting circuit 105 realizes an inverting function of converting dc to high-frequency ac, while the inverting/rectifying circuit 103 realizes a rectifying function of converting high-frequency ac to dc. In this case, the pre-regulator circuit 101 is a Boost booster circuit.
Referring to fig. 3 and 4, the basic driving timing of each switching tube when the BDC converter 10 is operating in the forward buck mode is further illustrated.
The pre-conditioning circuit 101 has an upper-tube driving signal Vgs _ S1 and a lower-tube driving signal Vgs _ S2. The Buck circuit adopts a PWM modulation control mode, the switching frequency of the Buck circuit is preset to be Fs, the duty ratio of S1 is DBKAnd S2 duty cycle of 1-DBKAnd an appropriate dead time is maintained with S1. The voltage pre-conditioning circuit 101 may be replaced by a multi-phase interleaved Buck circuit in other embodiments.
The clamp circuit 102 is an active clamp circuit, and includes a switch tube S3 and a clamp capacitor C2, and a switch tube S3 and a clamp capacitor C2 are connected in series between the positive and negative output terminals of the pre-regulator circuit 101. Taking the upper clamp circuit of the N-channel MOSFET as an example, the switching frequency of the driving signal is Fs as shown in Vgs _ S3, and a proper dead time is maintained between the driving signal and the driving signal of the primary side full bridge (inverter/rectifier circuit), and the clamp switching tube is maintained in a closed state during the overlapping time of the driving signal of the primary side full bridge.
Driving signals (first PWM signals) of four switching tubes (taking N-channel MOSFET as an example) in the inverter/rectifier circuit 103 are Vgs _ S4, Vgs _ S5, Vgs _ S6 and Vgs _ S7 respectively, a PWM modulation control mode is adopted, the switching frequency of the switching tubes is 0.5Fs, and the four switching tubes have the same duty ratio DFB，0.5<DFB<1, the side arm switch tubes S4 and S7, S5 and S6 are synchronously switched, the upper and lower tubes S4 and S5, and S6 and S7 on the same side work in a 180-degree phase-staggered mode, the rising edges of the driving signals Vgs _ S4, Vgs _ S5, Vgs _ S6 and Vgs _ S7 are in a synchronous relation with the rising edge of the tube driving signal Vgs _ S1 on the pre-regulation circuit 101, and the falling edge of the tube driving signal Vgs _ S1 is regulated by the PWM signal.
The driving signals (second PWM signals) of the four switching tubes in the rectifying/inverting circuit 105 are Vgs _ S8, Vgs _ S9, Vgs _ S10 and Vgs _ S11, respectively, a phase-shift modulation control mode is adopted, the switching frequency is 0.5Fs, the duty ratio is fixed to be slightly less than 50%, and appropriate dead time is maintained between the upper and lower tubes. Thus, the modulation phase of the second PWM signal has a linear relationship with the first PWM signal. It can be seen that the switching frequency of the switching tube S3 is about twice the switching frequency of the primary full bridge, and the switching frequency of the primary full bridge is the same as the switching frequency of the secondary full bridge. More specifically, the switching tubes S8 and S9 are leading arms, the switching tubes S10 and S11 are lagging arms, the leading arm driving signal has a rising edge in synchronization with the rising edge of the driving signal (first PWM signal) of the inverter/rectifier circuit 103, and the lagging arm driving signal has a falling edge in synchronization with the falling edge of the first PWM signal.
The logical relationship between the individual functional unit drive control signals is detailed above.
Suppose the high side voltage is VHVThe low-voltage side voltage is VLVThe turn ratio of the transformer is N:1, the influence of the conduction voltage drop of each switching tube and the resonance inductance Lr is neglected, and the steady-state relation between the voltage at the high-voltage side and the voltage at the low-voltage side can be deduced according to the voltage volt-second balance relation at the two ends of the inductance L1, and the process is as follows:
Figure GDA0001553122120000071
the method can be obtained after simplification and finishing:
Figure GDA0001553122120000072
since, the above equation shows that the present embodiment circuit can operate in Buck control mode, with duty ratio DBKDirect control; can also work in a full-bridge boost control mode, with a duty ratio DFBDirect control; or DBKAnd DFBAnd the combined control is carried out, so that the working voltage range of the high-voltage side or the low-voltage side is widened.
The following description is made in conjunction with the simulation waveform. In fig. 5-7, Vgs is the driving signal of the switch S5 of the full-bridge in fig. 3, Vds is the DS voltage waveform of the switch S5 of the full-bridge in fig. 3, IL1 is the current waveform of the inductor L1 in fig. 3, Id is the drain current waveform of the switch S5 of the full-bridge in fig. 3, and ILr is the current waveform of the resonant inductor Lr in fig. 3.
Assume the duty cycle D of the Buck circuit (preconditioning circuit 101)BK1, the circuit is defined by a duty cycle DFBDirect control, DFB0.75. Fig. 5 shows voltage and current waveforms of nodes when the active clamp circuit 102 is not added in the downstream step-down mode, where Vds is a DS voltage waveform of the MOSFET S5 in the primary full bridge (the inverter/rectifier circuit 103), and it can be seen that the resonant inductor Lr causes a very high Vds voltage peak of the primary full bridge, and meanwhile, the full bridge Vds waveform has high frequency ringing, which will also have adverse effects on EMI (Electromagnetic Interference).
In contrast, fig. 6 shows a simulated voltage-current waveform at each node after the active clamp circuit 102 is added. It can be seen that the Vds voltage peak of the primary side full bridge is effectively suppressed, and meanwhile, the high-frequency ringing phenomenon of the Vds disappears, so that the EMI characteristic of the circuit is improved. Meanwhile, after the active clamp circuit 102 is added, the clamp capacitor C2 absorbs the excess energy of the resonant inductor Lr in the first half of the time when the full bridge Vds is high, and then releases the excess energy again in the second half of the time when the full bridge Vds is high, which is the resonant process of the resonant inductor Lr and the clamp capacitor C2. It can be seen from the simulation waveform that, at the time when the full-bridge Vds level is going to be low, the current of the resonant inductor Lr is equal to the current of the inductor L1 plus the current of the clamp capacitor C2, at this time, the clamp Switch tube S3 is turned off in advance, which causes the current of the clamp capacitor C2 to be rapidly reduced to 0, so that the current of the resonant inductor Lr is greater than the current of the inductor L1, the resonant inductor Lr resonates with the junction capacitor Coss of the primary full-bridge, the Vds Voltage is rapidly reduced, and before the Vgs of the middle MOSFET S5 of the primary full-bridge is turned on, the Vds has been reduced to 0, thereby implementing ZVS (Zero Voltage Switch) soft switching.
The active clamp circuit can also effectively suppress the voltage spike of the primary side full bridge Vds in a reverse current boosting working mode, and details are not repeated here.
In a more specific embodiment, compared with the ordinary secondary full-bridge circuit, the inverting/rectifying circuit 103 unit of the primary full-bridge has the time overlap of the upper and lower tube duty cycles rather than the dead zone control. The primary side full bridge can reduce the loss of a switching tube in a soft switching mode of zero voltage conduction in a downstream voltage reduction working mode, and can also reduce the switching loss in a soft switching mode of zero voltage turn-off in a reverse voltage boosting working mode, and fig. 7 is a simulation waveform about zero voltage turn-off of the primary side full bridge in the reverse voltage boosting working mode.
The rectifying/inverting circuit 105 is a secondary side full bridge circuit, and adopts a phase shift control mode associated with a PWM signal of a primary side full bridge of the inverting/rectifying circuit 103, so that a Zero voltage switching-on condition of ZVS can be realized in a forward voltage reduction operating mode, and a soft switching condition of Zero voltage switching-Zero Current switching-off of a super-front arm ZVS-hysteresis arm ZCS (Zero Current Switch) can also be realized in a reverse voltage boosting operating mode due to a resonance effect of a resonant inductor Lr and a switching tube Coss, thereby further reducing switching loss, improving the efficiency of a system, and reducing the temperature rise of the system.
The above description details the circuit structure of the one-way BDC converter 10 and the operation principle and operation process of each circuit unit thereof. Through the organic cascade of the two-stage circuit sharing the buck-boost inductor, the organic combination of a downstream buck mode and a reverse boost mode is realized, the wide working voltage range is suitable for different use scenes, the reduction of circuit loss of soft switches such as ZVS (zero voltage switching) is realized, and the efficiency is improved.
Furthermore, according to the scheme, the multiphase BDC converters 10 are connected in parallel in a staggered mode, one or more phases of the BDC converters 10 can be turned off by utilizing a phase management technology, the no-load or light-load loss is reduced, and the light-load efficiency of the system is improved. The staggered phase-shift control technology realizes different phase-shift control, reduces ripple current on a high-voltage side or a low-voltage side, reduces a filter, and prolongs the service life of a filter capacitor. The ultra-high power single module design is realized, the high-voltage side and the low-voltage side share an EMI filter circuit, a polarity protection circuit, a surge suppression circuit, a reverse connection protection circuit and the like, and the cost and the space are saved.
The following illustrates the effect of interleaving of the multi-phase BDC converter 10 on the high side or low side output current ripple. On the basis of the simulation circuit, a path of BDC converter 10 lines with the same configuration is added to be connected in parallel in a staggered mode, and simulation analysis is carried out by taking the example of phase deviation of 90 degrees. FIG. 8 is a comparison of low side output current for single phase operation and two phase interleaving in forward buck mode. FIG. 9 is a comparison of the high-side output current for the case of two-phase interleaving and single-phase operation in the reverse boost mode. It can be seen that, after the multiphase BDC converters 10 are connected in parallel in a staggered manner, the ripple amplitude of the output current is reduced and the frequency is doubled no matter on the high-voltage side or the low-voltage side, so that the filter size on the high-voltage side and the filter size on the low-voltage side are reduced, the weight of the system is reduced, and the service life of the filter capacitor is prolonged.
According to the scheme, the multiphase BDC converters 10 are connected in parallel in a staggered mode, one-phase or multi-phase bidirectional DC-DC converters can be turned off by utilizing a phase management technology, no-load or light-load loss is reduced, and light-load efficiency of the system is improved. The staggered phase-shift control technology realizes different phase-shift control, reduces ripple current on a high-voltage side or a low-voltage side, reduces a filter, and prolongs the service life of a filter capacitor. The ultra-high power single module design is realized, the high-voltage side and the low-voltage side share an EMI filter circuit, a polarity protection circuit, a surge suppression circuit, a reverse connection protection circuit and the like, and the cost and the space are saved.
The solution can be widely applied to the fields of electric vehicles, photovoltaic energy storage systems, uninterrupted bidirectional UPS, aviation power supplies and the like, and has immeasurable market economic value.
The converter shares one circuit in a forward-flow voltage reduction working mode and a reverse-flow voltage increase working mode by arranging the plurality of paths of BDC converters 10 connected in parallel, so that the converter has two purposes, the system volume is reduced, the system weight is lightened, and the system cost is reduced. The working voltage range of the high-voltage side and the low-voltage side is wide, and the method is suitable for different application scenes. The phase management technology can turn off one-phase or several-phase bidirectional DC-DC converters, reduce the loss of no-load or light load and improve the light load efficiency of the system. The ultra-high power single module design is realized, the high-voltage side and the low-voltage side share a protection circuit and the like, and the cost and the space are saved.
The above description is only for the purpose of illustrating the preferred embodiments of the present invention and is not to be construed as limiting the invention, and any modifications, equivalents and improvements made within the spirit and principle of the present invention are intended to be included within the scope of the present invention.

Claims (8)

1. A multiphase interleaved bi-directional dc converter comprising:
a high pressure side port;
a first protection circuit connected to the high voltage side port;
a low pressure side port;
a second protection circuit connected to the low voltage side port; and
two or more paths of BDC converters which are connected in parallel between the first protection circuit and the second protection circuit, wherein the two or more paths of BDC converters control one or more paths of BDC converters to work simultaneously according to loads;
wherein the BDC converter comprises:
the pre-regulation circuit is connected with the first protection circuit and is used for pre-regulating the output and input voltage;
the clamping circuit is connected with the pre-adjusting circuit and is used for providing a zero voltage switching-on condition of a switch tube in the BDC converter and inhibiting voltage spikes;
the inverting/rectifying circuit is connected with the clamping circuit, inverts the direct current into alternating current when in forward voltage reduction work and rectifies the alternating current into the direct current when in reverse voltage increase work;
the primary winding of the isolation transformer is connected with the inversion/rectification circuit and is provided with a resonant inductor; and
the rectifier/inverter circuit is connected between the secondary winding of the isolation transformer and the second protection circuit, rectifies alternating current into direct current during forward voltage reduction work, and inverts the direct current into alternating current during reverse voltage increase work;
the inversion/rectification circuit is a primary side full bridge controlled by a first PWM signal, the rectification/inversion circuit is a secondary side full bridge controlled by a second PWM signal, and the first PWM signal is different from the second PWM signal;
the second PWM signal is a correlated phase-shifting signal of the first PWM signal, and the modulation phase of the second PWM signal is in a linear relation with the first PWM signal;
high side voltage VHVAnd a low-side voltage VLVThe steady-state relationship between the two is as follows:
Figure FDA0002969189830000021
when the Buck is operated in a Buck voltage reduction control mode, the duty ratio DBKDirect control; when the converter is operated in a full-bridge boost control mode, the duty ratio DFBDirect control, or DBKAnd DFBCombined control, wherein DFBIs the duty cycle of the first PWM signal, DBKIn order to drive the duty ratio of the PWM signal of the pre-adjusting circuit, the turn ratio of an isolation transformer is N: 1.
2. the multiphase interleaved bi-directional dc converter as set forth in claim 1, wherein in said second PWM signal, the leading edge of the drive signal of the leading arm of said secondary side full bridge is synchronized with the leading edge of said first PWM signal, and the trailing edge of the drive signal of the lagging arm of said secondary side full bridge is synchronized with the trailing edge of said first PWM signal.
3. The multiphase interleaved bidirectional dc converter as set forth in claim 1, wherein said clamping circuit comprises a first switching tube and a clamping capacitor, said first switching tube and said clamping capacitor being connected in series between positive and negative output terminals of said preconditioning circuit.
4. The multiphase interleaved bidirectional dc converter as set forth in claim 3, wherein said first switching transistor has a switching frequency twice that of said primary full bridge, and wherein said primary full bridge and said secondary full bridge have the same switching frequency.
5. The multiphase interleaved bi-directional dc converter as recited in claim 1 wherein said pre-conditioning circuit is a non-isolated single phase or multiphase interleaved voltage conditioning circuit.
6. The multiphase interleaved bidirectional dc converter as set forth in claim 5 wherein said voltage regulation circuit is a buck circuit when said BDC converter is operating in buck mode and a boost circuit when said BDC converter is operating in boost mode.
7. The multiphase interleaved bidirectional dc converter according to claim 1 wherein said inverter/rectifier circuit is a push-pull circuit or a current doubler circuit and said rectifier/inverter circuit is a full wave circuit.
8. The multiphase interleaved bi-directional dc converter according to claim 1 wherein the resonant inductance of the isolation transformer is an external inductance or a parasitic inductance.
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