CN107800300A - Multiphase staggered bi-directional DC converter - Google Patents
Multiphase staggered bi-directional DC converter Download PDFInfo
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- CN107800300A CN107800300A CN201710880759.7A CN201710880759A CN107800300A CN 107800300 A CN107800300 A CN 107800300A CN 201710880759 A CN201710880759 A CN 201710880759A CN 107800300 A CN107800300 A CN 107800300A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
A kind of multiphase staggered bi-directional DC converter, including：High pressure side ports；The first protection circuit being connected with the high pressure side ports；Low pressure side ports；The second protection circuit being connected with the low pressure side ports；And two-way or more, the BDC converters being connected in parallel between first protection circuit and second protection circuit, wherein, two-way or more BDC converters can according to load control wherein one or more work simultaneously；By setting the BDC converters of multi-channel parallel, it is depressured mode of operation in following current and adverse current boost operating mode shares a circuit, dual-use, reduce system bulk, alleviate system weight, reduce system cost.The operating voltage range of high-pressure side and low-pressure side is wide, suitable for different application scenarios.Phase administrative skill can turn off a phase or several mutually two-way DC DC converters, reduce unloaded or underloading loss, improve the light-load efficiency of system.
Description
Technical field
The invention belongs to DC converting technical field, more particularly to a kind of multiphase staggered bi-directional DC converter.
Background technology
With the development of science and technology and society, electric automobile, photovoltaic energy storage system, bidirectional, dc UPS (Uninterruped
Power Supply, uninterrupted power source), the occasion such as aviation power system is to the need of bi-directional DC-DC (direct current inversion of direct current) converter
Ask gradual increase.Bi-directional DC-DC (Bi-directional DC-DC Converter, BDC) converter is a kind of typical " one
Machine is dual-purpose " equipment, traditional Uniderectional DC-DC converter is unidirectionally converted to a kind of DC voltage by the mode such as boosting, being depressured
Another DC voltage, energy can only be transferred to another direction from a direction, and bidirectional DC-DC converter is a kind of double
Quadrant operational outfit, the transmitted in both directions of energy can be realized：Energy not only can flow to output end from input, can also be from defeated
Go out end and flow back to input.The application of bidirectional DC-DC converter can significantly reduce the volume of system, mitigate system weight and drop
Low system cost, system operation reliability is improved, there is important market economy to be worth.
At present, a kind of (publication number CN 104184323A) disclosed in patent document bidirectional DC-DC converter circuit is present：LLC
Resonant full bridge the right and left is full symmetric, when the battery of input side voltage same with output side joint, can not realize the double of energy
To controllable transmission；It is not bidirectional DC-DC converter truly for ideal voltage source circuit arrangement；Therefore, on the contrary
Than the resonant inductance and resonant capacitance constant power device that traditional LLC circuits add secondary, extra loss, efficiency are added
It is low.
The content of the invention
It is an object of the invention to provide a kind of multiphase staggered bi-directional DC converter, it is intended to solves traditional two-way DC-
Present in DC translation circuits compared with great number outside loss, the problem of efficiency is low.
A kind of multiphase staggered bi-directional DC converter, including：
High pressure side ports；
The first protection circuit being connected with the high pressure side ports；
Low pressure side ports；
The second protection circuit being connected with the low pressure side ports；And
Two-way or more, the BDC converters being connected in parallel between first protection circuit and second protection circuit,
Wherein, the BDC converters of two-way or more can according to load control wherein one or more work simultaneously；
Wherein, the BDC converters include：
Pre-regulating circuit, it is connected with first protection circuit, for being preconditioned to output-input voltage；
Clamp circuit, it is connected with the pre-regulating circuit, the no-voltage for providing switching tube in the BDC converters is opened
Gating condition, and suppress due to voltage spikes；
Inversion/rectification circuit, it is connected with the clamp circuit, inverse of the DC into AC when following current is depressured work,
By AC rectification into direct current during adverse current boosting work；
Isolating transformer, primary side winding are connected with the inversion/rectification circuit, have resonant inductance；And
Rectification/inverter circuit, it is connected between the vice-side winding of the isolating transformer and second protection circuit, it is suitable
By AC rectification into direct current during stream decompression work, adverse current boost work when inverse of the DC into AC.
Further, the inversion/rectification circuit is using the primary side full-bridge of the first pwm signal control, the rectification/inverse
The secondary full-bridge for becoming circuit to control using the second pwm signal, first pwm signal are different from second pwm signal.
Further, second pwm signal is the association phase shift signal of first pwm signal, the 2nd PWM letters
Number phase modulation and first pwm signal between it is linear.
Further, in second pwm signal, the drive signal rising edge of the advanced arm of the secondary full-bridge and institute
State the rising edge synch of the first pwm signal, the trailing edge of the drive signal of the lagging leg of the secondary full-bridge and the first PWM
The trailing edge of signal is synchronous.
Further, the clamp circuit includes first switch pipe and clamp capacitor, the first switch pipe and the pincers
Position capacitance series are between the positive-negative output end of the pre-regulating circuit.
Further, the switching frequency of the first switch pipe is about twice of the switching frequency of the primary side full-bridge, institute
The switching frequency for stating primary side full-bridge is identical with the switching frequency of the secondary full-bridge.
Further, the pre-regulating circuit is non-isolated single-phase or how staggered voltage regulator circuit.
Further, the voltage regulator circuit is reduction voltage circuit when the BDC converters following current is depressured work, in institute
State BDC converters adverse current boosting work when be booster circuit.
Further, the inversion/rectification circuit is push-pull circuit or current circuit again, and the rectification/inverter circuit is complete
Wave circuit.
Further, the resonant inductance of isolating transformer is external inductors or stray inductance.
Above-mentioned converter is boosted by setting the BDC converters of multi-channel parallel in following current decompression mode of operation and adverse current
Mode of operation shares a circuit, dual-use, reduces system bulk, alleviates system weight, reduces system cost.It is high
Press the operating voltage range of side and low-pressure side wide, suitable for different application scenarios.Phase administrative skill can turn off a phase or
A few phase bidirectional DC-DC converters, unloaded or underloading loss is reduced, improve the light-load efficiency of system.Realize super high power
Single module design, high-pressure side and low-pressure side share protection circuit etc., cost-effective and space.
Brief description of the drawings
Fig. 1 is the structural representation for the multiphase staggered bi-directional DC converter that present pre-ferred embodiments provide；
Fig. 2 be Fig. 1 shown in multiphase staggered bi-directional DC converter in BDC converters structural representation；
Fig. 3 be Fig. 1 shown in multiphase staggered bi-directional DC converter in BDC converters exemplary circuit schematic diagram；
Fig. 4 is that the drive signal of each switching tube when the BDC converters shown in Fig. 3 are operated in following current decompression mode drives substantially
Dynamic timing diagram；
Fig. 5 is that the BDC converters shown in Fig. 3 are operated under following current decompression mode each node electricity when not adding active clamp circuit
Current voltage simulation waveform；
Fig. 6 is that the BDC converters shown in Fig. 3 are operated under following current decompression mode each node electricity after increase active clamp circuit
Current voltage simulation waveform；
The zero voltage turn-off that Fig. 7 is operated in primary side full-bridge under adverse current boost operating mode for the BDC converters shown in Fig. 3 is imitated
True waveform；
Fig. 8 be Fig. 1 shown in multiphase staggered bi-directional DC converter following current decompression mode under two-phase crisscross parallel with it is single-phase
The low-pressure side that works output current contrast；
Fig. 9 be Fig. 1 shown in multiphase staggered bi-directional DC converter adverse current boost mode under two-phase crisscross parallel with it is single-phase
The output current contrast of working voltage side.
Embodiment
In order to make the purpose , technical scheme and advantage of the present invention be clearer, it is right below in conjunction with drawings and Examples
The present invention is further elaborated.It should be appreciated that the specific embodiments described herein are merely illustrative of the present invention, and
It is not used in the restriction present invention.
Referring to Fig. 1, the multiphase staggered bi-directional DC converter in present pre-ferred embodiments includes：High pressure side ports
20th, the first protection circuit 30 for being connected with the high pressure side ports 20, low pressure side ports 50, it is connected with the low pressure side ports 50
The second protection circuit 40；And the BDC converters 10 of two-way (phase) or more, wherein, the BDC conversion of two-way or more
Device 10 is connected in parallel between first protection circuit 30 and second protection circuit 40, can be according to load control wherein one
Road or multichannel work simultaneously.First protection circuit 30 includes high-pressure side EMI filter circuit, surge restraint circuit and polarity protection electricity
At least one in road, the second protection circuit 40 includes low-pressure side EMI filter circuit, surge restraint circuit and reverse-connection protection circuit
In it is at least one.Using phase administrative skill, under different loading conditions, a phase or multiphase BDC converters can be turned off
10, so as to reduce power attenuation, and lifting system efficiency.In the case where a phase BDC converters 10 work, realize minimum
Stand-by power consumption and open circuit loss.
Referring to Fig. 2, each BDC converters 10 include：Pre-regulating circuit 101, clamp circuit 102, inversion/rectification circuit
103rd, isolating transformer 104 and rectification/inverter circuit 105.
Pre-regulating circuit 101 is connected with first protection circuit 30, for being preconditioned to output-input voltage；Pincers
Position circuit 102 is connected with the pre-regulating circuit, and the no-voltage for providing switching tube in the BDC converters 10 opens bar
Part, and suppress due to voltage spikes；Inversion/rectification circuit 103 is connected with clamp circuit 102, the following current of BDC converters 10 decompression work
The inverse of the DC into AC of inversion/rectification circuit 103 when making, BDC converters 10 countercurrently boost work when inversion/rectified current
Road 103 is by AC rectification into direct current；The primary side winding of isolating transformer 104 is connected with the inversion/rectification circuit 103,
With resonant inductance Lr；Rectification/inverter circuit 105 is connected to the vice-side winding of the isolating transformer 104 and described second and protected
Between protection circuit 40, during the following current of BDC converters 10 decompression work rectification/inverter circuit 105 by AC rectification into direct current,
BDC converters 10 countercurrently boost work when the inverse of the DC into AC of rectification/inverter circuit 105.It is inverse in BDC converters 10
Change/rectification circuit 103 and rectification/inverter circuit 105 realize that ripple is offset by the Phase Shift Control Study of out of phase, reduce low
Side or on high-tension side ripple current are pressed, so as to reduce the volume of wave filter, the current stress of filter capacitor is reduced, extends filtering
The service life of electric capacity.By multiphase BDC crisscross parallels, super high power single module design is realized.
Specifically, pre-regulating circuit 101 is non-isolated single-phase or how staggered voltage regulator circuit.Voltage regulator circuit
It is reduction voltage circuit when the following current of BDC converters 10 is depressured work, is liter when the BDC converters 10 countercurrently boost work
Volt circuit.If voltage regulator circuit is Buck-Boost circuits.Clamp circuit 102 can be by using on the MOSFET of N-channel
Clamper mode is realized, can also be realized by using clamper mode under the MOSFET of P-channel, or any pincers using other forms
Position circuit realiration.Inversion/rectification circuit 103 can be full-bridge circuit or push-pull circuit.Isolated converter 104 in order to
Coordinate different inversion/rectification circuits, primary side can be that single turn can also be with centre cap, and secondary can be that single turn can also band
Centre cap.Resonant inductance (leakage inductance) Lr of transformer can be realized with external inductors, can also use the stray inductance of transformer
Realize, inductance can be connected on the primary side of transformer, can also be connected on the secondary of transformer.Inversion/rectification circuit 105 can be with
It is full-bridge circuit, or full-wave circuit.
Referring to Fig. 3, a preferred embodiment of effect BDC converters 10, clamp circuit 102 is by the upper of active clamp
Clamp circuit is formed, and inversion/rectification circuit 103 is made up of primary side full-bridge, and isolating transformer 104 is by high-frequency isolation transformer structure
Into rectification/inverter circuit is made up of secondary full-bridge.Wherein, inversion/rectification circuit 103 and rectification/inverter circuit 105 have double
Weight function, when BDC converters 10 are operated in following current decompression state, pre-regulating circuit 101 is by synchronous rectification Buck reduction voltage circuits
Form, inversion/rectification circuit 103 realizes that direct current turns the inversion function of high-frequency ac, while rectification/inverter circuit 105 realizes height
Frequency exchange turns the rectification function of direct current；In addition, when BDC converters 10 are operated in adverse current pressure-increasning state, rectification/inverter circuit
105 realize that direct current turns the inversion function of high-frequency ac, while inversion/rectification circuit 103 realizes that high-frequency ac turns the rectification of direct current
Function.Moreover, now pre-regulating circuit 101 becomes Boost circuit.
Fig. 3 and Fig. 4 are referred to, further, when being operated in following current decompression state with BDC converters 10, each switching tube
Basic driver sequential illustrate operation principle.
Wherein, the upper tube drive signal of pre-regulating circuit 101 be Vgs_S1, down tube drive signal be Vgs_S2.Buck electricity
Road uses PWM control model, and its switching frequency is preset as Fs, and S1 dutycycles are DBK, S2 dutycycles are 1-DBK, and and S1
Between maintain appropriate dead time.Voltage pre-regulating circuit 101 can also use multiphase interleaving in other embodiments
Buck circuitry insteads.
Clamp circuit 102 is active clamp circuit, including a switching tube S3 and clamp capacitor C2, a switching tube S3 and clamper
Electric capacity C2 is serially connected between the positive-negative output end of the pre-regulating circuit 101.By taking N-channel MOS FET upper clamp circuit as an example
Be illustrated, for drive signal as shown in Vgs_S3, its switching frequency is Fs, and with the drive of primary side full-bridge (inversion/rectification circuit)
Appropriate dead time is maintained between dynamic signal, is overlapped in primary side full-bridge drive signal in the time and keeps clamping switch tube to be in
Closed mode.
(the first PWM believes the drive signal of four switching tubes (by taking N-channel MOS FET as an example) in inversion/rectification circuit 103
Number) it is respectively Vgs_S4, Vgs_S5, Vgs_S6, Vgs_S7, using PWM modulation control patterns, its switching frequency is 0.5Fs,
Four switching tubes have identical dutycycle DFB, 0.5< DFB<1, offside bridge arm switching tube S4 and S7, S5 and S6 synchro switch,
Down tube S4 and S5, S6 and S7 are worked with 180 degree phase cross-over on homonymy, drive signal Vgs_S4, Vgs_S5, Vgs_S6 and
The rising edge holding synchronized relation of Vgs_S7 rising edge and the upper tube drive signal Vgs_S1 of pre-regulating circuit 101, and itself
Pwm signal adjusts its trailing edge.
The drive signal (the second pwm signal) of four switching tubes is respectively Vgs_S8, Vgs_ in rectification/inverter circuit 105
S9, Vgs_S10, Vgs_S11, using phase shift modulation control model, its switching frequency is 0.5Fs, and dutycycle is fixed as being slightly less than
Appropriate dead time is maintained between 50% and upper down tube.In this way, the second pwm signal phase modulation and the first pwm signal
Between it is linear.It can be seen that switching tube S3 switching frequency is about twice of the switching frequency of primary side full-bridge, primary side full-bridge
Switching frequency is identical with the switching frequency of secondary full-bridge.More specifically, switching tube S8, S9 are advanced arms, switching tube S10, S11
It is lagging leg, the rising edge of advanced arm drive signal and the rising of the drive signal of inversion/rectification circuit 103 (the first PWM signals)
Along the trailing edge holding synchronized relation for keeping synchronized relation, the trailing edge of lagging leg drive signal and the first pwm signal.
Logical relation between each functional unit driving control signal described in detail above.
Assuming that high side voltage is VHV, low-pressure side voltage VLV, transformer turns ratio N:1, ignore leading for each switching tube
Flow voltage drop, and resonant inductance Lr influence, according to the voltage voltage-second balance relation at inductance L1 both ends, high-pressure side can be derived
Steady state relation between voltage and low-pressure side voltage, process are as follows：
Abbreviation can obtain after arranging：
Because above-mentioned equation illustrates that this specific implementation circuit can be operated in Buck decompression control models, by dutycycle DBK
Directly control；Full-bridge boost control model can also be operated in, by dutycycle DFBDirectly control；Or DBKWith DFBJointly control,
So as to widen the operating voltage range of high-pressure side or low-pressure side.
It is illustrated below in conjunction with simulation waveform.In Fig. 5-Fig. 7, Vgs is the drive that the switch S5 of primary side full-bridge in Fig. 3 is
Dynamic signal, Vds are the DS voltage waveforms of the switch S5 of primary side full-bridge in Fig. 3, and IL1 is the current waveform of inductance L1 in Fig. 3, Id
For the switch S5 drain current wavefonns of primary side full-bridge in Fig. 3, ILr is the current waveform of resonant inductance Lr in Fig. 3.
Assuming that the dutycycle D of Buck circuits (pre-regulating circuit 101)BK=1, circuit is by dutycycle DFBDirectly control, DFB=
0.75.Fig. 5 is the voltage current waveform of each node plus during active clamp circuit 102 under following current decompression mode of operation, wherein Vds
It is the DS voltage waveforms of MOSFET S5 in primary side full-bridge (inversion/rectification circuit 103), it can be seen that resonant inductance Lr is caused
The Vds due to voltage spikes of primary side full-bridge is very high, while high frequency ringing occur in full-bridge Vds waveforms, to EMI
(Electromagnetic Interference, electromagnetic interference) will also produce harmful effect.
With this contrast, Fig. 6 is the increase in the voltage x current simulation waveform of each node after active clamp circuit 102.It can see
Go out, the Vds due to voltage spikes of primary side full-bridge has obtained effective suppression, while Vds high frequency ringing phenomenon also disappears, and improves circuit
EMI characteristics.Meanwhile after adding active clamp circuit 102, clamp capacitor C2 is when full-bridge Vds is the front half section of high level
The interior excess energy for absorbing resonant inductance Lr, then discharged again in the latter half that full-bridge Vds is high level
Come, the process is resonant inductance Lr and clamp capacitor C2 resonant process.With reference to simulation waveform as can be seen that in full-bridge Vds electricity
At the time of putting down step-down i.e., resonant inductance Lr electric current of the electric current equal to inductance L1 adds clamp capacitor C2 electric current, now clamps
Bit switch pipe S3 is closed in advance, causes clamp capacitor C2 electric current to be reduced to 0 rapidly, is more than inductance so as to resonant inductance Lr electric current
Resonance occurs for L1 electric current, resonant inductance Lr and primary side full-bridge junction capacity Coss, and Vds voltages decline rapidly, in primary side full-bridge
Middle MOSFET S5 Vgs open before, its Vds has decreased to 0, it is achieved thereby that ZVS (Zero Voltage Switch,
ZVT) Sofe Switch.
The active clamp circuit can be equally realized under adverse current boost operating mode to primary side full-bridge Vds due to voltage spikes
Effectively suppress, will not be repeated here.
In more specifically embodiment, the unit of inversion/rectification circuit 103 of primary side full-bridge and common secondary full-bridge electricity
Road is compared, and down tube dutycycle has temporal overlapping rather than dead zone function thereon.The primary side full-bridge is depressured Working mould in following current
Switching tube loss can be reduced under formula in a manner of the Sofe Switch that no-voltage turns on, also can be with zero under adverse current boost operating mode
The Sofe Switch mode of voltage shut-off reduces switching loss, and Fig. 7 is closed on primary side full-bridge zero-voltage under adverse current boost operating mode
Disconnected simulation waveform.
Rectification/inverter circuit 105 is a secondary full-bridge circuit, using the primary side full-bridge with inversion/rectification circuit 103
The associated phase shifting control pattern of pwm signal, it can realize that ZVS no-voltage opens condition in the case where following current is depressured mode of operation,
Due to resonant inductance Lr and switching tube Coss resonance effect under adverse current boost operating mode, advanced arm can be also realized
ZVS- lagging legs ZCS (Zero Current Switch, Zero Current Switch) no-voltage opens-Sofe Switch of zero-current switching
Condition, so as to reduce further switching loss, the efficiency of system is improved, reduces system temperature rise.
The operation principle of the above-mentioned circuit structure for detailing single channel BDC converters 10 and its each circuit unit and worked
Journey.Organic cascade of lifting voltage inductance is shared by two-stage circuit, realize following current decompression mode and adverse current boost mode has
Machine combines, and realizes wide operating voltage range and is applied to different usage scenarios, and realizing the Sofe Switch such as ZVS reduces circuit damage
Consumption, improves efficiency.
Further, this programme can turn off one by the crisscross parallel of multiphase BDC converters 10 using phase administrative skill
Phase or a few phase BDC converters 10, unloaded or underloading loss is reduced, improve the light-load efficiency of system.Staggeredly phase shifting control
Technology realizes different phase shifting controls, reduces the ripple current of high-pressure side or low-pressure side, reduces wave filter, improves filtering
The life-span of electric capacity.Realize super high power single module design, high-pressure side and low-pressure side share EMI filter circuit, polar protective circuit,
Surge restraint circuit, reverse-connection protection circuit etc., cost-effective and space.
The crisscross parallel of multiphase BDC converters 10 illustrated below is to high-pressure side or the shadow of low-pressure side output current ripple
Ring.On the basis of above-mentioned artificial circuit, the circuit of BDC converters 10 that equally configures all the way crisscross parallel therewith is further added by, with
Simulation analysis are carried out exemplified by 90 degree of phase shifting.Fig. 8 be that following current decompression mode two is staggered and single-phase working condition under, low-pressure side
The contrast of output current.Fig. 9 be that adverse current boost mode two is staggered and single-phase working condition under, pair of high-pressure side output current
Than.As can be seen that after the crisscross parallel of multiphase BDC converters 10, no matter high-pressure side or low-pressure side, the ripple width of its output current
Degree reduces, and frequency is double, and some advantages that arise therefrom is the diminution of high-pressure side and low-pressure side wave filter volume, and system weight subtracts
Gently, the life-span of filter capacitor is improved.
This programme can turn off a phase or a few phases by the crisscross parallel of multiphase BDC converters 10 using phase administrative skill
Bidirectional DC-DC converter, unloaded or underloading loss is reduced, improve the light-load efficiency of system.Staggeredly Phase Shift Control Study
Different phase shifting controls is realized, the ripple current of high-pressure side or low-pressure side is reduced, reduces wave filter, improve filter capacitor
Life-span.Super high power single module design is realized, high-pressure side and low-pressure side share EMI filter circuit, polar protective circuit, surge
Suppression circuit, reverse-connection protection circuit etc., cost-effective and space.
This solution can be widely applied to electric automobile, photovoltaic energy storage system, uninterrupted two-way UPS, airplane power source etc.
All multiple fields, there is immeasurable market economy value.
Above-mentioned converter is risen by setting the BDC converters 10 of multi-channel parallel in following current decompression mode of operation and adverse current
Press mode of operation to share a circuit, dual-use, reduce system bulk, alleviate system weight, reduce system cost.
The operating voltage range of high-pressure side and low-pressure side is wide, suitable for different application scenarios.Phase administrative skill can turn off a phase
Or several phase bidirectional DC-DC converters, unloaded or underloading loss is reduced, improves the light-load efficiency of system.Realize super large work(
Rate single module design, high-pressure side and low-pressure side share protection circuit etc., cost-effective and space.
The foregoing is merely illustrative of the preferred embodiments of the present invention, is not intended to limit the invention, all essences in the present invention
All any modification, equivalent and improvement made within refreshing and principle etc., should be included in the scope of the protection.
Claims (10)
- A kind of 1. multiphase staggered bi-directional DC converter, it is characterised in that including：High pressure side ports；The first protection circuit being connected with the high pressure side ports；Low pressure side ports；The second protection circuit being connected with the low pressure side ports；AndTwo-way or more, the BDC converters being connected in parallel between first protection circuit and second protection circuit, wherein, The BDC converters of two-way or more can according to load control wherein one or more work simultaneously；Wherein, the BDC converters include：Pre-regulating circuit, it is connected with first protection circuit, for being preconditioned to output-input voltage；Clamp circuit, it is connected with the pre-regulating circuit, the no-voltage for providing switching tube in the BDC converters opens bar Part, and suppress due to voltage spikes；Inversion/rectification circuit, it is connected with the clamp circuit, inverse of the DC into AC when following current is depressured work, adverse current Boost work when by AC rectification into direct current；Isolating transformer, primary side winding are connected with the inversion/rectification circuit, have resonant inductance；AndRectification/inverter circuit, it is connected between the vice-side winding of the isolating transformer and second protection circuit, following current drop By AC rectification into direct current when pressing work, adverse current boost work when inverse of the DC into AC.
- 2. multiphase staggered bi-directional DC converter as claimed in claim 1, it is characterised in that the inversion/rectification circuit is The primary side full-bridge controlled using the first pwm signal, the rectification/inverter circuit are complete using the secondary of the second pwm signal control Bridge, first pwm signal are different from second pwm signal.
- 3. multiphase staggered bi-directional DC converter as claimed in claim 2, it is characterised in that second pwm signal is institute The association phase shift signal of the first pwm signal is stated, is between the phase modulation of second pwm signal and first pwm signal Linear relationship.
- 4. multiphase staggered bi-directional DC converter as claimed in claim 2 or claim 3, it is characterised in that in second pwm signal In, the rising edge synch of the drive signal rising edge of the advanced arm of the secondary full-bridge and first pwm signal, the secondary The trailing edge of the drive signal of the lagging leg of full-bridge is synchronous with the trailing edge of first pwm signal.
- 5. multiphase staggered bi-directional DC converter as claimed in claim 2, it is characterised in that the clamp circuit includes first Switching tube and clamp capacitor, the first switch pipe and the clamp capacitor are serially connected in the positive-negative output end of the pre-regulating circuit Between.
- 6. multiphase staggered bi-directional DC converter as claimed in claim 5, it is characterised in that the switch of the first switch pipe Frequency is about twice of the switching frequency of the primary side full-bridge, the switching frequency of the primary side full-bridge and opening for the secondary full-bridge It is identical to close frequency.
- 7. multiphase staggered bi-directional DC converter as claimed in claim 1, it is characterised in that the pre-regulating circuit for it is non-every From single-phase or how staggered voltage regulator circuit.
- 8. multiphase staggered bi-directional DC converter as claimed in claim 7, it is characterised in that the voltage regulator circuit is in institute State the following current of BDC converters decompression work when be reduction voltage circuit, the BDC converters adverse current boost work when be booster circuit.
- 9. multiphase staggered bi-directional DC converter as claimed in claim 1, it is characterised in that the inversion/rectification circuit is Push-pull circuit or again current circuit, the rectification/inverter circuit are full-wave circuit.
- 10. multiphase staggered bi-directional DC converter as claimed in claim 1, it is characterised in that the resonance electricity of isolating transformer Feel for external inductors or stray inductance.
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| CN201710880759.7A CN107800300B (en) | 2017-09-26 | 2017-09-26 | Multiphase interleaved bidirectional DC converter |
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| CN201710880759.7A CN107800300B (en) | 2017-09-26 | 2017-09-26 | Multiphase interleaved bidirectional DC converter |
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| CN114221549A (en) * | 2021-11-30 | 2022-03-22 | 广州金升阳科技有限公司 | Cascade circuit and control method thereof |
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