CN107659527B - Phase noise suppression system and method for simultaneous same-frequency full duplex cooperative communication - Google Patents

Phase noise suppression system and method for simultaneous same-frequency full duplex cooperative communication Download PDF

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CN107659527B
CN107659527B CN201710843738.8A CN201710843738A CN107659527B CN 107659527 B CN107659527 B CN 107659527B CN 201710843738 A CN201710843738 A CN 201710843738A CN 107659527 B CN107659527 B CN 107659527B
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relay
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CN107659527A (en
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黄川�
陈家令
何萌
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University of Electronic Science and Technology of China
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2689—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation
    • H04L27/2691—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation involving interference determination or cancellation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/022—Channel estimation of frequency response
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03178—Arrangements involving sequence estimation techniques
    • H04L25/03248—Arrangements for operating in conjunction with other apparatus
    • H04L25/0328—Arrangements for operating in conjunction with other apparatus with interference cancellation circuitry
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2689—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation
    • H04L27/2692—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation with preamble design, i.e. with negotiation of the synchronisation sequence with transmitter or sequence linked to the algorithm used at the receiver
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2689—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation
    • H04L27/2695—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation with channel estimation, e.g. determination of delay spread, derivative or peak tracking
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/38—Demodulator circuits; Receiver circuits
    • H04L27/3845—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier
    • H04L27/3854—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier using a non - coherent carrier, including systems with baseband correction for phase or frequency offset
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/14—Two-way operation using the same type of signal, i.e. duplex
    • H04L5/1461—Suppression of signals in the return path, i.e. bidirectional control circuits

Abstract

The invention discloses a phase noise suppression system and a phase noise suppression method for simultaneous co-frequency full duplex cooperative communication, wherein the system comprises an information source subsystem, a relay subsystem and a terminal receiving subsystem; the output end of the information source subsystem is connected with the terminal receiving subsystem through the relay subsystem; the information source subsystem is used for generating a target signal, processing the generated signal and sending the processed signal to the relay subsystem; the relay subsystem is used for receiving the signal from the information source subsystem, converting the signal into a digital domain, performing receiving processing, performing digital suppression on the received signal in the digital domain, amplifying and inserting pilot frequency into the signal subjected to digital suppression, performing transmitting processing, converting the signal into an analog domain, and transmitting the signal to the receiving subsystem; and the terminal receiving subsystem is used for processing the signals from the relay subsystem to complete the receiving of the target signals. The invention reduces the error rate of signal transmission and inhibits the influence of phase noise interference.

Description

Phase noise suppression system and method for simultaneous same-frequency full duplex cooperative communication
Technical Field
The invention relates to cooperative transmission and phase noise suppression of a relay subsystem, in particular to a phase noise suppression system and a phase noise suppression method for simultaneous same-frequency full duplex cooperative communication.
Background
Phase noise is a harmonic and intermodulation product generated by the nonlinear effects in nonlinear devices, the noise introduced by the oscillator non-idealities creates random phase modulation on the output carrier, and in general, free oscillator phase noise is modeled as a wiener process. Phase noise causes inter-carrier interference (ICI) and Common Phase Error (CPE) of signals in multi-carrier transmission, for example, in a system using Orthogonal Frequency Division Multiplexing (OFDM) modulation, wherein the energy of the common phase error part is much larger than that of the inter-carrier interference part. Therefore, the influence of phase noise can be greatly weakened by suppressing CPE; in the existing mode, a CPE and a self-interference channel can be estimated simultaneously, and a part of the CPE is removed from a self-interference signal, so that the influence of phase noise interference of the self-interference signal in a relay can be suppressed; meanwhile, reasonable power distribution on each subcarrier at the relay effectively improves the signal-to-noise ratio of a receiving end, and although the prior art considers the power distribution under the condition of a single carrier, an optimal power distribution calculation method is not provided, so that the method is not beneficial to reducing the error rate of signal transmission and inhibiting the influence of phase noise interference.
Disclosure of Invention
The invention aims to overcome the defects of the prior art and provides a phase noise suppression system and a phase noise suppression method for simultaneous co-frequency full duplex cooperative communication.
The purpose of the invention is realized by the following technical scheme: a phase noise suppression system for simultaneous co-frequency full duplex cooperative communication comprises an information source subsystem, a relay subsystem and a terminal receiving subsystem; the output end of the information source subsystem is connected with the terminal receiving subsystem through the relay subsystem;
the information source subsystem is used for generating a target signal, processing the generated signal and sending the processed signal to the relay subsystem; specifically, the information source subsystem comprises an information source, an output end of the information source is connected with an information source transmitter sequentially through a first pilot frequency insertion module, a first inverse Fourier transform module, a first cyclic prefix insertion module and a first digital-to-analog conversion module, and the information source transmitter modulates an output signal of the analog-to-digital conversion module to a frequency band in an oscillation mode and transmits the modulated output signal to the relay subsystem through an information source antenna.
The relay subsystem is used for receiving the signal from the information source subsystem, converting the signal into a digital domain and carrying out receiving processing, carrying out digital suppression on the signal subjected to receiving processing in the digital domain, carrying out amplification and pilot frequency insertion on the signal subjected to digital suppression, carrying out emission processing in the next period, converting the signal into an analog domain and transmitting the signal to the receiving subsystem; specifically, the relay subsystem includes a relay receiving antenna, the relay receiving antenna is configured to receive a signal from the information source subsystem, an output end of the relay receiving antenna is connected to the relay receiver, the relay receiver modulates the received signal to a baseband in an oscillating manner, the signal output by the relay receiver is processed sequentially by the first analog-to-digital conversion module, the first cyclic prefix removal module, the first fourier transform module, the digital suppression module, the amplification module, the second pilot frequency insertion module, the second inverse fourier transform module, the second cyclic prefix insertion module, and the second digital-to-analog conversion module, and then the obtained signal is transmitted to the relay transmitter, and the relay transmitter modulates an output signal of the second analog-to-digital conversion module to a frequency band in an oscillating manner and transmits the signal to the receiving subsystem through the relay transmitting antenna; the output end of the second pilot frequency insertion module is also connected with the digital suppression module.
And the terminal receiving subsystem is used for processing the signals from the relay subsystem to complete the receiving of the target signals. Specifically, the terminal receiving subsystem includes a terminal antenna, the terminal antenna receives a signal from the relay transmitter, an output end of the terminal antenna is connected with the terminal receiver, the interrupt receiver modulates the received signal to a baseband in an oscillation mode, then sequentially transmits the signal to the second analog-to-digital conversion module, the second cyclic prefix removal module and the second fourier transform module for processing, and the second fourier transform module outputs a finally obtained signal.
A phase noise suppression method for simultaneous co-frequency full duplex cooperative communication comprises the following steps:
s1, a source subsystem generates a target signal and processes the generated signal, and the processed signal is sent to a relay subsystem; specifically, the step S1 includes the following sub-steps: s101, in the mth communication period, the source generates the transmission power PsSignal
Figure BDA0001411382560000021
S102, uniformly inserting N into signals generated by information sourcespThe position set of the pilot frequency is as follows:
Figure BDA0001411382560000022
and S103, sequentially carrying out inverse Fourier transform, cyclic prefix insertion and digital-to-analog conversion on the signal after pilot frequency insertion to obtain an analog signal to be transmitted, modulating the analog signal to a frequency domain in an oscillation mode, and transmitting the analog signal to the relay subsystem.
S2, the relay subsystem receives a signal from the information source subsystem, converts the signal into a digital domain and performs receiving processing, performs digital suppression on the received signal in the digital domain, performs amplification and pilot frequency insertion on the digitally suppressed signal, performs transmitting processing in the next period, converts the digitally suppressed signal into an analog domain, and transmits the signal to the receiving subsystem; specifically, the step S2 includes the following sub-steps: s201, modulating a received signal to a baseband by a relay subsystem in an oscillation mode, and performing analog-to-digital conversion, cyclic prefix removal and Fourier transform on the baseband signal; s202, performing digital suppression on the signal obtained by Fourier transform, amplifying and inserting pilot frequency into the signal subjected to digital suppression, and taking the inserted pilot frequency signal as the basis of digital suppression of the next period; and S203, delaying the signal obtained in the step S202 for a period, performing Fourier inverse transformation to a time domain, inserting a cyclic prefix into the signal, performing digital-to-analog conversion, modulating the signal to a frequency band in an oscillation mode, and sending the signal to a terminal receiving subsystem.
And S3, the terminal receiving subsystem processes the signal from the relay subsystem to complete the signal receiving. Specifically, the step S3 includes the following sub-steps: the receiving end subsystem modulates the received signal to a baseband in an oscillation mode, and obtains the finally received signal in the (m + 1) th period after analog-to-digital conversion, cyclic prefix removal and Fourier transform
Figure BDA0001411382560000023
Wherein the step S202 comprises the following substeps:
dividing the signal received by the relay subsystem at the pilot position in the mth period by the signal inserted by the relay subsystem at the pilot position in the previous period to obtain the sub-carrier channel estimation value of the pilot position, obtaining the channel estimation values on other sub-carriers in a linear interpolation mode by using the estimation values, and subtracting the product of the transmission signal delayed in the previous period and the estimation channel from the signal received by the relay subsystem in the mth period to realize the self-interference digital suppression of the current period;
calculating the optimal value of the subcarrier power of the transmitted signal in the relay subsystem
Figure BDA0001411382560000031
Amplifying the power of the signal of the k-th subcarrier after self-interference digital suppression to Pk，
Figure BDA0001411382560000032
Obtaining an amplified signal;
inserting power P at ith position of amplified signaltThe resulting signal is used as the basis for digital suppression of the next cycle, i ∈ D.
Wherein the optimal value of the subcarrier power of the transmitted signal in the relay subsystem
Figure BDA0001411382560000033
The calculation steps are as follows:
in a first step, the values of parameters in the system are set, including a total power constraint P at the sourceSTotal power constraint P at the relayR(ii) a Setting an initialization flag value flag to 0 and a point to 0;
and step two, judging whether the conditions are met: pS≤Np·PsOr PR≤Np·PtIf yes, ending and resetting the system parameter value; if not, entering a third step;
thirdly, calculating the signal power of the useful signal subcarrier of the information source
Figure BDA0001411382560000034
The fourth stepCalculating
Figure BDA0001411382560000035
Zero point P ofR0If P isR0＞PR-NpPtA 1 is to PR0Reassign value to PR-NpPtWherein:
Figure BDA0001411382560000036
Figure BDA0001411382560000037
Figure BDA0001411382560000038
kis the mean square of the estimation error of the kth self-interference channel:
Figure BDA0001411382560000041
wherein A (i) represents a sequence
Figure BDA0001411382560000042
N of (A)cThe ith value of the point DFT transform, Δ f, is the ratio of the phase noise 3dB bandwidth to the carrier frequency domain spacing, ErrAnd EsrEnergy, H, representing the impulse response of the channelsr[k]And Hrd[k]A kth value representing DFT variations of channel impulse responses from the source to the relay and from the relay to the destination node, respectively;
the fifth step, setting the stop threshold value to 10-7Setting a parameter a1＝0,b1＝PR0,lef＝a1+0.382·(b1-a1)，rig＝a1+0.618·(b1-a1)；
Sixthly, judging whether flag is 0 or not, if so, setting a parameter Pr-lef; if not, setting a parameter Pr＝rig；
And step seven, performing the following operations:
A. initializing power allocation P on each useful signal subcarrier at the relay0，P0Is 1 × NcThe vector of (a):
Figure BDA0001411382560000043
initialization
Figure BDA0001411382560000044
Setting an iteration stop condition ηo＝10-2，ηi＝10-5T 4096, the incremental multiple mu 10 and the total number of constraints m 2 (N)c-Np)；
B. Is provided with
Figure BDA0001411382560000045
As a function of variables
Figure BDA0001411382560000046
Comprises the following steps:
Figure BDA0001411382560000047
wherein the content of the first and second substances,
Figure BDA0001411382560000048
Eu[k]denotes λ2Ps|Hrd[k]|2|Hsr[k]|2，FkRepresents the intercarrier interference energy on the kth subcarrier at the relay, and the estimated value is
Figure BDA0001411382560000049
C. Judging whether the requirements are met
Figure BDA00014113825600000410
If not, go to step F, if not, go toThe method comprises the following steps:
(1) if it is
Figure BDA00014113825600000411
According to gammaFD[k]In respect of P0,kDerivative of (2)
Figure BDA00014113825600000412
Calculating a function
Figure BDA00014113825600000413
In respect of P0,kDerivative of, P0,kRepresents P0The value of the kth element of (c):
Figure BDA0001411382560000051
then according to gammaFD[k]In respect of P0,kSecond derivative of (2)
Figure BDA0001411382560000052
Calculating a function
Figure BDA0001411382560000053
In respect of P0,kSecond derivative of (d):
Figure BDA0001411382560000054
and calculating an intermediate value w:
Figure BDA0001411382560000055
calculating P from the intermediate value w0To (1) a
Figure BDA0001411382560000056
An update value increment for each element;
Figure BDA0001411382560000057
when k ∈D, when is equal to Δ PkThe value is assigned to 0. To P0Performing update, the updated P0Is equal to P before update0Adding 0.1 times of Δ P, wherein Δ P represents Δ PkA vector of components;
according to the intermediate value w pair
Figure BDA0001411382560000058
Updating, after updating
Figure BDA0001411382560000059
The method comprises the following steps:
Figure BDA00014113825600000510
(2) if it is judged to be updated
Figure BDA00014113825600000511
Whether or not to satisfy
Figure BDA00014113825600000512
If yes, entering operation D, otherwise, returning to the step (1);
D. updating the value of t, wherein the value of t after updating is equal to the multiplication mu of t before updating;
E. judging whether the updated t satisfies
Figure BDA00014113825600000513
If yes, entering operation F, and if not, returning to operation C;
F. calculating the median mw [ k ]:
Figure BDA00014113825600000514
calculating the bit error rate r according to the intermediate value mw [ k ]:
Figure BDA00014113825600000515
then judging whether flag is 0 or not, if so, judging P0Assign value to Pf and assign value to rBf, otherwise, P is added0Assigning a value to Pg and assigning a value to r to Bg;
eighthly, judging whether the point is equal to 0, if so, reassigning the point and the flag to be 1, and returning to the sixth step; if not, entering the ninth step;
ninthly, judging whether | Bf-Bg | is satisfied or not, if yes, returning Pf as a vector formed by optimal values of relay subcarrier power distribution, and finishing calculation; if not, entering the tenth step;
step ten, comparing Bf and Bg:
if Bf > Bg, let a1＝lef,lef＝rig,rig＝a1+0.618·(b1-a1) If flag is 1, returning to the sixth step;
if Bf is less than or equal to Bg, let b1＝rig,rig＝lef,lef＝a1+0.382·(b1-a1) And if the flag is 0, returning to the sixth step.
The invention has the beneficial effects that: in the relay subsystem, the influence of phase noise is inhibited by inhibiting the public phase error part of self-interference, and in the following amplification process, the signal-to-noise ratio of a receiving end is improved by reasonably setting the power on the subcarrier through calculation, so that the influence of the phase noise is further inhibited, the error rate of signal transmission is reduced, and the influence of the phase noise interference on full-duplex cooperative communication is reduced.
Drawings
FIG. 1 is a schematic block diagram of the system of the present invention;
FIG. 2 is a flow chart of a method of the present invention;
FIG. 3 is a diagram illustrating the effect of CPE suppression from interference signals on the system bit error rate;
fig. 4 is a schematic diagram illustrating the effect of the power allocation method on the system error rate.
Detailed Description
The technical solutions of the present invention are further described in detail below with reference to the accompanying drawings, but the scope of the present invention is not limited to the following.
As shown in fig. 1, a phase noise suppression system for simultaneous co-frequency full duplex cooperative communication includes a signal source subsystem, a relay subsystem and a terminal receiving subsystem; the output end of the information source subsystem is connected with the terminal receiving subsystem through the relay subsystem;
the information source subsystem is used for generating a target signal, processing the generated signal and sending the processed signal to the relay subsystem; specifically, the information source subsystem comprises an information source, an output end of the information source is connected with an information source transmitter sequentially through a first pilot frequency insertion module, a first inverse Fourier transform module, a first cyclic prefix insertion module and a first digital-to-analog conversion module, and the information source transmitter modulates an output signal of the analog-to-digital conversion module to a frequency band in an oscillation mode and transmits the modulated output signal to the relay subsystem through an information source antenna.
The relay subsystem is used for receiving the signal from the information source subsystem, converting the signal into a digital domain and carrying out receiving processing, carrying out digital suppression on the signal subjected to receiving processing in the digital domain, carrying out amplification and pilot frequency insertion on the signal subjected to digital suppression, carrying out emission processing in the next period, converting the signal into an analog domain and transmitting the signal to the receiving subsystem; specifically, the relay subsystem includes a relay receiving antenna, the relay receiving antenna is configured to receive a signal from the information source subsystem, an output end of the relay receiving antenna is connected to the relay receiver, the relay receiver modulates the received signal to a baseband in an oscillating manner, the signal output by the relay receiver is processed sequentially by the first analog-to-digital conversion module, the first cyclic prefix removal module, the first fourier transform module, the digital suppression module, the amplification module, the second pilot frequency insertion module, the second inverse fourier transform module, the second cyclic prefix insertion module, and the second digital-to-analog conversion module, and then the obtained signal is transmitted to the relay transmitter, and the relay transmitter modulates an output signal of the second analog-to-digital conversion module to a frequency band in an oscillating manner and transmits the signal to the receiving subsystem through the relay transmitting antenna; the output end of the second pilot frequency insertion module is also connected with the digital suppression module.
And the terminal receiving subsystem is used for processing the signals from the relay subsystem to complete the receiving of the target signals. Specifically, the terminal receiving subsystem includes a terminal antenna, the terminal antenna receives a signal from the relay transmitter, an output end of the terminal antenna is connected with the terminal receiver, the interrupt receiver modulates the received signal to a baseband in an oscillation mode, then sequentially transmits the signal to the second analog-to-digital conversion module, the second cyclic prefix removal module and the second fourier transform module for processing, and the second fourier transform module outputs a finally obtained signal.
As shown in fig. 2, a method for suppressing phase noise in simultaneous co-frequency full duplex cooperative communication includes the following steps:
s1, a source subsystem generates a target signal and processes the generated signal, and the processed signal is sent to a relay subsystem; specifically, the step S1 includes the following sub-steps: s101, in the mth communication period, the source generates the transmission power PsSignal
Figure BDA0001411382560000071
S102, uniformly inserting N into signals generated by information sourcespThe position set of the pilot frequency is as follows:
Figure BDA0001411382560000072
and S103, sequentially carrying out inverse Fourier transform, cyclic prefix insertion and digital-to-analog conversion on the signal after pilot frequency insertion to obtain an analog signal to be transmitted, modulating the analog signal to a frequency domain in an oscillation mode, and transmitting the analog signal to the relay subsystem.
S2, the relay subsystem receives a signal from the information source subsystem, converts the signal into a digital domain and performs receiving processing, performs digital suppression on the received signal in the digital domain, performs amplification and pilot frequency insertion on the digitally suppressed signal, performs transmitting processing in the next period, converts the digitally suppressed signal into an analog domain, and transmits the signal to the receiving subsystem; specifically, the step S2 includes the following sub-steps: s201, modulating a received signal to a baseband by a relay subsystem in an oscillation mode, and performing analog-to-digital conversion, cyclic prefix removal and Fourier transform on the baseband signal; s202, performing digital suppression on the signal obtained by Fourier transform, amplifying and inserting pilot frequency into the signal subjected to digital suppression, and taking the inserted pilot frequency signal as the basis of digital suppression of the next period; and S203, delaying the signal obtained in the step S202 for a period, performing Fourier inverse transformation to a time domain, inserting a cyclic prefix into the signal, performing digital-to-analog conversion, modulating the signal to a frequency band in an oscillation mode, and sending the signal to a terminal receiving subsystem.
And S3, the terminal receiving subsystem processes the signal from the relay subsystem to complete the signal receiving. Specifically, the step S3 includes the following sub-steps: the receiving end subsystem modulates the received signal to a baseband in an oscillation mode, and obtains the finally received signal in the (m + 1) th period after analog-to-digital conversion, cyclic prefix removal and Fourier transform
Figure BDA0001411382560000081
Wherein the step S202 comprises the following substeps:
dividing the signal received by the relay subsystem at the pilot position in the mth period by the signal inserted by the relay subsystem at the pilot position in the previous period to obtain the sub-carrier channel estimation value of the pilot position, obtaining the channel estimation values on other sub-carriers in a linear interpolation mode by using the estimation values, and subtracting the product of the transmission signal delayed in the previous period and the estimation channel from the signal received by the relay subsystem in the mth period to realize the self-interference digital suppression of the current period;
calculating the optimal value of the subcarrier power of the transmitted signal in the relay subsystem
Figure BDA0001411382560000082
Amplifying the power of the signal of the k-th subcarrier after self-interference digital suppression to Pk，
Figure BDA0001411382560000083
Obtaining an amplified signal;
inserting power P at ith position of amplified signaltThe resulting signal is suppressed as the next cycle number, i ∈ DAnd (4) a foundation.
Wherein the optimal value of the subcarrier power of the transmitted signal in the relay subsystem
Figure BDA0001411382560000084
The calculation steps are as follows:
in a first step, the values of parameters in the system are set, including a total power constraint P at the sourceSTotal power constraint P at the relayR(ii) a Setting an initialization flag value flag to 0 and a point to 0;
and step two, judging whether the conditions are met: pS≤Np·PsOr PR≤Np·PtIf yes, ending and resetting the system parameter value; if not, entering a third step;
thirdly, calculating the signal power of the useful signal subcarrier of the information source
Figure BDA0001411382560000085
The fourth step, calculating
Figure BDA0001411382560000086
Zero point P ofR0If P isR0＞PR-NpPtA 1 is to PR0Reassign value to PR-NpPtWherein:
Figure BDA0001411382560000087
Figure BDA0001411382560000088
Figure BDA0001411382560000091
kis the mean square of the estimation error of the kth self-interference channel:
Figure BDA0001411382560000092
wherein A (i) represents a sequence
Figure BDA0001411382560000093
N of (A)cThe ith value of the point DFT transform, Δ f, is the ratio of the phase noise 3dB bandwidth to the carrier frequency domain spacing, ErrAnd EsrEnergy, H, representing the impulse response of the channelsr[k]And Hrd[k]A kth value representing DFT variations of channel impulse responses from the source to the relay and from the relay to the destination node, respectively;
the fifth step, setting the stop threshold value to 10-7Setting a parameter a1＝0,b1＝PR0,lef＝a1+0.382·(b1-a1)，rig＝a1+0.618·(b1-a1)；
Sixthly, judging whether flag is 0 or not, if so, setting a parameter Pr-lef; if not, setting a parameter Pr＝rig；
And step seven, performing the following operations:
A. initializing power allocation P on each useful signal subcarrier at the relay0，P0Is 1 × NcThe vector of (a):
Figure BDA0001411382560000094
initialization
Figure BDA0001411382560000095
Setting an iteration stop condition ηo＝10-2，ηi＝10-5T 4096, the incremental multiple mu 10 and the total number of constraints m 2 (N)c-Np)；
B. Is provided with
Figure BDA0001411382560000096
As a function of variables
Figure BDA0001411382560000097
Comprises the following steps:
Figure BDA0001411382560000098
wherein the content of the first and second substances,
Figure BDA0001411382560000099
Eu[k]denotes λ2Ps|Hrd[k]|2|Hsr[k]|2，FkRepresents the intercarrier interference energy on the kth subcarrier at the relay, and the estimated value is
Figure BDA0001411382560000101
C. Judging whether the requirements are met
Figure BDA0001411382560000102
If not, entering the step F, if yes, carrying out the following steps:
(1) if it is
Figure BDA0001411382560000103
According to gammaFD[k]In respect of P0,kDerivative of (2)
Figure BDA0001411382560000104
Calculating a function
Figure BDA0001411382560000105
In respect of P0,kDerivative of, P0,kRepresents P0The value of the kth element of (c):
Figure BDA0001411382560000106
then according to gammaFD[k]In respect of P0,kSecond derivative of (2)
Figure BDA0001411382560000107
Calculating a function
Figure BDA0001411382560000108
In respect of P0,kSecond derivative of (d):
Figure BDA0001411382560000109
and calculating an intermediate value w:
Figure BDA00014113825600001010
calculating P from the intermediate value w0To (1) a
Figure BDA00014113825600001011
An update value increment for each element;
Figure BDA00014113825600001012
when k ∈ D, Δ PkThe value is assigned to 0. To P0Performing update, the updated P0Is equal to P before update0Adding 0.1 times of Δ P, wherein Δ P represents Δ PkA vector of components;
according to the intermediate value w pair
Figure BDA00014113825600001013
Updating, after updating
Figure BDA00014113825600001014
The method comprises the following steps:
Figure BDA00014113825600001015
(2) if it is judged to be updated
Figure BDA00014113825600001016
Whether or not to satisfy
Figure BDA00014113825600001017
If yes, entering operation D, otherwise, returning to the step (1);
D. updating the value of t, wherein the value of t after updating is equal to the multiplication mu of t before updating;
E. judging whether the updated t satisfies
Figure BDA00014113825600001018
If yes, entering operation F, and if not, returning to operation C;
F. calculating the median mw [ k ]:
Figure BDA0001411382560000111
calculating the bit error rate r according to the intermediate value mw [ k ]:
Figure BDA0001411382560000112
then judging whether flag is 0 or not, if so, judging P0Assign value to Pf and r to Bf, otherwise, assign P to0Assigning a value to Pg and assigning a value to r to Bg;
eighthly, judging whether the point is equal to 0, if so, reassigning the point and the flag to be 1, and returning to the sixth step; if not, entering the ninth step;
ninthly, judging whether | Bf-Bg | is satisfied or not, if yes, returning Pf as a vector formed by optimal values of relay subcarrier power distribution, and finishing calculation; if not, entering the tenth step;
step ten, comparing Bf and Bg:
if Bf > Bg, let a1＝lef,lef＝rig,rig＝a1+0.618·(b1-a1) If flag is 1, returning to the sixth step;
if Bf is less than or equal to Bg, let b1＝rig,rig＝lef,lef＝a1+0.382·(b1-a1) And if the flag is 0, returning to the sixth step.
In the invention, the influence of phase noise is inhibited by inhibiting the CPE part of self-interference, and the power on the subcarrier is reasonably set by calculation in the following amplification process
Figure BDA0001411382560000113
The signal-to-noise ratio of the receiving end is improved, and the influence of phase noise is further inhibited.
In the embodiment of the application, in order to verify the effect of reducing the bit error rate and suppressing the phase noise interference, a simulation experiment is performed: setting the total number of carriers to Nc1057, sample interval TsIs 3.3 × 10-8s, number of pilots NpIs 33, inter-carrier frequency spacing fcarr15kHz, 10dB of pilot power at the source, 15dB of pilot power at the relay, 0,1,4 taps of the signal transmitted from the relay and 0dB, -5dB, -15dB of self-interference channel hrrThe channel parameters from source to relay and from relay to destination node are set to be the same, i.e. the number of taps is 0, 20, 45 and the corresponding power delay profile is 0dB, -9dB, -20 dB. Modeling the phase noise as a wiener process, and 3dB bandwidth f of the phase noise at the oscillator3dB＝80Hz。
As shown in fig. 3, a schematic diagram of the influence of CPE suppression of the self-interference signal on the system error rate in the simulation experiment shows that the change of the system error rate is compared between the suppression with the self-interference signal CPE and the suppression without the self-interference signal CPE. It can be seen that the BER of the system will be significantly reduced by the CPE suppressing the self-interference signal at the relay. When the source power is 18dB, the error rate can be reduced by one order of magnitude by adopting the method for inhibiting the CPE in the patent.
As shown in fig. 4, a schematic diagram of the influence of the power allocation manner on the system error rate is shown, in which the influence of the uniform power allocation manner and the optimal power allocation manner on the system error rate is compared, and the uniform power allocation scheme is an optimal value obtained when the powers on the subcarriers at the relay are consistent. It can be seen from the figure that the optimal power distribution method in the patent can reduce the bit error rate to half of the original bit error rate when the signal power of the signal source is 25dB, and compared with the uniform power method, the method improves the signal-to-noise ratio of the system and suppresses the influence of phase noise interference.

Claims (6)

1. A phase noise suppression system for simultaneous co-frequency full duplex cooperative communication is characterized in that: the system comprises an information source subsystem, a relay subsystem and a terminal receiving subsystem; the output end of the information source subsystem is connected with the terminal receiving subsystem through the relay subsystem;
the information source subsystem is used for generating a target signal, processing the generated signal and sending the processed signal to the relay subsystem;
the relay subsystem is used for receiving the signal from the information source subsystem, converting the signal into a digital domain and carrying out receiving processing, carrying out digital suppression on the signal subjected to the receiving processing in the digital domain, carrying out amplification and pilot frequency insertion on the signal subjected to the digital suppression, carrying out emission processing in the next period, converting the signal into an analog domain, and transmitting the signal to the terminal receiving subsystem;
when the digital suppression is carried out on the received signals, the signals after the digital suppression are amplified and pilot frequency inserted, the relay subsystem uses the signals received at the pilot frequency position in the mth period to divide the signals inserted at the pilot frequency position by the relay subsystem in the previous period to obtain the subcarrier channel estimation values of the pilot frequency position, the estimation values are used for obtaining the estimation values of the channels on other subcarriers in a linear interpolation mode, and the product of the transmission signals delayed in the previous period and the estimation channels is subtracted from the signals received by the relay subsystem in the mth period to realize the self-interference digital suppression of the current period; and calculating an optimum value P of the subcarrier power of the transmission signalk(ii) a Amplifying the power of the signal of the k-th subcarrier after self-interference digital suppression to PkObtaining an amplified signal; inserting pilot frequency in the ith position of the amplified signal, and taking the obtained signal as the basis of digital suppression of the next period;
the terminal receiving subsystem is used for processing the signals from the relay subsystem to complete the receiving of the target signals;
in the relay subsystem, the influence of phase noise is inhibited by inhibiting a public phase error part of self-interference, and in the following amplification process, the power on a subcarrier is reasonably set through calculation to improve the signal-to-noise ratio of a receiving end and further inhibit the influence of the phase noise, so that the error rate of signal transmission is reduced, and the influence of the phase noise interference on full-duplex cooperative communication is reduced.
2. The system of claim 1, wherein the system further comprises a phase noise suppression module configured to perform full duplex cooperative communication with the same frequency: the signal source subsystem comprises a signal source, the output end of the signal source is connected with a signal source transmitter sequentially through a first pilot frequency insertion module, a first inverse Fourier transform module, a first cyclic prefix insertion module and a first digital-to-analog conversion module, and the signal source transmitter modulates the output signal of the first digital-to-analog conversion module to a frequency band in an oscillation mode and sends the signal to the relay subsystem through a signal source antenna.
3. The system of claim 1, wherein the system further comprises a phase noise suppression module configured to perform full duplex cooperative communication with the same frequency: the relay subsystem comprises a relay receiving antenna, the relay receiving antenna is used for receiving signals from the information source subsystem, the output end of the relay receiving antenna is connected with the relay receiver, the relay receiver modulates the received signals to a baseband in an oscillation mode, the signals output by the relay receiver are processed by a first analog-to-digital conversion module, a first cyclic prefix removing module, a first Fourier transform module, a digital suppression module, an amplification module, a second pilot frequency inserting module, a second inverse Fourier transform module, a second cyclic prefix inserting module and a second digital-to-analog conversion module in sequence and then are transmitted to the relay transmitter, the relay transmitter modulates the output signals of the second digital-to-analog conversion module to a frequency band in an oscillation mode and sends the signals to the terminal receiving subsystem through the relay transmitting antenna; the output end of the second pilot frequency insertion module is also connected with the digital suppression module.
4. The system of claim 1, wherein the system further comprises a phase noise suppression module configured to perform full duplex cooperative communication with the same frequency: the terminal receiving subsystem comprises a terminal antenna, the terminal antenna receives signals from the relay transmitter, the output end of the terminal antenna is connected with a terminal receiver, the terminal receiver modulates the received signals to a baseband in an oscillation mode, then sequentially transmits the signals to the second analog-to-digital conversion module, the second cyclic prefix removing module and the second Fourier transform module for processing, and the second Fourier transform module outputs the finally obtained signals.
5. A phase noise suppression method for simultaneous co-frequency full duplex cooperative communication is characterized in that: the method comprises the following steps:
s1, a source subsystem generates a target signal and processes the generated signal, and the processed signal is sent to a relay subsystem;
the step S1 includes the following sub-steps:
s101, in the mth communication period, the source generates the transmission power PsSignal
Figure FDA0002555225620000021
S102, uniformly inserting N into signals generated by information sourcespThe position set of the pilot frequency is as follows:
Figure FDA0002555225620000022
s103, sequentially carrying out inverse Fourier transform, cyclic prefix insertion and digital-to-analog conversion on the signal with the pilot frequency inserted, obtaining an analog signal to be transmitted, modulating the analog signal to a frequency domain in an oscillation mode, and transmitting the analog signal to a relay subsystem;
s2, the relay subsystem receives a signal from the information source subsystem, converts the signal into a digital domain and performs receiving processing, performs digital suppression on the received signal in the digital domain, performs amplification and pilot frequency insertion on the digitally suppressed signal, performs transmission processing in the next period, converts the signal into an analog domain, and transmits the signal to the terminal receiving subsystem;
the step S2 includes the following sub-steps:
s201, modulating a received signal to a baseband by a relay subsystem in an oscillation mode, and performing analog-to-digital conversion, cyclic prefix removal and Fourier transform on the baseband signal;
s202, carrying out digital suppression on the signal obtained by Fourier transform, carrying out amplification and pilot frequency insertion on the signal subjected to digital suppression, and taking the inserted pilot frequency signal as the basis of digital suppression of the next period:
dividing the signal received by the relay subsystem at the pilot position in the mth period by the signal inserted by the relay subsystem at the pilot position in the previous period to obtain the sub-carrier channel estimation value of the pilot position, obtaining the channel estimation values on other sub-carriers in a linear interpolation mode by using the estimation values, and subtracting the product of the transmission signal delayed in the previous period and the estimation channel from the signal received by the relay subsystem in the mth period to realize the self-interference digital suppression of the current period;
calculating the optimal value of the subcarrier power of the transmitted signal in the relay subsystem
Figure FDA0002555225620000023
Optimum value of subcarrier power of transmission signal in relay subsystem
Figure FDA0002555225620000024
The calculation steps are as follows:
in a first step, the values of parameters in the system are set, including a total power constraint P at the sourceSTotal power constraint P at the relayR(ii) a Setting an initialization flag value flag to 0 and a point to 0;
and step two, judging whether the conditions are met: pS≤Np·PsOr PR≤Np·PtIf yes, ending and resetting the system parameter value; if not, entering a third step;
thirdly, calculating the signal power of the useful signal subcarrier of the information source
Figure FDA0002555225620000031
The fourth stepCalculating
Figure FDA0002555225620000032
Zero point P ofR0If P isR0＞PR-NpPtA 1 is to PR0Reassign value to PR-NpPtWherein:
Figure FDA0002555225620000033
Figure FDA0002555225620000034
Figure FDA0002555225620000035
kis the mean square of the estimation error of the kth self-interference channel:
Figure FDA0002555225620000036
wherein A (i) represents a sequence
Figure FDA0002555225620000037
N of (A)cThe ith value of the point DFT transform, Δ f, is the ratio of the phase noise 3dB bandwidth to the carrier frequency domain spacing, ErrAnd EsrEnergy, H, representing the impulse response of the channelsr[k]And Hrd[k]A kth value representing DFT variations of channel impulse responses from the source to the relay and from the relay to the destination node, respectively;
the fifth step, setting the stop threshold value to 10-7Setting a parameter a1＝0,b1＝PR0,lef＝a1+0.382·(b1-a1)，rig＝a1+0.618·(b1-a1)；
Sixthly, judging whether flag is 0 or not, if so, setting a parameter Pr-lef; if notSetting a parameter Pr＝rig；
And step seven, performing the following operations:
A. initializing power allocation P on each useful signal subcarrier at the relay0，P0Is 1 × NcThe vector of (a):
Figure FDA0002555225620000041
initialization
Figure FDA0002555225620000042
Setting an iteration stop condition ηo＝10-2，ηi＝10-5T 4096, the incremental multiple mu 10 and the total number of constraints m 2 (N)c-Np)；
B. Is provided with
Figure FDA0002555225620000043
As a function of variables
Figure FDA00025552256200000417
Comprises the following steps:
Figure FDA0002555225620000044
wherein the content of the first and second substances,
Figure FDA0002555225620000045
Eu[k]denotes λ2Ps|Hrd[k]|2|Hsr[k]|2，FkRepresents the intercarrier interference energy on the kth subcarrier at the relay, and the estimated value is
Figure FDA0002555225620000046
C. Judging whether the requirements are met
Figure FDA0002555225620000047
If not, entering the step F, if yes, carrying out the following steps:
(1) if it is
Figure FDA0002555225620000048
According to gammaFD[k]In respect of P0,kDerivative of (2)
Figure FDA0002555225620000049
Calculating a function
Figure FDA00025552256200000416
In respect of P0,kDerivative of, P0,kRepresents P0The value of the kth element of (c):
Figure FDA00025552256200000410
then according to gammaFD[k]In respect of P0,kSecond derivative of (2)
Figure FDA00025552256200000411
Calculating a function
Figure FDA00025552256200000412
In respect of P0,kSecond derivative of (d):
Figure FDA00025552256200000413
and calculating an intermediate value w:
Figure FDA00025552256200000414
calculating P from the intermediate value w0To (1) a
Figure FDA00025552256200000415
An update value increment for each element;
Figure FDA0002555225620000051
when k ∈ D, Δ PkAssigned a value of 0, to P0Performing update, the updated P0Is equal to P before update0Adding 0.1 times of Δ P, wherein Δ P represents Δ PkA vector of components;
according to the intermediate value w pair
Figure FDA0002555225620000052
Updating, after updating
Figure FDA0002555225620000053
The method comprises the following steps:
Figure FDA0002555225620000054
(2) if it is judged to be updated
Figure FDA0002555225620000055
Whether or not to satisfy
Figure FDA0002555225620000056
If yes, entering operation D, otherwise, returning to the step (1);
D. updating the value of t, wherein the value of t after updating is equal to the multiplication mu of t before updating;
E. judging whether the updated t satisfies
Figure FDA00025552256200000510
If yes, entering operation F, and if not, returning to operation C;
F. calculating the median mw [ k ]:
Figure FDA0002555225620000058
calculating the bit error rate r according to the intermediate value mw [ k ]:
Figure FDA0002555225620000059
then judging whether flag is 0 or not, if so, judging P0Assign value to Pf and r to Bf, otherwise, assign P to0Assigning a value to Pg and assigning a value to r to Bg;
eighthly, judging whether the point is equal to 0, if so, reassigning the point and the flag to be 1, and returning to the sixth step; if not, entering the ninth step;
ninthly, judging whether | Bf-Bg | is satisfied or not, if yes, returning Pf as a vector formed by optimal values of relay subcarrier power distribution, and finishing calculation; if not, entering the tenth step;
step ten, comparing Bf and Bg:
if Bf > Bg, let a1＝lef,lef＝rig,rig＝a1+0.618·(b1-a1) If flag is 1, returning to the sixth step;
if Bf is less than or equal to Bg, let b1＝rig,rig＝lef,lef＝a1+0.382·(b1-a1) If flag is 0, returning to the sixth step;
amplifying the power of the signal of the k-th subcarrier after self-interference digital suppression to Pk，
Figure FDA0002555225620000062
Obtaining an amplified signal;
inserting power P at ith position of amplified signaltThe pilot frequency i ∈ D, and taking the obtained signal as the basis for digital suppression of the next period;
s203, delaying the signal obtained in the step S202 for a period, performing Fourier inverse transformation to a time domain, inserting a cyclic prefix into the signal, performing digital-to-analog conversion, modulating the signal to a frequency band in an oscillation mode, and sending the signal to a terminal receiving subsystem;
and S3, the terminal receiving subsystem processes the signal from the relay subsystem to complete the signal receiving.
6. The method of claim 5, wherein the method for suppressing phase noise in simultaneous co-frequency full duplex cooperative communication comprises: the step S3 includes the following sub-steps: the receiving end subsystem modulates the received signal to a baseband in an oscillation mode, and obtains the finally received signal in the (m + 1) th period after analog-to-digital conversion, cyclic prefix removal and Fourier transform
Figure FDA0002555225620000061
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Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1325198A (en) * 2000-05-22 2001-12-05 美国电报电话公司 Multi-input multi-output orthogonal frequency-division multiplexing system

Family Cites Families (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR100719111B1 (en) * 2005-07-29 2007-05-17 삼성전자주식회사 Phaase noise compensation apparatus to be applied OFDM system and method thereof
CN101136731B (en) * 2007-08-09 2011-08-31 复旦大学 Method for eliminating phase noise using continuous transmission parameter signalling
CN102724027B (en) * 2012-06-15 2015-04-08 西安电子科技大学 Asynchronous space-time code coding/decoding system and method in full-duplex cooperative communication system
GB2509935B (en) * 2013-01-17 2015-06-17 Broadcom Corp Method and apparatus for reducing self-interference
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CN105187115B (en) * 2015-09-30 2018-04-17 西安电子科技大学 Orthogonal frequency division multiplex OFDM while co-channel full duplex trunking method
CN106101045B (en) * 2016-06-03 2019-05-21 北京邮电大学 A kind of OFDM full duplex polarization self-interference removing method based on phase noise Gauss albefaction
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Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1325198A (en) * 2000-05-22 2001-12-05 美国电报电话公司 Multi-input multi-output orthogonal frequency-division multiplexing system

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
同时同频全双工数字自干扰抑制关键技术;张志亮;《中国博士学位论文全文数据库信息科技辑》;20170228;全文 *
同时同频全双工自适应数字自干扰抑制技术研究与验证;文翔;《中国优秀硕士学位论文全文数据库信息科技辑》;20170228;全文 *

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