CN107465353B - Rectifier and control method thereof - Google Patents

Rectifier and control method thereof Download PDF

Info

Publication number
CN107465353B
CN107465353B CN201710630160.8A CN201710630160A CN107465353B CN 107465353 B CN107465353 B CN 107465353B CN 201710630160 A CN201710630160 A CN 201710630160A CN 107465353 B CN107465353 B CN 107465353B
Authority
CN
China
Prior art keywords
diode
phase
current
power switch
switch tube
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN201710630160.8A
Other languages
Chinese (zh)
Other versions
CN107465353A (en
Inventor
李金玉
龚春英
周烨
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Nanjing University of Aeronautics and Astronautics
Original Assignee
Nanjing University of Aeronautics and Astronautics
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Nanjing University of Aeronautics and Astronautics filed Critical Nanjing University of Aeronautics and Astronautics
Priority to CN201710630160.8A priority Critical patent/CN107465353B/en
Publication of CN107465353A publication Critical patent/CN107465353A/en
Application granted granted Critical
Publication of CN107465353B publication Critical patent/CN107465353B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4216—Arrangements for improving power factor of AC input operating from a three-phase input voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The invention discloses a rectifier and a control method thereof, and belongs to the technical field of high power factor rectification. The rectifier includes: the circuit comprises a three-phase voltage source circuit (1), a three-phase uncontrolled rectifying circuit (2), two symmetrical boost circuits (3), a third harmonic voltage generating circuit (4) and an H bridge boost PFC circuit (5). The double half-wave boost PFC can generate two steamed bun wave phase current waveforms in opposite directions within a period of 30-150 degrees and 210-330 degrees respectively, when a certain phase current is vacant, the waveform compensation circuit can be switched to a corresponding phase to compensate the phase current waveform lacking in the corresponding phase, so that the input current is changed into a standard sine wave, and the converter works in a unit power factor rectification state. The invention can be used for a three-phase AC/DC conversion circuit with a Power Factor Correction (PFC) function, and the topological structure is simple, convenient to control and easy to realize.

Description

Rectifier and control method thereof
Technical Field
The invention relates to a rectifier and a control method thereof, belonging to the technical field of high power factor rectification.
Background
The Power Factor Correction technology (Power Factor Correction technology) is a basic technology in the Power electronics field and the industrial field, and is used for inhibiting harmonic pollution so as to reduce the harm of higher current harmonics to a Power grid and various electric equipment. With the increase of electric equipment, the requirements of high efficiency, high power density and high power factor are also put forward on the electric energy converter, so that various novel PFC conversion topologies are generated.
The three-phase PFC circuit is characterized in that the current control is simple, but the input and output currents of the circuit are large, the requirements on filter current are high, the output voltage is overhigh, certain difficulty is brought to the selection of a power tube, the circuit is generally applied to the occasions with unqualified output power less than 10kw and current THD (total harmonic distortion) requirements, the multi-phase multi-switch can control the input current with high precision, the excellent performance is obtained, the number of required switches is large, the compensation cost is high, and the compensation cost is more suitable for the occasions with high average power compensation (APtc) and non-steady state power compensation (APtc) compensation devices.
Disclosure of Invention
In order to solve the problems, the invention provides a rectifier and a control method thereof, which can be used for a three-phase AC/DC conversion circuit with a Power Factor Correction (PFC) function, and the topological structure is simple, convenient to control and easy to realize.
The invention adopts the following technical scheme for solving the technical problems:
a rectifier, comprising: the three-phase voltage source circuit comprises a three-phase voltage source circuit (1), a three-phase uncontrolled rectifying circuit (2), two symmetrical boost circuits (3), a third harmonic voltage generating circuit (4) and an H bridge boost PFC circuit (5), wherein the three-phase voltage source circuit (1) consists of three sinusoidal voltage sources of which the three phases of ua, ub and uc form an angle of 120 degrees with each other, one ends of the ua, ub and uc three-phase voltage sources are connected together to be connected with a central line, and the other ends of the ua, ub and uc three-phase voltage sources are respectively connected with the three-phase uncontrolled rectifying circuit (2);
the three-phase uncontrolled rectifying circuit (2) comprises a first diode D1, a second diode D2, a third diode D3, a fourth diode D4, a fifth diode D5 and a sixth diode D6, wherein the anode of the first diode D1 is connected with the cathode of the second diode D2 to form a first series circuit, the anode of the third diode D3 is connected with the cathode of the fourth diode D4 to form a second series circuit, the anode of the fifth diode D5 is connected with the cathode of the sixth diode D6 to form a third series circuit, the cathodes and the cathodes of the three series circuits are shared, and the anode are shared to form the three-phase uncontrolled rectifying circuit (2); the other end of the ua voltage source is connected with the midpoint of the first series circuit, the other end of the ub voltage source is connected with the midpoint of the second series circuit, the other end of the uc voltage source is connected with the midpoint of the third series circuit, and the central lines of the ua voltage source, the ub voltage source and the uc voltage source are connected with the two symmetrical boost circuits (3);
the two symmetrical boost circuits (3) comprise two input inductors, two power switch tubes, two diodes and two capacitors, wherein the first boost circuit comprises a first input inductor L, a first power switch tube Q1, a seventh diode D7 and a first output capacitor C1, one end of the first input inductor L is connected with the cathode of a fifth diode D5, the other end of the first input inductor L is connected with the drain of the first power switch tube Q1 and the anode of the seventh diode D7, the cathode of the seventh diode D7 is connected with the anode of a first output capacitor C1, the source of the first power switch tube Q1 and the cathode of a first output capacitor C1 are connected with the neutral line of a three-phase voltage source, the second boost circuit comprises a second input inductor L, a second power switch tube Q2, an eighth diode D8 and a second output capacitor C2, one end of the second input inductor Q592 is connected with the cathode of a sixth input inductor D56, the drain of the second input inductor Q8653 is connected with the anode of a second power switch tube D8653, the drain of the second power switch tube Q8653 and the anode of the second output capacitor C8653;
the third harmonic voltage generation circuit (4) comprises a third power switch tube Q3, a fourth power switch tube Q4 and a fifth power switch tube Q5, wherein one end of a power lead end of the third power switch tube Q3 is connected with ua, one end of a power lead end of the fourth power switch tube Q4 is connected with ub, one end of a power lead end of the fifth power switch tube Q5 is connected with uc, and the other end of the power lead end of the third power switch tube Q3, the other end of the power lead end of the fourth power switch tube Q4 and the other end of the power lead end of the fifth power switch tube Q5 are connected and then connected with the anode of a ninth diode D9;
the H bridge boost PFC rectification (5) comprises a ninth diode D9, a twelfth diode D10, an eleventh diode D11, a twelfth diode D12, a third inductor L3, a sixth power switch tube Q6, a thirteenth diode D13 and a third capacitor C3, wherein the anode of the ninth diode D9 is connected with the cathode of the twelfth diode D10, the anode of the eleventh diode D11 is connected with the cathode of the twelfth diode D12, the ninth diode D9 and the eleventh diode D11 are connected with the common cathode and then connected with one end of the third inductor L3, the other end of the third inductor L3 is connected with the anode of the thirteenth diode D13 and the drain of the sixth power switch tube Q6, the cathode of the thirteenth diode D13 is connected with the anode of the third capacitor C3, the twelfth diode D12 and the twelfth diode D10 are connected with the common anode and then connected with the source of the sixth power switch tube Q6 and the cathode of the third capacitor C3, and the twelfth diode D2 is connected with the second power switch tube Q12.
The third power switch tube Q3And a fourth power switch tube Q4And a fifth power switch tube Q5Is a bidirectional controllable switch.
The first power switch tube Q1A second power switch tube Q2And a sixth power switch tube Q6Is a MOSFET or an IGBT.
A method of controlling a rectifier comprising the steps of:
(1) comparing a feedback value of the first output capacitor C1 with a given value, determining the amplitude of the current of the first input inductor L1 through PI regulation, multiplying the amplitude by a voltage sampling value of the cathode of the fifth diode D5 to the ground to obtain a given current inner loop of the first input inductor L1, comparing the given current inner loop of the first input inductor L1 with the current feedback value of the first input inductor L1, and controlling the first power switch Q1 after PI regulation, namely controlling the current of the first inductor L1 to track the envelope curve of the cathode of the fifth diode D5 to the ground;
(2) the amplitude of the current of the second input inductor L2 is given by adopting the amplitude of the current of the first input inductor L1, the amplitude is multiplied by a sampled value of the voltage to ground of the anode of the sixth diode D6 to obtain a given current inner loop of the second input inductor L2, the given current inner loop of the second input inductor L2 is compared with a current feedback value of the second input inductor L2 and is subjected to PI regulation, and then the second power switch tube Q2 is controlled, namely the current of the second input inductor L2 is controlled to track the envelope curve of the voltage to ground of the anode of the sixth diode D6, and at the moment, the three-phase current keeps the same phase with the phase voltage except the zero crossing point of-30 degrees to 30 degrees and the phase current of 150 degrees to 210;
(3) when a certain phase voltage is in the middle of three-phase voltages, no current flows through three-phase uncontrolled rectifier diodes D1-D6 in the phase, at the moment, a bidirectional switch of the corresponding phase of a waveform compensation circuit is conducted to compensate the part lacking in the waveform of the corresponding phase current, the given amplitude of the current of a third input inductor L3 is half of the amplitude of the phase current, the absolute value of the current divided by the third harmonic voltage is used as the given current loop of the third input inductor L3, the given current loop of the third input inductor L3 and the current feedback value of the third input inductor L3 are subjected to difference and PI adjustment, then a sixth power switch tube Q6 is controlled, namely the current of the third input inductor L3 is controlled to track the rectifying voltage envelope curve of a diode H bridge D9-D12, the phase current is controlled to be 30 degrees, the middle 2/4 part of the waveform is compensated from 150 degrees to 210 degrees, the part lacking in the waveform is supplemented, the phase current is a complete sine wave, and the power factor is in phase with.
The invention has the following beneficial effects:
(1) the power factor is higher than that of a three-phase L C filtering passive power factor correction circuit, is improved by 5 percent, and reaches a unit power factor.
(2) The circuit works in a continuous mode, and the current ripple is lower than that of a three-phase single-switch power factor correction circuit.
(3) Compared with three-phase PWM (pulse width modulation) rectification and Vienna rectification, the control of sine wave current input by unit power factor can be realized, but the basic unit of the proposed circuit is a boost circuit, the control is simple, and the work is more reliable and stable.
(4) Compared with a three-single-phase combined three-phase PFC circuit, the total effective value flowing through a switching tube is lower, and the double-frequency ripple of the capacitor voltage is smaller.
(5) The topological circuit is simple in structure, and the power factor correction is realized by adopting an average current control strategy.
Drawings
FIG. 1 is a topology of the present invention, wherein: 1. a three-phase voltage source; 2. a three-phase uncontrolled rectifying circuit; 3. two areA symmetrical boost circuit; 4. a third harmonic voltage generation circuit; 5. an H-bridge boost fc circuit, wherein: u. ofa-uc-a three-phase voltage source; d1-D6Three-phase uncontrolled rectifier diode L1-L3-boost inductance; q1、Q2、Q6-boost power switching tube; q3、Q4、Q5-a bidirectional controllable power switching tube; d7、D8、D13-a boost diode; d9、D10、D11、D12-a rectifier diode; c1-C3-an output filter capacitor; i.e. ia-ic-compensating for the front phase current; i.e. ia2-ic2-compensating for the rear phase current; v1-three phase rectified common cathode-neutral line voltage; v2-three phase rectified common anode-neutral line voltage; i.e. iL1Inductor L1Inputting a current; i.e. iL2Inductor L2Inputting a current; i.e. iL3Inductor L3Inputting a current.
Fig. 2 is a block diagram of a three-phase dual half-wave boost PFC control loop, in which: u. of0-output voltage sampling; u. of0 *-given for the output voltage; i.e. iL1Inductor L1Inputting a current; i.e. iL2Inductor L2Input current uv-outer loop output value, iL1 *Inductor L1Current command value, iL2 *Inductor L2Current command value, v1-three-phase rectified common cathode-neutral voltage sample value, v2-three-phase rectified common anode-neutral voltage sample values.
Fig. 3 is a block diagram of a control loop of a phase current waveform compensation circuit of the present invention, wherein: u. ofa-uc-a three-phase voltage source samples the voltage; u. ofv-an inner loop current amplitude signal; u. oft-the third harmonic extraction circuit output signal; i.e. iL3Inductor L3Input current, R1-amplifier circuit resistance 20000 ohm, R2-amplifying circuit resistor 10000 ohm.
Fig. 4(a) is a three-phase half-wave diode-common-cathode rectified output voltage waveform, and fig. 4(b) is a three-phase half-wave diode-common-cathode rectified output current waveform.
Fig. 5(a) shows the current waveform of the current-a phase current before compensation, fig. 5(b) shows the current waveform of the current-b phase current before compensation, and fig. 5(c) shows the current waveform of the current-c phase current before compensation.
Fig. 6(a) is an uncompensated current waveform of the a phase, fig. 6(b) is a current waveform of the a phase requiring compensation, and fig. 6(c) is a current waveform of the a phase after compensation.
Fig. 7(a) shows the current-waveform-compensated phase a current, fig. 7(b) shows the current-waveform-compensated phase b current, and fig. 7(c) shows the current-waveform-compensated phase c current.
Fig. 8 compensates the a-phase voltage and current waveforms (larger amplitude for voltage and smaller for current).
Fig. 9 shows the input voltage and current waveforms (voltage with larger amplitude and current with smaller amplitude) of part 5 of fig. 1.
Detailed Description
The invention is described in further detail below with reference to the accompanying drawings.
The three-phase double-half-wave boost PFC power factor correction adopts three-phase half-wave rectification combined with two boost switching tubes, the circuit works in an inductive current continuous mode, and the waveform compensation circuit compensates 2/4 parts (-30 degrees to 30 degrees and 150 degrees to 210 degrees) in the middle of input current of the three-phase double-half-wave boost PFC power factor correction circuit, so that the phase input current is a complete sine wave, and the purpose of complete power factor correction is realized.
As shown in fig. 2, the output voltage sample value u0And given value u0 *After difference is made, PI regulation is carried out to form an inner loop current amplitude signal uvMultiplying by a unit half-wave rectified voltage signal to obtain a given signal i of the inner loopL1 */iL2 *After the current feedback value of the inductor L1/L2 is subtracted and PI adjusted, the first power switch tube and the second power switch tube are controlled, namely the current of the inductor L1 is controlled to track the envelope curve of the positive half cycle of the three-phase input voltage, and the current waveform of the inductor L1 is input three timesThe envelope curve of the positive half-cycle steamed bread wave of the phase voltage is controlled, the current of the inductor L2 is controlled to track the envelope curve of the negative half-cycle of the three-phase input voltage, and the current waveform of the inductor L2 is the envelope curve of the negative half-cycle steamed bread wave of the input three-phase voltage.
When a certain phase voltage is in the middle of three-phase voltages, no current flows through the three-phase uncontrolled rectifier diodes D1-D6 in FIG. 1, and in a period, when the certain phase voltage rises from-0.5 Vp (voltage peak value) to 0.5Vp or falls from 0.5Vp to-0.5 Vp under the condition that the three-phase input voltage is symmetrical, the bidirectional switch of the corresponding phase of the waveform compensation circuit is conducted to compensate the part lacking corresponding to the phase current. The conduction conditions of the three-phase selection switches Q3-Q5 of the waveform compensation circuit are as follows: when u isb<ua<ucOr uc<ua<ubThe a-phase selection switch Q3 is on. When u isa<ub<ucOr uc<ub<uaAnd the B-phase selection switch Q4 is turned on. When u isb<uc<uaOr ua<uc<ubThe C-phase selection switch Q5 is turned on, where uaIs a phase voltage, ubIs a b-phase voltage, ucIs the c-phase voltage.
The output voltage waveform of the waveform selection circuit (part 4 of fig. 1) is a waveform (similar to a triangular wave, with a frequency three times the input voltage) composed of the phase voltages of the three-phase input phase voltage waveform at the middle of the voltage at each moment, and is named as a third harmonic voltage here, the diode H-bridge boost PFC (part 5 of fig. 1) works in such a way that the input current is controlled to track the input voltage, i.e., the rectified voltage of the current-tracking diode H-bridge (D9-D12) of the inductor L3, and thus the input voltage and the input current waveform of the diode H-bridge boost PFC (part 5 of fig. 1) are controlled to be the same.
The magnitude of inductor current L3 is controlled to be half of inductor current L1.
Description of waveform shape: third harmonic voltage is defined herein:
Figure GDA0002471455930000071
in fig. 1, the output voltage and the neutral line current before uncompensation in section 4 are waveforms, and the input current of the diode H bridge boost fc in section 5 in fig. 1 is controlled to be the waveform, and the amplitude of the input current is 0.5 times that of the current of the inductor L1.
FIG. 3 is a control block diagram of a diode H-bridge boost PFC (section 5 of FIG. 1). Using single current loop control, the feedback amount is the current of inductor L3, given as the third harmonic u t1, if there is a neutral line, sampling neutral line current, and using absolute value as given value (this method needs neutral line of power supply), 2, using third harmonic generation circuit as part 4 of fig. 1, after phase current waveform with given value being half of current of inductor L1, 0-30 degree, 150-210 degree, 330-360 degree is compensated, phase current is complete sine wave.
The waveform compensation circuit compensates the phase current (-30 DEG to 30 DEG, 150 DEG to 210 DEG), i.e., the central 2/4 portion of the waveform, and fills the missing portion of the waveform. Thus, the phase current is a complete sine wave and in phase with the input voltage, with a power factor of 1.
Fig. 4(a) is a three-phase half-wave diode-cathode-shared rectified output voltage waveform, and fig. 4(b) is a three-phase half-wave diode-cathode-shared rectified output current waveform, and it can be seen from the figure that the inductor current waveform tracks the input voltage waveform.
Fig. 5(a) shows the current waveform of the current before compensation, the phase current a before compensation, fig. 5(b) shows the current waveform of the current before compensation, the phase current b before compensation, and fig. 5(c) shows the phase current c before compensation, and it can be seen that the phase current waveform has a part missing from-30 ° to 30 °, 150 ° to 210 ° in the uncompensated case.
Fig. 6(a) is an uncompensated current waveform of phase a, fig. 6(b) is a current waveform of phase a requiring compensation, and fig. 6(c) is a current waveform of phase a after compensation.
Fig. 7(a) shows the current-waveform-compensated phase a, fig. 7(b) shows the current-waveform-compensated phase b, and fig. 7(c) shows the current-waveform-compensated phase c, which shows that the three-phase input currents are compensated to have a standard sine wave waveform and have a phase difference of 120 °.
Fig. 8 shows the compensated a-phase voltage and current waveforms (voltage with larger amplitude and current with smaller amplitude), and the phase difference between the input voltage and the current is zero.
Fig. 9 shows the input voltage and current waveforms (larger amplitude for voltage and smaller for current) of part 5 of fig. 1, with current tracking voltage envelope and current amplitude 0.5 times the phase current amplitude of the three-phase input current.

Claims (1)

1. A method of controlling a rectifier, the rectifier comprising: the three-phase direct current power supply comprises a three-phase voltage source circuit (1), a three-phase uncontrolled rectifying circuit (2), two symmetrical boost circuits (3), a third harmonic voltage generating circuit (4) and an H bridge boost PFC circuit (5), wherein the three-phase voltage source circuit (1) is composed of a u bridgea、ub、ucThree-phase voltage source composition ua、ub、ucOne end of the three-phase voltage source is connected with a neutral line, and the other end of the three-phase voltage source is respectively connected with the three-phase uncontrolled rectifying circuit (2);
the three-phase uncontrolled rectifying circuit (2) comprises a first diode D1A second diode D2A third diode D3A fourth diode D4A fifth diode D5And a sixth diode D6Wherein the first diode D1Anode of and a second diode D2Are connected to form a first series circuit, a third diode D3And a fourth diode D4Are connected to form a second series circuit, a fifth diode D5And a sixth diode D6The cathodes of the three series circuits are connected to form a third series circuit, the cathodes of the three series circuits are the same as the cathodes, and the anodes of the three series circuits are the same as the anodes to form a three-phase uncontrolled rectifying circuit (2); wherein u isaThe other end of the voltage source is connected to the midpoint of the first series circuit, ubThe other end of the voltage source is connected to the midpoint of a second series circuit ucThe other end of the voltage source is connected with the midpoint of the third series circuit, and the central line and two pairs of ua, ub and uc three-phase voltage sourcesThe named boost circuits (3) are connected;
the two symmetrical boost circuits (3) comprise two input inductors, two power switching tubes, two diodes and two capacitors, wherein the first boost circuit comprises a first inductor L1A first power switch tube Q1The seventh diode D7And a first output capacitor C1Wherein the first inductor L1And a fifth diode D5Is connected to the cathode of the first inductor L1And the other end of the first power switch tube Q1And a seventh diode D7Is connected to the anode of a seventh diode D7The cathode is connected with a first output capacitor C1The first power switch tube Q1Source electrode and first output capacitor C1Is connected to the neutral line of the three-phase voltage source, the second boost circuit comprises a second inductor L2A second power switch tube Q2An eighth diode D8And a second output capacitor C2Wherein the second inductor L2And a sixth diode D6Is connected with the anode of the second power switch tube Q2Source and eighth diode D8Cathode connected to a second power switch tube Q2And a second output capacitor C2Is connected to the neutral line of the three-phase voltage source, and an eighth diode D8Anode and second output capacitor C2Connecting the negative electrodes;
the third harmonic voltage generation circuit (4) comprises a third power switch tube Q3And a fourth power switch tube Q4And a fifth power switch tube Q5Wherein the third power switch tube Q3One end of the power lead terminal is connected with uaFourth power switch tube Q4One end of the power lead terminal is connected with ubFifth power switch tube Q5One end of the power lead terminal is connected with ucThird power switch tube Q3The other end of the power lead end and a fourth power switch tube Q4The other end of the power lead terminal and a fifth power switch tube Q5The other end of the power lead wire end is connected with a ninth diode D9An anode;
the H-bridge boost PFC rectifier (5) comprises a ninth diodeD9The twelfth polar tube D10Eleventh diode D11The twelfth diode D12A third inductor L3And a sixth power switch tube Q6Thirteenth diode D13And a third capacitance C3Wherein the ninth diode D9Anode and twelfth polar tube D10Cathode connected, eleventh diode D11Anode and twelfth diode D12Cathode connected to a ninth diode D9Eleventh diode D11The third inductor L is connected after the connection of the common cathode3Third inductor L3The other end is connected with a thirteenth diode D13Anode of and sixth power switch tube Q6Drain electrode, thirteenth diode D13Is connected with a third capacitor C3Anode of (2), a twelfth diode D12The twelfth polar tube D10The common anode is connected with a sixth power switch tube Q6Source electrode of and third capacitor C3Negative electrode of (1), twelfth diode D12Cathode and second power switch tube Q2The drain electrodes are connected;
the method is characterized by comprising the following steps:
(1) a first output capacitor C1Is compared with a given value and a first inductance L is determined by PI regulation1The amplitude of the current, this amplitude being multiplied by the fifth diode D5Sampling the cathode to ground voltage to obtain a first inductor L1Given current inner loop, first inductance L1Current inner loop given and first inductance L1The current feedback value is compared and is regulated by PI to control the first power switch tube Q1I.e. control of the first inductance L1Current-tracking fifth diode D5A cathode voltage-to-ground envelope;
(2) second inductor L2The first inductor L is used for the given amplitude of the current1The amplitude of the current is given and is multiplied by the sixth diode D6Second inductor L obtained by sampling anode-to-ground voltage2Given current inner loop, second inductance L2Current inner loop given and second inductance L2The current feedback value is compared and is regulated by PI to control the second power switch tube Q2I.e. controlSecond inductor L2Current-tracking sixth diode D6An envelope curve of the anode to the ground voltage, wherein the three-phase current keeps consistent with the phase voltage except-30 degrees to 30 degrees and 150 degrees to 210 degrees;
(3) when a certain phase voltage is in the middle of three-phase voltage, no current flows through the three-phase uncontrolled rectifier diode D1-D6At this time, the bidirectional switch of the corresponding phase of the waveform compensation circuit is turned on to compensate the missing part of the corresponding phase current waveform, and the third inductor L3The current is given an amplitude of half the phase current amplitude divided by the absolute value of the third harmonic voltage as the third inductor L3Given current loop, third inductance L3Current loop setting and third inductance L3The sixth power switch tube Q is controlled after the current feedback value is subjected to difference and PI regulation6I.e. the current-tracking diode H-bridge D controlling the third inductor L39-D12The envelope of the rectified voltage of-30 deg. to 30 deg., 150 deg. to 210 deg., i.e., the central 2/4 portion of the phase current waveform, is compensated for, filling the missing portion of the waveform, the phase current is a complete sine wave, and is in phase with the input voltage, and the power factor is 1.
CN201710630160.8A 2017-07-28 2017-07-28 Rectifier and control method thereof Active CN107465353B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201710630160.8A CN107465353B (en) 2017-07-28 2017-07-28 Rectifier and control method thereof

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201710630160.8A CN107465353B (en) 2017-07-28 2017-07-28 Rectifier and control method thereof

Publications (2)

Publication Number Publication Date
CN107465353A CN107465353A (en) 2017-12-12
CN107465353B true CN107465353B (en) 2020-07-28

Family

ID=60547786

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201710630160.8A Active CN107465353B (en) 2017-07-28 2017-07-28 Rectifier and control method thereof

Country Status (1)

Country Link
CN (1) CN107465353B (en)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR3099010B1 (en) * 2019-07-15 2021-08-06 Commissariat Energie Atomique COMPACT UWB TRANSMITTER WITH VERY LOW CONSUMPTION AND RECONFIGURABLE WAVEFORM
AU2022234677A1 (en) * 2021-03-10 2023-10-19 Enphase Energy, Inc. Partial-resonant converters for pv applications
CN113131764B (en) * 2021-04-19 2022-08-26 湘潭大学 Terminal sliding mode back-thrust current control method of 12-pulse hybrid Vienna rectifier

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6154380A (en) * 1996-08-22 2000-11-28 Telefonaktiebolaget Lm Ericsson AC/DC boost converter
CN101540507A (en) * 2008-03-21 2009-09-23 力博特公司 Compensating three-phase active power factor correcting circuit
CN102447403A (en) * 2011-11-09 2012-05-09 北京工业大学 Three-phase rectifier circuit with low harmonic wave continuous input current
CN102593945A (en) * 2012-02-20 2012-07-18 华为技术有限公司 Uninterruptible power supply circuit

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6154380A (en) * 1996-08-22 2000-11-28 Telefonaktiebolaget Lm Ericsson AC/DC boost converter
CN101540507A (en) * 2008-03-21 2009-09-23 力博特公司 Compensating three-phase active power factor correcting circuit
CN102447403A (en) * 2011-11-09 2012-05-09 北京工业大学 Three-phase rectifier circuit with low harmonic wave continuous input current
CN102593945A (en) * 2012-02-20 2012-07-18 华为技术有限公司 Uninterruptible power supply circuit

Also Published As

Publication number Publication date
CN107465353A (en) 2017-12-12

Similar Documents

Publication Publication Date Title
CN111416534B (en) Current path reconstruction type single-phase five-level rectifier
CN101986542A (en) PFC (power factor correction) control method with high input power factor and control circuit thereof
CN107465353B (en) Rectifier and control method thereof
CN112865587B (en) Single-phase three-level rectifier of double-barrelled T type bridge
CN111082680B (en) Single-phase five-level rectifier based on T-shaped structure
CN112865569A (en) Single-phase three-level rectifier of mixed T-shaped bridge
CN209787041U (en) Three-phase boost-buck PFC (power factor correction) rectification circuit
CN109309447B (en) Constant switching frequency controlled CRM buck PFC converter
CN107332438B (en) Power factor correction method based on double-inductor double-voltage direct current output circuit
CN103840652A (en) Composite power factor correction circuit
CN107070196A (en) A kind of three-phase PFC rectification circuits with center line
CN102769394B (en) Single-phase controllable rectification circuit
CN112350590A (en) Uncontrolled rectifier harmonic compensation circuit and control method
CN107124105A (en) Improve isolated form three-level PFC converter PF control system and method
CN110829823B (en) Device and method for improving critical inductance of DCM boost PFC converter
CN111316558B (en) Power conversion device
Baharom et al. Computer simulation model and performance analysis of high power factor three-phase AC-DC current injection hybrid resonant converter
CN108809130B (en) Modulation method of Semi-Z source single-phase inverter
CN113224964B (en) Control method of single-phase single-stage boost inverter
Alias et al. Bidirectional three phase power converter
CN110112902B (en) Three-phase boost-buck PFC rectification circuit
Sreenivas et al. Design and Analysis of Predictive control using PI controller for Boost Converter with Active Power Factor Correction
CN112865508A (en) Single-phase three-level power factor correction circuit of novel asymmetric T-shaped bridge
Singh et al. Analysis and design of a zeta converter based three-phase switched mode power supply
CN112072908A (en) Six-inductor double-switch PFC topological structure for improving UPS power factor

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant