CN107086789B - Secondary control quasi-resonance switching power supply converter - Google Patents

Secondary control quasi-resonance switching power supply converter Download PDF

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Publication number
CN107086789B
CN107086789B CN201710288928.8A CN201710288928A CN107086789B CN 107086789 B CN107086789 B CN 107086789B CN 201710288928 A CN201710288928 A CN 201710288928A CN 107086789 B CN107086789 B CN 107086789B
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switching
switching tube
tube
quasi
voltage
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CN107086789A (en
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汤能文
朱昌亚
洪光岱
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Huizhou Jinhu Industrial Development Co ltd
Ten Pao Electronics Huizhou Co Ltd
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Huizhou Jinhu Industrial Development Co ltd
Ten Pao Electronics Huizhou Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4815—Resonant converters
    • H02M7/4818—Resonant converters with means for adaptation of resonance frequency, e.g. by modification of capacitance or inductance of resonance circuits
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The invention relates to the technical field of switching power supplies, and particularly discloses a secondary control quasi-resonant switching power supply converter which is provided with a power input positive end, a power input negative end, a power output positive end and a power output negative end which are connected with a power supply, and a switching controller. The implementation of the secondary control quasi-resonance switching power supply converter provided by the invention greatly reduces the switching loss of the switching power supply converter and has high conversion efficiency; the overlarge current flowing through the switching tube is avoided, so that the switching tube is protected from being damaged; the rectifier tube realizes soft turn-on, has high efficiency, no voltage spike and good EMI characteristics.

Description

Secondary control quasi-resonance switching power supply converter
Technical Field
The invention relates to the technical field of switching power supplies, in particular to a secondary control quasi-resonance switching power supply converter.
Background
At present, a flyback switching power supply converter mostly adopts a PWM (pulse width modulation) control mode with fixed frequency and a PFM (pulse frequency modulation) quasi-resonance control mode with variable frequency, and in the conventional power supply converter with the PWM control mode, a power switch tube is in a hard switching state and is not switched off at zero voltage, so that switching loss is large, and the conversion efficiency of the power supply converter is low; in the PFM quasi-resonant switch mode power supply converter with variable frequency, the power switch tube is conducted at the trough bottom of the resonant voltage wave at two ends of the resonant capacitor Cr, so that partial on loss can be reduced, and when the switch tube is turned off, the voltage at two ends of the switch tube rises rapidly from zero, and the current of the switch tube drops rapidly from the maximum, so that an overlap area is inevitably formed between the voltage and the current at two ends of the switch tube, the switching loss is generated by overlapping of voltage and current waveforms, and the loss increases rapidly with the increase of the switching frequency.
The PWM control mode with fixed frequency and the PFM quasi-resonance control mode with variable frequency are adopted, after a power switch tube is turned off, the energy stored in a primary inductance winding of a transformer is switched to a secondary inductance winding, the flyback voltage of the secondary winding of the transformer is rapidly increased until the flyback voltage is higher than the output voltage, at the moment, a secondary rectifying diode is conducted, in the process, the change rate of the induced current of the secondary inductance winding from the minimum to the maximum is large, and the rectifying diode needs to recover from the cut-off to the conduction, so that larger loss and peak voltage are brought about when the rectifying diode is conducted during high-frequency operation, the voltage stress of the diode is high, and the EMI (electromagnetic interference) characteristic of a power supply is poor. In order to reduce the current change rate when the rectifier diode is turned on, the rectifier diode is generally connected with an inductor in series, but the inductor stores energy in the conduction period of the rectifier tube, and the energy needs to be reversely released when the rectifier tube is turned off, so that the peak and loss when the rectifier tube is turned off can be increased.
In a flyback switching power converter, to reduce the turn-off loss of a switching tube of a high-frequency switch, the change rate of voltage and current needs to be reduced, the change rate of voltage and current is generally reduced mainly by connecting capacitors in parallel at two ends of the switching tube, or an active clamping circuit is adopted to reduce the turn-off loss, while part of energy stored in the switching tube turn-off period by connecting the capacitors in parallel at two ends of the switching tube can directly short-circuit the capacitor when the switching tube is turned on, great loss is brought, even the switching tube is damaged, and the active clamping circuit is complex to control, so that the effect of reducing the turn-off loss is very limited.
Disclosure of Invention
The invention provides a secondary control quasi-resonance switching power supply converter, which is characterized in that an internal circuit of the switching power supply converter is built by an original switching controller, a switching tube, a resonance capacitor, a transformer, a rectifying diode and a polarity capacitor, and an additional diode, a transformer, a switching tube and a quasi-resonance control circuit which is only composed of a resistor, a capacitor, a triode and a voltage stabilizing tube, so that the technical problems of zero voltage turn-off of the original switching tube and smaller current and voltage change rate of the original secondary rectifying tube are solved.
In order to solve the technical problems, the invention provides a secondary control quasi-resonant switching power supply converter, which is provided with a power input positive end, a power input negative end, a power output positive end and a power output negative end which are connected with a power supply, and a switching controller, wherein the power input negative end is connected with a power negative end of the switching controller and one end of a current detection resistor, the other end of the current detection resistor is connected with a switching current detection end of the switching controller and a voltage output end of a first switching tube, a control end of the first switching tube is connected with a switching control output end of the switching controller, a voltage input end of the first switching tube is connected with a synonym end of a primary winding of a first transformer, and a synonym end of the primary winding of the first transformer is connected with the power input positive end;
the synonym end of the secondary winding of the first transformer, the anode of the first diode, the positive end of the power supply of the quasi-resonance control circuit, the cathode of the second diode and the positive end of the polar capacitor are connected with the positive end of the power supply output, the cathode of the first diode is connected with the resonance capacitor and then connected with the homonymous end of the secondary winding of the first transformer, the rectification input end of the secondary rectifying tube and the control signal input end of the quasi-resonance control circuit;
the power supply negative terminal of the quasi-resonance control circuit, the rectification output end of the secondary rectifying tube, the voltage output end of the second switching tube, the homonymous end of the secondary winding of the second transformer and the negative electrode end of the polar capacitor are connected with the power supply output negative terminal, and the control signal output end of the quasi-resonance control circuit is connected with the control end of the second switching tube;
the voltage input end of the second switching tube is connected with the synonym end of the primary winding of the second transformer, the synonym end of the primary winding of the second transformer is connected with the cathode of the first diode, and the synonym end of the secondary winding of the second transformer is connected with the anode of the second diode.
Specifically, a first triode, a second triode, a third triode, a first resistor, a second resistor, a third resistor, a first voltage stabilizing tube, a second voltage stabilizing tube, a first capacitor and a second capacitor are arranged in the quasi-resonance control circuit;
the collector of the first triode is connected with the positive power end of the quasi-resonance control circuit, the positive power end of the quasi-resonance control circuit is connected with the base electrode of the first triode and the cathode of the first voltage regulator after being connected with the first resistor, the emitter of the first triode is connected with one end of the first capacitor and the collector of the second triode, and the other end of the first capacitor, the anode of the first voltage regulator, the anode of the second voltage regulator, one end of the second resistor and the collector of the third triode are connected with the negative power end of the quasi-resonance control circuit;
the control signal input end of the quasi-resonance control circuit is connected with the second capacitor and the third resistor in series and then is connected with the cathode of the second voltage stabilizing tube, the other end of the second resistor, the base electrode of the second triode and the base electrode of the third triode, and the emitter electrode of the second triode and the emitter electrode of the third triode are connected with the control signal output end of the quasi-resonance control circuit.
Preferably, the first switch tube and the second switch tube are N-channel MOS tubes or NPN bipolar transistor or insulated gate bipolar transistor.
Particularly, when the first switching tube and the second switching tube are N-channel MOS tubes, the control end of the first switching tube or the control end of the second switching tube is a gate, the voltage input end of the first switching tube or the voltage input end of the second switching tube is a drain, and the voltage output end of the first switching tube or the voltage output end of the second switching tube is a source.
Particularly, when the first switching tube and the second switching tube are NPN bipolar transistors, the control end of the first switching tube or the control end of the second switching tube is a base, the voltage input end of the first switching tube or the voltage input end of the second switching tube is a collector, and the voltage output end of the first switching tube or the voltage output end of the second switching tube is an emitter.
Particularly, when the first switching tube and the second switching tube are insulated gate bipolar transistors, the control end of the first switching tube or the control end of the second switching tube is a grid, the voltage input end of the first switching tube or the voltage input end of the second switching tube is a collector, and the voltage output end of the first switching tube or the voltage output end of the second switching tube is an emitter.
Preferably, the secondary rectifying tube is a rectifying diode or a field effect transistor rectifying module.
Particularly, when the secondary rectifying tube is a rectifying diode, the rectifying input end of the secondary rectifying tube is a cathode, and the rectifying output end of the secondary rectifying tube is an anode.
Preferably, the first triode and the second triode are NPN bipolar transistor, and the third triode is PNP bipolar transistor.
According to the secondary control quasi-resonant switching power supply converter provided by the invention, the original resonant capacitor is adjusted to the secondary end of the original transformer, the energy stored by the resonant capacitor is discharged to the power supply output end, and the capacitor voltage of the resonant capacitor resonates and rises from zero, so that the voltage of an original switching tube can also resonates and rises from zero, zero voltage turn-off of the original switching tube is realized, the switching loss of the switching power supply converter in the existing PWM control mode or PFM quasi-resonant switching control mode is greatly reduced, and the conversion efficiency of the converter is high;
meanwhile, a discharging loop of the resonance capacitor at the secondary end of the original transformer is completely blocked with an original switching tube at the primary end of the original transformer, so that soft switching is realized, and the phenomenon that the current flowing through the switching tube is overlarge due to the capacitive opening of the switching tube caused by the resonance capacitor in the prior art is avoided, thereby protecting the switching tube from being damaged;
and the capacitance voltage of the original resonance capacitor is resonated and increased from zero, the current of the secondary side of the transformer is naturally transited from small current flowing through the resonance capacitor to flowing through the secondary rectifying tube, the current change rate is low, the rectifying tube realizes soft switching on, the efficiency is high, no voltage spike exists, the EMI characteristic is good, and the working frequency of the switching power supply converter can be further improved, so that the power supply volume can be further reduced on the device, and the cost is reduced.
Drawings
FIG. 1 is a schematic circuit diagram of a prior art PFM quasi-resonant switching mode power converter of variable frequency provided by an embodiment of the present invention;
FIG. 2 is a voltage waveform diagram of two ends of the switching tube in FIG. 1 according to an embodiment of the present invention;
FIG. 3-1 is a circuit diagram of a secondary control quasi-resonant switching power converter according to an embodiment of the present invention;
fig. 3-2 is a circuit connection diagram of the first switching tube and the second switching tube in fig. 3-1, which are N-channel MOS tubes and the secondary rectifying tube is a rectifying diode according to an embodiment of the present invention;
fig. 4 is a circuit connection diagram of the quasi-resonant control circuit of fig. 3-1 provided by an embodiment of the present invention.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings in the embodiments of the present invention. The following components are only preferred embodiments, and do not limit the scope of the invention.
Referring to fig. 1, a schematic circuit diagram of a PFM quasi-resonant switching mode power converter with variable frequency in the prior art is provided according to an embodiment of the present invention. In this embodiment, in the flyback switching power converter in the prior art, no matter the PWM control mode with a fixed frequency and the PFM quasi-resonant control mode with a variable frequency, the turn-off loss of the switching tube of the high-frequency switch needs to be reduced, the rate of change of the voltage and the current needs to be reduced, and the rate of change of the voltage and the current is generally reduced mainly by using the parallel resonant capacitor Cr at two ends of the switching tube in fig. 1, or the turn-off loss is reduced by using the active clamp circuit, but the active clamp circuit is complex to control, and the invention does not further study.
As shown in fig. 1, a flyback switching power converter in the prior art is provided with a power input positive terminal vin+ connected with a power supply, a power input negative terminal Vin-and a power output positive terminal vout+ connected with a load, a switching controller KC, wherein the power input negative terminal Vin-is connected with a power negative terminal kc_pin1 of the switching controller KC and one end of a current detection resistor Rs, the other end of the current detection resistor Rs is connected with a switching current detection terminal kc_pin2 of the switching controller KC and a voltage output terminal kq1_pin1 of a switching tube KQ1, a control terminal kq1_pin2 of the switching tube KQ1 is connected with a switching control output terminal kc_pin2 of the switching controller KC, a resonance capacitor Cr is connected in parallel between a voltage output terminal kq1_pin1 and a voltage input terminal kq1_pin3 of the switching tube KQ1, the voltage input end KQ1_PIN3 of the switch tube KQ1 is also connected with the anode of the diode D1 and the opposite-name end of the primary winding T1_1 of the transformer T1 (the end with black dots in the figure is the opposite-name end without black dots), the cathode of the diode D1 is connected with the parallel RC circuit 1 and then is commonly connected with the opposite-name end of the primary winding T1_1 of the transformer T1 to be connected with the positive end vin+ of the power supply, the opposite-name end of the secondary winding T1_2 of the transformer T1 is connected with the rectifying diode Di in the positive direction and then is connected with the positive end Vout+ of the power supply output and the positive end of the polarity capacitor EC, and the negative end of the polarity capacitor EC and the opposite-name end of the secondary winding T1_2 of the transformer T1 are connected with the negative end Vout of the power supply output.
In the circuit shown in fig. 1, in conjunction with fig. 2, fig. 2 is a voltage waveform diagram of two ends of a switching tube KQ1 in fig. 1 provided by the embodiment of the invention, the power switching tube KQ1 is turned on at the bottom of the trough of a resonance voltage wave of two ends of a resonance capacitor Cr, so that partial turn-on loss can be reduced, but when the switching tube KQ1 is turned off, the voltage of two ends of the switching tube KQ1 rises rapidly from zero, and the current of the switching tube KQ1 drops rapidly from the maximum, so that an overlap area exists inevitably between the voltage and the current of two ends of the switching tube KQ1, and turn-off loss will be brought. After the switching tube KQ1 is turned off, the energy stored in the primary winding t1_1 of the transformer T1 is switched to the secondary winding t1_2, the flyback voltage of the secondary winding t1_2 of the transformer T1 rises rapidly until the flyback voltage is higher than the output voltage, at this time, the rectifying diode Di is turned on, in this process, the change rate of the induced current of the secondary winding t1_2 from the minimum to the maximum is very large, and the rectifying diode Di needs to recover from the turn-off to the turn-on, therefore, larger loss and peak voltage are brought about when the rectifying diode Di is turned on during high-frequency operation, so that the voltage stress of the diode Di is high, and the EMI (electromagnetic interference) characteristic of the power supply is poor.
The invention provides a secondary control quasi-resonance switching power supply converter, which is built into an internal circuit of the switching power supply converter by using an original switching controller KC, a switching tube KQ1, a resonance capacitor Cr, a transformer T1, a rectifier diode Di and a polarity capacitor EC, and an additional diode, a transformer, a switching tube and a quasi-resonance control circuit which is only composed of a resistor, a capacitor, a triode and a voltage regulator.
Referring to fig. 3-1, a circuit diagram of a secondary control quasi-resonant switching power converter according to an embodiment of the present invention is shown. In this embodiment, the secondary control quasi-resonant switching power converter retains the original power input positive terminal vin+ of the power supply, the power input negative terminal Vin-and the power output positive terminal vout+ of the load, the switching controller KC, the current detection resistor Rs, the resonant capacitor Cr, the transformer T1 (hereinafter, the first transformer T1), the rectifier diode Di (hereinafter, the secondary rectifier tube Di), the polarity capacitor EC, and the diode, the transformer, the switching tube KQ1 and the quasi-resonant control circuit 2 composed of only the resistor, the capacitor, the triode and the voltage regulator tube are newly built into the internal circuit of the switching power converter, and the connection relationship is as follows:
the power supply input negative terminal Vin-is connected with the power supply negative terminal KC_PIN1 of the switch controller KC and one end of the current detection resistor Rs, the other end of the current detection resistor Rs is connected with the switch current detection terminal KC_PIN2 of the switch controller KC and the voltage output terminal KQ1_PIN1 of the first switch tube KQ1, the control terminal KQ1_PIN2 of the first switch tube KQ1 is connected with the switch control output terminal KC_PIN3 of the switch controller KC, the voltage input terminal KQ1_PIN3 of the first switch tube KQ1 is connected with the synonym terminal of the primary winding T1_1 of the first transformer T1, and the homonymous terminal of the primary winding T1_1 of the first transformer T1 is connected with the power supply input positive terminal vin+;
the synonym end of the secondary winding t1_2 of the first transformer T1, the anode of the first diode D1, the power supply positive end 20 of the quasi-resonance control circuit 2, the cathode of the second diode D2, the positive end of the polar capacitor EC is connected with the power supply output positive end vout+, and the cathode of the first diode D1 is connected with the resonance capacitor Cr and then is connected with the synonym end of the secondary winding t1_2 of the first transformer T1, the rectification input end di_1 of the secondary rectifying tube Di and the control signal input end 21 of the quasi-resonance control circuit 2;
the power negative terminal 22 of the quasi-resonance control circuit 2, the rectification output end Di_2 of the secondary rectifying tube Di, the voltage output end KQ2_PIN1 of the second switching tube KQ2, the homonymous end of the secondary winding T2_1 of the second transformer T2, the negative terminal of the polar capacitor EC is connected with the power output negative terminal Vout-, and the control signal output end 23 of the quasi-resonance control circuit 2 is connected with the control end KQ2_PIN2 of the second switching tube KQ 2;
the voltage input end KQ2_PIN3 of the second switching tube KQ2 is connected with the synonym end of the primary winding T2_1 of the second transformer T2, the synonym end of the primary winding T2_1 of the second transformer T2 is connected with the cathode of the first diode D1, and the synonym end of the secondary winding T2_2 of the second transformer T2 is connected with the anode of the second diode D2.
It should be noted that, the first switching tube KQ1 and the second switching tube KQ2 may be an N-channel MOS tube or an NPN bipolar transistor or an insulated gate bipolar transistor.
When the first switching tube KQ1 and the second switching tube KQ2 are N-channel MOS tubes, the control end kq1_pin2 of the first switching tube KQ1 or the control end kq2_pin2 of the second switching tube KQ2 is a gate G, the voltage input end kq1_pin3 of the first switching tube KQ1 or the voltage input end kq2_pin3 of the second switching tube KQ2 is a drain D, and the voltage output end kq1_pin1 of the first switching tube KQ1 or the voltage output end kq2_pin1 of the second switching tube KQ2 is a source S.
When the first switching tube KQ1 and the second switching tube KQ2 are NPN bipolar transistors, the control end kq1_pin2 of the first switching tube KQ1 or the control end kq2_pin2 of the second switching tube KQ2 is a base B, the voltage input end kq1_pin3 of the first switching tube KQ1 or the voltage input end kq2_pin3 of the second switching tube KQ2 is a collector C, and the voltage output end kq1_pin1 of the first switching tube KQ1 or the voltage output end kq2_pin1 of the second switching tube KQ2 is an emitter E.
When the first switching tube KQ1 and the second switching tube KQ2 are insulated gate bipolar transistors, a control end kq1_pin2 of the first switching tube KQ1 or a control end kq2_pin2 of the second switching tube KQ2 is a gate G, a voltage input end kq1_pin3 of the first switching tube KQ1 or a voltage input end kq2_pin3 of the second switching tube KQ2 is a collector C, and a voltage output end kq1_pin1 of the first switching tube KQ1 or a voltage output end kq2_pin1 of the second switching tube KQ2 is an emitter E.
It should be further noted that, the secondary rectifying tube Di is a rectifying diode or a field-effect transistor rectifying module, and the field-effect transistor module is a circuit module with a rectifying input end di_1 and a rectifying output end di_2, which uses a field-effect transistor as a main device. When the secondary rectifying tube Di is a rectifying diode, the rectifying input end Di_1 of the secondary rectifying tube Di is a cathode, and the rectifying output end Di_2 of the secondary rectifying tube Di is an anode.
Referring to fig. 3-2 in combination with the above description, a circuit connection diagram of the first switching tube KQ2 and the second switching tube KQ2 in fig. 3-1 as N-channel MOS tubes and the secondary rectifying tube Di as rectifying diodes according to the embodiment of the present invention is shown. When the switching tube KQ1 is an N-channel MOS tube, an NPN bipolar transistor or an insulated gate bipolar transistor, the secondary rectifying tube Di is a rectifying diode, and the circuit connection diagrams under other five arrangements and combinations of the field effect transistor rectifying modules are easily obtained with reference to fig. 3-1, which is not illustrated herein.
It should be further noted that, referring to fig. 4, a circuit connection diagram of the quasi-resonant control circuit 2 in fig. 3-1 according to an embodiment of the present invention is provided. The quasi-resonance control circuit 2 is provided with a first triode Q1, a second triode Q2, a third triode Q3, a first resistor R1, a second resistor R2, a first voltage stabilizing tube Dv1, a second voltage stabilizing tube Dv2, a first capacitor C1 and a second capacitor C2;
the collector C of the first triode Q1 is connected with the power supply positive end 20 of the quasi-resonance control circuit 2, the power supply positive end 20 of the quasi-resonance control circuit 2 is connected with the base B of the first triode Q1 and the cathode of the first voltage stabilizing tube Dv1 after being connected with the first resistor R1, the emitter E of the first triode Q1 is connected with one end of the first capacitor C1 and the collector C of the second triode Q2, and the other end of the first capacitor C1, the anode of the first voltage stabilizing tube Dv1, the anode of the second voltage stabilizing tube Dv2, one end of the second resistor R2 and the collector C of the third triode Q3 are connected with the power supply negative end 22 of the quasi-resonance control circuit 2;
the control signal input end 21 of the quasi-resonant control circuit 2 is connected in series with the second capacitor C2 and the third resistor R3, and then connected with the cathode of the second voltage stabilizing tube Dv2, the other end of the second resistor R2, the base B of the second triode Q2 and the base B of the third triode Q3, and the emitter E of the second triode Q2 and the emitter E of the third triode Q3 are connected with the control signal output end 23 of the quasi-resonant control circuit 2.
The first triode Q1 and the second triode Q2 are NPN bipolar transistor, and the third triode Q3 is PNP bipolar transistor.
Referring to fig. 3-1 and fig. 4 again, in the secondary control quasi-resonant switching power supply converter provided by the embodiment of the invention, when the switching controller KC makes the first switching tube KQ1 be turned on, the primary winding t1_1 of the first transformer T1 stores energy, the induced voltage of the secondary winding t1_2 is positive at the same name end, the secondary rectifying tube Di is turned off in a reverse bias manner, the primary switch rising edge detection circuit and the delay circuit formed by the first capacitor C1, the second resistor R2, the third resistor R3 and the second voltage stabilizing tube Dv2 in the quasi-resonant control circuit 2 output drive the second switching tube KQ2 through the first triode Q1 and the second triode Q2, the resonant capacitor Cr and the primary winding t2_1 of the second transformer T2 resonate, the energy stored in the resonant capacitor Cr in the turn-off period of the first switching tube KQ1 is dumped into the second transformer T2, when the energy stored in the resonant capacitor Cr reaches the second switching tube KQ2 and the reset voltage reaches the positive end, and the energy is released from the second switching tube Q2 to the positive end, and the power supply voltage is released from the second switching tube Q2;
when the switch controller KC turns off the first switch tube KQ1, the induced voltage of the primary winding t1_1 of the first transformer T1 is positive, the first switch tube KQ1 is turned on in forward bias, the secondary winding t1_2 resonates with the resonance capacitor Cr, the terminal voltage of the resonance capacitor Cr resonates from zero to rise, and due to the mutual inductance of the first transformer T1, the voltage between the voltage input terminal kq1_pin3 and the voltage output terminal kq1_pin1 of the first switch tube KQ1 also rises, and at this time, the current of the voltage input terminal kq1_pin3 of the first switch tube KQ1 has fallen to zero, so that the first switch tube KQ1 is turned off close to zero loss. In the process that the terminal voltage of the resonance capacitor Cr rises from zero, the voltage at the moment is lower than the output voltage, the secondary rectifying tube Di is reversely biased and cut off, only small current flows to the resonance capacitor Cr from the secondary winding T1_2 of the first transformer T1, when the terminal voltage of the resonance capacitor Cr rises to exceed the output voltage, the secondary rectifying tube Di is naturally soft-opened, the opening loss is small, the current of the secondary winding T1_2 of the first transformer T1 begins to be switched to flow to the output, the change rate of the current is relatively low, voltage spikes at the two ends of the secondary rectifying tube Di are avoided, the stress is small, the EMI characteristic is relatively good, the working frequency of the whole switching power supply converter can be further improved, and therefore the power supply volume can be reduced, and the cost is reduced.
While the foregoing is directed to the preferred embodiments of the present invention, it will be appreciated by those skilled in the art that changes and modifications may be made without departing from the principles of the invention, such changes and modifications are also intended to be within the scope of the invention.

Claims (9)

1. The secondary control quasi-resonance switching power supply converter is provided with a power input positive terminal, a power input negative terminal, a power output positive terminal and a power output negative terminal which are connected with a power supply, and a switching controller, and is characterized in that the power input negative terminal is connected with the power negative terminal of the switching controller and one end of a current detection resistor, the other end of the current detection resistor is connected with a switching current detection end of the switching controller and a voltage output end of a first switching tube, a control end of the first switching tube is connected with a switching control output end of the switching controller, a voltage input end of the first switching tube is connected with a different-name end of a primary winding of a first transformer, and a same-name end of the primary winding of the first transformer is connected with the power input positive terminal;
the synonym end of the secondary winding of the first transformer, the anode of the first diode, the positive end of the power supply of the quasi-resonance control circuit, the cathode of the second diode and the positive end of the polar capacitor are connected with the positive end of the power supply output, the cathode of the first diode is connected with the resonance capacitor and then connected with the homonymous end of the secondary winding of the first transformer, the rectification input end of the secondary rectifying tube and the control signal input end of the quasi-resonance control circuit;
the power supply negative terminal of the quasi-resonance control circuit, the rectification output end of the secondary rectifying tube, the voltage output end of the second switching tube, the homonymous end of the secondary winding of the second transformer and the negative electrode end of the polar capacitor are connected with the power supply output negative terminal, and the control signal output end of the quasi-resonance control circuit is connected with the control end of the second switching tube;
the voltage input end of the second switching tube is connected with the synonym end of the primary winding of the second transformer, the synonym end of the primary winding of the second transformer is connected with the cathode of the first diode, and the synonym end of the secondary winding of the second transformer is connected with the anode of the second diode.
2. A secondary controlled quasi-resonant switching power converter in accordance with claim 1 wherein: the quasi-resonance control circuit is provided with a first triode, a second triode, a third triode, a first resistor, a second resistor, a third resistor, a first voltage stabilizing tube, a second voltage stabilizing tube, a first capacitor and a second capacitor;
the collector of the first triode is connected with the positive power end of the quasi-resonance control circuit, the positive power end of the quasi-resonance control circuit is connected with the base electrode of the first triode and the cathode of the first voltage regulator after being connected with the first resistor, the emitter of the first triode is connected with one end of the first capacitor and the collector of the second triode, and the other end of the first capacitor, the anode of the first voltage regulator, the anode of the second voltage regulator, one end of the second resistor and the collector of the third triode are connected with the negative power end of the quasi-resonance control circuit;
the control signal input end of the quasi-resonance control circuit is connected with the second capacitor and the third resistor in series and then is connected with the cathode of the second voltage stabilizing tube, the other end of the second resistor, the base electrode of the second triode and the base electrode of the third triode, and the emitter electrode of the second triode and the emitter electrode of the third triode are connected with the control signal output end of the quasi-resonance control circuit.
3. A secondary controlled quasi-resonant switching power converter in accordance with claim 1 wherein: the first switch tube and the second switch tube are N-channel MOS tubes or NPN bipolar transistor or insulated gate bipolar transistor.
4. A secondary controlled quasi-resonant switching power converter in accordance with claim 3 wherein: when the first switching tube and the second switching tube are N-channel MOS tubes, the control end of the first switching tube or the control end of the second switching tube is a grid, the voltage input end of the first switching tube or the voltage input end of the second switching tube is a drain, and the voltage output end of the first switching tube or the voltage output end of the second switching tube is a source.
5. A secondary controlled quasi-resonant switching power converter in accordance with claim 3 wherein: when the first switching tube and the second switching tube are NPN bipolar transistor, the control end of the first switching tube or the control end of the second switching tube is a base, the voltage input end of the first switching tube or the voltage input end of the second switching tube is a collector, and the voltage output end of the first switching tube or the voltage output end of the second switching tube is an emitter.
6. A secondary controlled quasi-resonant switching power converter in accordance with claim 3 wherein: when the first switching tube and the second switching tube are insulated gate bipolar transistors, the control end of the first switching tube or the control end of the second switching tube is a grid, the voltage input end of the first switching tube or the voltage input end of the second switching tube is a collector, and the voltage output end of the first switching tube or the voltage output end of the second switching tube is an emitter.
7. A secondary controlled quasi-resonant switching power converter in accordance with claim 1 wherein: the secondary rectifying tube is a rectifying diode or a field effect transistor rectifying module.
8. A secondary controlled quasi-resonant switching power converter in accordance with claim 7 wherein: when the secondary rectifying tube is a rectifying diode, the rectifying input end of the secondary rectifying tube is a cathode, and the rectifying output end of the secondary rectifying tube is an anode.
9. A secondary controlled quasi-resonant switching power converter in accordance with claim 2 wherein: the first triode and the second triode are NPN bipolar transistor, and the third triode is PNP bipolar transistor.
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JP2001161067A (en) * 1999-11-30 2001-06-12 Sony Corp Switching power supply circuit
CN101657960A (en) * 2007-03-29 2010-02-24 弗莱克斯电子有限责任公司 Only elementary constant voltage/constant current (CVCC) control in the quasi resonant convertor
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