CN106253324A - Photovoltaic micro inverter sync control device with decision-making device and control method thereof - Google Patents

Abstract

Photovoltaic micro inverter sync control device with decision-making device and control method thereof, belong to micro-capacitance sensor and control technical field.Control device, be characterized in, control device and also include that wireless standard time base circuit, the outfan of wireless standard time base circuit are connected with the communication interface of governor circuit.Control method, the signal when present invention utilizes the wireless second base clock controller in DSP master controller to generate global synchronization pair, being adjusted triangular wave clock signal, efficiently solving controller output pulse that controller clock frequency difference brought can not the problem of temporal synchronization；The present invention utilizes decision-making compensating controller to be estimated frequency and the phase error of feedback, the frequency of prediction inverter output voltage and the regulation trend of phase place, draw control strategy, realize the Fast synchronization of inverter output voltage, to realize the dynamic synchronization of the different photovoltaic DC-to-AC converter output voltages of distributed existence in micro-capacitance sensor, suppress instantaneous circulation, promote the stable and high effective operation of micro-capacitance sensor.

Description

Photovoltaic micro inverter sync control device with decision-making device and control method thereof

Technical field

The invention belongs to micro-capacitance sensor and control technical field, particularly relate to the photovoltaic micro inverter of a kind of band decision-making device Sync control device and control method thereof.

Background technology

In recent years, along with the development of photovoltaic industry, photovoltaic generation market scale constantly expands, and its cleaning is renewable, construction Advantage easy to maintenance gradually manifests.Photovoltaic energy is widely distributed, the most desirable, and photovoltaic power generation apparatus disperses on geographical position Distribution, inverter, as the interface of photovoltaic power generation apparatus, is connected on the spot with photovoltaic power generation apparatus, the most also presents distributed The feature existed.In order to provide the user with high-quality and high reliability electric energy, photovoltaic DC-to-AC converter is many to be connected by common bus, shape Become photovoltaic micro.

In photovoltaic micro, in order to realize reliable and stable distributed operation, need to control different photovoltaic DC-to-AC converter and exist Realize in the amplitude of output voltage, frequency and phase place synchronizing, otherwise may result in the generation of circulation.The existence of circulation not only can make Micro-source inverter can output capacity diminish, export the quality of power supply decline, shortening power electronic devices service life, sternly Also result in photovoltaic micro concussion during weight even to collapse.Therefore, it is achieved the distributed synchronization that photovoltaic DC-to-AC converter is good controls into For the research topic that photovoltaic micro control field is important.

Being conceived to this control target, Chinese scholars has carried out many research and has proposed different control methods, Such as master-slave control method, equity control mode, hierarchical control mode based on multi-agent technology, the independent controlling party of no control interconnection Formula etc..Wherein, the independent control mode of the no control interconnection with droop control as representative has been increasingly becoming main flow.

But these control methods remain problems: one is in actual motion control, and voltage is generally with pulse Form directly exports from inverter, but existing control method is all controlled using filtered voltage as controlling target, It is not concerned with the net synchronization capability of output voltage pulse, is the most just difficult to ensure that the temporal synchronization of output voltage；Two are as integrated electricity The development of road technique, the distributed director with DSP as core is extensively applied, but the existence of the oscillation frequency clock of each controller is poor Different, bring and trigger the problem that pulse is difficult to synchronize, trigger the asynchronous of pulse and cause output voltage pulse can not synchronize, to ring The Instantaneous Control of stream brings challenge；Three is that the most commonly used droop control itself exists to sacrifice voltage and FREQUENCY CONTROL Precision realizes the feature of power distribution, and the control accuracy of voltage magnitude and frequency is limited, it is difficult to realize the most effective of circulation Control.

Summary of the invention

The problem existed for prior art, the present invention provides the photovoltaic micro inverter of a kind of band decision-making device to synchronize control Device processed and control method thereof.The present invention utilizes the wireless second base clock controller in DSP master controller to generate global synchronization pair Time signal, triangular wave clock signal is adjusted, efficiently solves the controller that controller clock frequency difference brought defeated Going out pulse can not the problem of temporal synchronization；It addition, the present invention utilizes the decision-making compensating controller in DSP master controller to feedback Frequency and phase error are estimated, it was predicted that the regulation trend of the frequency of inverter output voltage and the phase place of output voltage, Go out optimization, quick control strategy, it is achieved the Fast synchronization of inverter output voltage, to realize distributed existence in micro-capacitance sensor The dynamic synchronization of different photovoltaic DC-to-AC converter output voltages, suppresses instantaneous circulation, promotes the stable and high effective operation of micro-capacitance sensor.

To achieve these goals, the present invention adopts the following technical scheme that the photovoltaic micro inversion of a kind of band decision-making device Device sync control device, including photo-voltaic power supply, photovoltaic DC-to-AC converter main circuit, cutting-in control switch, voltage sensor, current sense Device, PWM drive circuit and governor circuit；The outfan of described photo-voltaic power supply is connected with the input of photovoltaic DC-to-AC converter main circuit Connecing, outfan one tunnel of photovoltaic DC-to-AC converter main circuit is connected with public exchange bus through cutting-in control switch, and another road is with negative Load is connected；The input of described voltage sensor and current sensor outfan with photovoltaic DC-to-AC converter main circuit respectively is connected Connect, the outfan of voltage sensor and current sensor respectively with the voltage sampling circuit of governor circuit and current sampling circuit Input is connected, and the outfan of described governor circuit is connected with the input of PWM drive circuit, PWM drive circuit defeated Go out end to be connected with the control end of photovoltaic DC-to-AC converter main circuit；Being characterized in, described control device also includes base during wireless standard Circuit, the described outfan of wireless standard time base circuit is connected with the communication interface of governor circuit.

Described wireless standard time base circuit includes wireless signal receiving antenna, coax signal cable, reception of wireless signals electricity Road and level process circuit, and the outfan of wireless signal receiving antenna is defeated through coax signal cable and wireless signal receiving circuit Entering end to be connected, the input that the outfan of wireless signal receiving circuit processes circuit with level is connected, and level processes circuit Outfan as the outfan of wireless standard time base circuit.

Described governor circuit includes voltage sampling circuit, current sampling circuit, protection circuit, simulation I/O circuit, numeral I/ O circuit, RS232 communicating circuit, alarm device and DSP, outfan one tunnel of described voltage sampling circuit and current sampling circuit Being connected with the A/D sampling module of DSP respectively, another road is connected with the input of protection circuit respectively, protection circuit defeated Go out end to be connected with the simulation I/O interface of DSP through simulation I/O circuit；The input of described RS232 communicating circuit and numeral I/O The input of circuit as the communication interface of governor circuit, the SCI communication interface phase of the outfan of RS232 communicating circuit and DSP Connecting, the outfan of numeral I/O circuit is connected with alarm device, the communication interface of numeral I/O circuit and the digital I/O of DSP Interface is connected, and the outfan of the SPWM generation module of DSP is as the outfan of governor circuit.

The control method of the photovoltaic micro inverter sync control device of described band decision-making device, comprises the steps:

Step one: utilize voltage sensor to gather the three-phase output voltage of photovoltaic DC-to-AC converter main circuit outfan, and transmit To the voltage sampling circuit of governor circuit；Utilize current sensor to gather the three-phase of photovoltaic DC-to-AC converter main circuit outfan simultaneously Inductive current and three-phase output electric current, and transmit to the current sampling circuit of governor circuit；

Step 2: the UTC time signal received and pps pulse per second signal are sent to governor circuit by wireless standard time base circuit In, governor circuit UTC time signal, pps pulse per second signal, three-phase output voltage, three pole reactor electric current and three-phase to receiving Output electric current process, generate PWM trigger signal, and PWM is triggered signal send to PWM drive circuit, it specifically includes Following steps:

Step A: utilize voltage sampling circuit three-phase output voltage to be filtered and amplitude transformation, obtain three phase samplers defeated Go out voltage and send to protection circuit and DSP；Utilize current sampling circuit that three pole reactor electric current and three-phase are exported electric current to enter Row signal type is changed, and is filtered and amplitude transformation, obtains three phase sampler inductive currents and three-phase sampled output current, and Send to protection circuit and DSP；

Step B: protection circuit receives three-phase sampling and outputting voltage, three phase sampler inductive currents and three-phase sampled output current And process, respectively obtain overvoltage protection signal and overcurrent protection signal, overvoltage protection signal and overcurrent protection Signal sends to DSP after simulation I/O processing of circuit；The DSP overvoltage protection signal to receiving and overcurrent protection letter Number process, it is judged that whether it meets protection act condition: when meeting protection act condition, DSP output pulse blocking letter Number, block PWM triggers signal, and when being unsatisfactory for protection act condition, DSP does not export pulse blocking signal, and normal output PWM touches Signal；

Meanwhile, DSP receives three-phase sampling and outputting voltage, three phase sampler inductive currents and three-phase sampled output current, and leads to The A/D sampling module crossing DSP therein processes, and correspondence obtains output voltage sampled value, inductive current sampled value respectively With output current sampling data, then carry out abc/dq coordinate transform, obtain the biphase output voltage under biphase rotating coordinate system Sampled value, biphase inductive current sampled value and biphase output current sampling data；

Step C: by the biphase output voltage sampled value under biphase rotating coordinate system and biphase output current sampling data meter Instantaneous active power and instantaneous reactive power, instantaneous active power and the instantaneous reactive power of calculating photovoltaic DC-to-AC converter output determine After, obtain actual active power of output and actual output reactive power through low pass filter filtering；

Step D: by the biphase output voltage sampled value under biphase rotating coordinate system and biphase output current sampling data meter Calculate photovoltaic DC-to-AC converter output voltage frequency and output voltage phase place；

Step E: UTC time signal is sent to RS232 communicating circuit by wireless standard time base circuit, RS232 communication electricity After road carries out level conversion to UTC time signal, send the SCI communication interface to DSP；Wireless standard time base circuit is by pulse per second (PPS) Signal sends to numeral I/O circuit, and pps pulse per second signal is filtered and after integer process, sends to DSP by numeral I/O circuit Digital I/O interface；

Step F: by the wireless second base clock controller in DSP master controller to UTC time signal, pps pulse per second signal and Real-time clock frequency of oscillation value calculates, and generates global synchronization frequency, revised triangular wave output frequency and revised Triangular wave output phase place；

Step G: according to the overall situation determined in output voltage frequency, output voltage phase place and step F of photovoltaic DC-to-AC converter The actual active power of output determined in synchronizing frequency and step C and actual output reactive power, determining in DSP master controller Plan compensating controller calculates and obtains output voltage frequency reference value and output voltage amplitude reference value；

Step H: according to the output voltage frequency reference value determined in step G and output voltage amplitude reference value, Jing Guo electricity It is pressed into acquisition output voltage reference value；

Step I: by poor to output voltage reference value and biphase output voltage sampled value, it is thus achieved that voltage controller set-point, And by the voltage controller in voltage controller set-point input to DSP master controller, obtain after voltage controller processes Output current reference value；

Step J: by poor with biphase output current sampling data for output current reference value, it is thus achieved that current controller set-point, And by the current controller in current controller set-point input to DSP master controller, it is thus achieved that command voltage reference value；

Step K: obtain PWM according to command voltage reference value and revised triangular wave output frequency and trigger signal, and will PWM triggers signal and sends to PWM drive circuit；

Step 3: by PWM drive circuit, PWM is triggered signal and carry out level conversion, it is thus achieved that start pulse signal is concurrent Deliver to, in photovoltaic DC-to-AC converter main circuit, control the break-make of its switching tube, it is achieved photovoltaic DC-to-AC converter output voltage is inverse with other photovoltaics Become the synchronization of device output voltage.

Described in step F by the wireless second base clock controller in DSP master controller to UTC time signal, second arteries and veins Rush signal and real-time clock frequency of oscillation value calculate, generate global synchronization frequency, revised triangular wave output frequency and Revised triangular wave output phase place, it specifically comprises the following steps that

Step f1: utilize UTC time signal and pps pulse per second signal, it is thus achieved that global synchronization frequency signal, clock frequency are measured Signal and triangular wave phase reset signal；

Step f2: utilize global synchronization frequency signal to determine global synchronization frequency, and it is true to utilize clock frequency to measure signal Timing clock frequency of oscillation value of calculation, described oscillation frequency clock value of calculation is determined by following formula:

${\mathrm{\ω}}_{cry}=\frac{\underset{i=1}{\overset{n}{\mathrm{\Σ}}}{\mathrm{\ω}}_{cryo}}{n}---\left(1\right)$

In formula, ω_cryoFor real-time clock frequency of oscillation value；ω_cryFor the clock oscillation frequency obtained after average value filtering Rate value of calculation；I is the variable representing pulse per second (PPS) number, i ∈ [1, n]；

Step f3: given oscillation frequency clock rated value and triangular wave frequency rated value, and specified with oscillation frequency clock Value, divided by triangular wave frequency rated value, obtains triangular wave clock division rated value, is shown below:

$M_0=\frac{{\mathrm{\ω}}_{cry}^{*}}{{\mathrm{\ω}}_{tri}^{*}}---\left(2\right)$

In formula, M₀For triangular wave clock division rated value；For oscillation frequency clock rated value；For triangular wave frequency Rated value；

Step f4: by poor to oscillation frequency clock rated value and the oscillation frequency clock value of calculation obtained, obtain clock Oscillation frequency shifts amount, then be multiplied by deviation ratio and obtain triangular wave clock division value correction；By specified for triangular wave clock division Value is poor with the triangular wave clock division value correction obtained, and obtains revised triangular wave clock division value, such as following formula institute Show:

$M^{*}=M_0-k({\mathrm{\ω}}_{cry}^{*}-{\mathrm{\ω}}_{cry})---\left(3\right)$

In formula, M₀For triangular wave clock division rated value；M^*For revised triangular wave clock division value；Shake for clock Swing frequency rated value；K is deviation ratio；ω_cryFor the oscillation frequency clock value of calculation obtained after average value filtering；

Step f5: by the oscillation frequency clock value of calculation that obtained divided by revised triangular wave clock division value, obtain Revised triangular wave output frequency；

Step f6: be integrated revised triangular wave output frequency, obtains triangular wave original real-time phase value；By institute The triangular wave original real-time phase value obtained processes through triangular wave Phase synchronization control function, obtains the output of revised triangular wave Phase place.

Triangular wave Phase synchronization control function described in step f6, is shown below:

θ_tri=sgn (s_TPR)·θ_trio (4)

In formula, θ_trioFor triangular wave original real-time phase value；s_TPRFor triangular wave phase reset signal；θ_triFor revised Triangular wave output phase place；sgn(s_TPR) it is with s_TPRSign function for variable.

The output voltage frequency according to photovoltaic DC-to-AC converter described in step G, output voltage phase place and step F determine Global synchronization frequency and step C in the actual active power of output that determines and actual output reactive power, through decision-making compensation Controller calculates and obtains output voltage frequency reference value and output voltage amplitude reference value, and it specifically comprises the following steps that

Step g1: be integrated global synchronization frequency, obtains global synchronization phase place；

Step g2: by poor for the output voltage frequency of global synchronization frequency Yu photovoltaic DC-to-AC converter, obtain output voltage frequency Offset Δ e_ω, by poor for the output voltage phase place of global synchronization phase place Yu photovoltaic DC-to-AC converter, obtain output voltage phase offset Amount Δ e_θ；

Step g3: preset synchronization controls threshold value and security control threshold value, and described Synchronization Control threshold value includes sine wave freuqency Difference is the upper limit threshold Δ e of zero_ωminWith lower threshold-Δ e_ωmin, sine wave phase difference be zero upper limit threshold Δ e_θminUnder with Limit threshold value-Δ e_θmin；Described security control threshold value includes sine wave freuqency difference upper limit threshold Δ e during stable operation_ωmaxAnd lower limit Threshold value-Δ e_ωmax, stable operation time sine wave phase difference upper limit threshold Δ e_θmaxWith lower threshold-Δ e_θmax；

Step g4: according to output voltage frequency side-play amount, output voltage phase pushing figure and Synchronization Control threshold value and peace Entirely control threshold value, determine that the functional value of valuation functions, described valuation functions include frequency estimation function, phase evaluation function, phase Position bit switch valuation functions and step-out Forewarn evaluation function, as follows:

$\left\{\begin{array}{c}{s}_{\mathrm{\ω}}=g({\mathrm{\Δe}}_{\mathrm{\ω}},{\mathrm{\Δe}}_{\mathrm{\θ}})\\ s_{\mathrm{\θ}}=h({\mathrm{\Δe}}_{\mathrm{\ω}},{\mathrm{\Δe}}_{\mathrm{\θ}})\\ s_{SPR}=\mathrm{sgn}\left({\mathrm{\Δe}}_{\mathrm{\θ}}\right)\\ s_{warn}=\mathrm{sgn}\left({\mathrm{\Δe}}_{\mathrm{\ω}}\right)*f\left(t\right)\end{array}\right.---\left(5\right)$

In formula, s_ωThe entitled g of representative function, with Δ e_ωWith Δ e_θFrequency estimation function for variable；s_θThe entitled h of representative function, With Δ e_ωWith Δ e_θPhase evaluation function for variable；s_SPRFor phase position bit switch valuation functions, s_warnFor step-out Forewarn evaluation Function, sgn is sign function, and f (t) represents the function with time t as variable；

The Decision Evaluation method of described valuation functions, specifically includes following steps:

Step X1: according to output voltage frequency offset Δ e_ω, sine wave freuqency in preset Synchronization Control threshold value poor It is the upper limit threshold Δ e of zero_ωminWith lower threshold-Δ e_ωminAnd it is sinusoidal wave during stable operation in preset security control threshold value Difference on the frequency upper limit threshold Δ e_ωmaxWith lower threshold-Δ e_ωmax, it is judged that FREQUENCY CONTROL state now:

If | Δ e_ω| ＜ Δ e_ωmin, then output voltage frequency side-play amount is less than Synchronization Control threshold value, and sine wave freuqency synchronizes, The now FREQUENCY CONTROL state that defines is state one；

If Δ e_ωmin＜ Δ e_ω＜ Δ c_ωmax, then output voltage frequency side-play amount is more than Synchronization Control threshold value but not less than peace Entirely controlling threshold value, the frequency shift (FS) of output voltage is forward migration, and the now FREQUENCY CONTROL state that defines is state two；

If-Δ e_ωmax＜ Δ e_ω＜-Δ e_ωmin, then output voltage frequency side-play amount exceed Synchronization Control threshold value but not less than Security control threshold value, the frequency shift (FS) of output voltage is negative offset, and the now FREQUENCY CONTROL state that defines is state three；

If Δ e_ω＞ Δ e_ωmax, then output voltage frequency side-play amount exceedes security control threshold value, and the frequency of output voltage is inclined Moving is forward migration, and the now FREQUENCY CONTROL state that defines is state four；

If Δ e_ω＜-Δ e_ωmax, then output voltage frequency side-play amount exceedes security control threshold value, and the frequency of output voltage is inclined Moving is negative offset, and the now FREQUENCY CONTROL state that defines is state five；

Step X2: according to the FREQUENCY CONTROL state drawn in step X1, and output voltage phase pushing figure Δ e_θ, preset Synchronization Control threshold value in the upper limit threshold Δ e that sine wave phase difference is zero_θminWith lower threshold-Δ e_θmin, preset safety Control sine wave phase difference upper limit threshold Δ e during the stable operation in threshold value_θmaxWith lower threshold-Δ e_θmax, through selecting assessment Determine the functional value of valuation functions:

If FREQUENCY CONTROL state is state one, then:

If | Δ e_θ| ＜ Δ e_θmin, then output voltage phase pushing figure is less than Synchronization Control threshold value, and the frequency of output voltage is described Rate synchronizes, and the phase place of output voltage also synchronizes, and is not required to start any control, and the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=0；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, then output voltage phase pushing figure is more than Synchronization Control threshold value but not less than peace Entirely controlling threshold value, the phase offset of output voltage is forward migration, and the Frequency Synchronization of output voltage is described, the phase place of output voltage In advance, needing to carry out phase controlling, the functional value of valuation functions is: s_θ=1, s_ω=0, s_SPR=0, s_warn=0；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, then output voltage phase pushing figure exceed Synchronization Control threshold value but not less than Security control threshold value, the phase offset of output voltage is negative offset, and the Frequency Synchronization of output voltage is described, the phase of output voltage After steric retardation, needing to carry out phase controlling, the functional value of valuation functions is: s_θ=1, s_ω=0, s_SPR=0, s_warn=0；

If | Δ e_θ| ＞ Δ e_θmax, then output voltage phase pushing figure exceedes security control threshold value, and the frequency of output voltage is described Rate synchronizes, the serious step-out of phase place of output voltage, needs to carry out phase position bit switch control, and i.e. sinusoidal wave starting point controls again Activating and control, the functional value of valuation functions is: s_θ=0, s ω=0, s_SPR=1, s_warn=0；

If FREQUENCY CONTROL state is state two, then:

If | Δ e_θ| ＜ Δ e_θmin, then output voltage phase pushing figure is less than Synchronization Control threshold value, and the frequency of output voltage is described Rate increases, and the Phase synchronization of output voltage needs to carry out FREQUENCY CONTROL, and the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR =0, s_warn=0；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, then output voltage phase pushing figure is more than Synchronization Control threshold value but not less than peace Entirely controlling threshold value, the phase offset of output voltage is forward migration, illustrates that the frequency of output voltage increases, the phase place of output voltage In advance, phase place can be adjusted by the frequency of increase, is not required to start any control, and the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=0:

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, then output voltage phase pushing figure exceed Synchronization Control threshold value but not less than Security control threshold value, the phase offset of output voltage is negative offset, illustrates that the frequency of output voltage increases, the phase of output voltage After steric retardation, the frequency of increase can make phase contrast continue to increase, and needs to carry out FREQUENCY CONTROL, and the functional value of valuation functions is: s_θ= 0, s_ω=1, s_SPR=0, s_warn=0；

If | Δ e_θ| ＞ Δ e_θmax, then output voltage phase pushing figure exceedes security control threshold value, and the frequency of output voltage is described Rate increases, the serious step-out of phase place of output voltage, now needs to carry out FREQUENCY CONTROL and phase position bit switch controls, valuation functions Functional value be: s_θ=0, s_ω=1, s_SPR=1, s_warn=0；

If FREQUENCY CONTROL state is state three, then:

If | Δ e_θ| ＜ Δ e_θmin, then output voltage phase pushing figure is less than Synchronization Control threshold value, and the frequency of output voltage is described Rate reduces, and the Phase synchronization of output voltage needs to carry out FREQUENCY CONTROL, and the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR =0, s_warn=0；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, then output voltage phase pushing figure is more than Synchronization Control threshold value but not less than peace Entirely controlling threshold value, the phase offset of output voltage is forward migration, illustrates that the frequency of output voltage reduces, the phase place of output voltage In advance, the frequency of reduction can make phase contrast continue to increase, and needs to carry out FREQUENCY CONTROL, and the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=0；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, then output voltage phase pushing figure exceed Synchronization Control threshold value but not less than Security control threshold value, the phase offset of output voltage is negative offset, illustrates that the frequency of output voltage reduces, the phase of output voltage After steric retardation, phase place can be adjusted by the frequency of reduction, is not required to start any control, and the functional value of valuation functions is: s_θ= 0, s_ω=0, s_SPR=0, s_warn=0:

If | Δ e_θ| ＞ Δ e_θmax, then output voltage phase pushing figure exceedes security control threshold value, and the frequency of output voltage is described Rate reduces, the serious step-out of phase place of output voltage, now needs to carry out FREQUENCY CONTROL and phase position bit switch controls, valuation functions Functional value be: s_θ=0, s_ω=1, s_SPR=1, s_warn=0；

If FREQUENCY CONTROL state is state four, then:

If | Δ e_θ| ＜ Δ e_θmin, then output voltage phase pushing figure is less than Synchronization Control threshold value, and the frequency of output voltage is described Rate increases, and exceedes security control threshold value, the Phase synchronization of output voltage, needs to carry out FREQUENCY CONTROL and step-out early warning controls, The functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, then output voltage phase pushing figure is more than Synchronization Control threshold value but not less than peace Entirely controlling threshold value, the phase offset of output voltage is forward migration, illustrates that the frequency of output voltage increases, and exceedes security control Threshold value, the phase place of output voltage is advanced, and phase place can be adjusted by the frequency of increase, affects for exclusive PCR, the most only enters Row step-out early warning controls, and the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=1；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, then output voltage phase pushing figure exceed Synchronization Control threshold value but not less than Security control threshold value, the phase offset of output voltage is negative offset, illustrates that the frequency of output voltage increases, and exceedes safe control Threshold value processed, the delayed phase of output voltage, the frequency of increase can make phase contrast continue to increase, need to carry out FREQUENCY CONTROL and step-out Early warning controls, and the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1；

If | Δ e_θ| ＞ Δ e_θmax, then output voltage phase pushing figure exceedes security control threshold value, and the frequency of output voltage is described Rate increases, and exceedes security control threshold value, and the serious step-out of phase place of output voltage now needs to carry out FREQUENCY CONTROL, phase position Bit switch controls and step-out early warning controls, and the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=1, s_warn=1；

If FREQUENCY CONTROL state is state five, then:

If | Δ e_θ| ＜ Δ e_θmin, then output voltage phase pushing figure is less than Synchronization Control threshold value, and the frequency of output voltage is described Rate reduces, and exceedes security control threshold value, the Phase synchronization of output voltage, needs to carry out FREQUENCY CONTROL and step-out early warning controls, The functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, then output voltage phase pushing figure is more than Synchronization Control threshold value but not less than peace Entirely controlling threshold value, the phase offset of output voltage is forward migration, illustrates that the frequency of output voltage reduces, and exceedes security control Threshold value, the phase place of output voltage is advanced, and the frequency of reduction can make phase contrast continue to increase, and needs to carry out FREQUENCY CONTROL and step-out is pre- Alert control, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, then output voltage phase pushing figure exceed Synchronization Control threshold value but not less than Security control threshold value, the phase offset of output voltage is negative offset, illustrates that the frequency of output voltage reduces, and exceedes safe control Threshold value processed, the delayed phase of output voltage, phase place can be adjusted by the frequency of reduction, affects for exclusive PCR, now only Carrying out step-out early warning control, the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=1；

If | Δ e_θ| ＞ Δ e_θmax, then output voltage phase pushing figure exceedes security control threshold value, and the frequency of output voltage is described Rate reduces, and exceedes security control threshold value, and the serious step-out of phase place of output voltage now needs to carry out FREQUENCY CONTROL, phase position Bit switch controls and step-out early warning controls, and the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=1, s_warn=1；

Step X3: utilize the output voltage frequency side-play amount obtained, uses PI to control to obtain amount of frequency compensation initial value；

Step X4: set meritorious sagging coefficient according to equipment energy characteristic, and determine output voltage frequency reference value, described output Electric voltage frequency reference value is determined by following formula:

ω_ref=(ω^*+s_ω·Δω)-k_p·P (6)

In formula, ω_refFor output voltage frequency reference value, ω^*For global synchronization frequency, k_pFor meritorious sagging coefficient, P is real Border active power of output, Δ ω is amount of frequency compensation initial value, s_ωFunctional value for frequency estimation function；

Step X5: determine sinusoidal wave real-time phase value, completes the adjustment to phase place, described sinusoidal wave real-time phase value by under Formula determines:

θ=(1-s_SPR)(θ_p+s_θ*Δe_θ) (7)

In formula, θ is sinusoidal wave real-time phase value；θ_pFor phase place intermediate value；s_SPRLetter for phase position bit switch valuation functions Numerical value；s_θFunctional value for phase evaluation function；Δe_θFor output voltage phase pushing figure；

Step X6: set output voltage amplitude rated value and idle sagging coefficient according to equipment energy characteristic, by output voltage width Value rated value and idle sagging coefficient and actual output reactive power long-pending poor, obtains output voltage amplitude reference value.

Beneficial effects of the present invention:

The signal when present invention utilizes the wireless second base clock controller in DSP master controller to generate global synchronization pair, to three Angle ripple clock signal is adjusted, and efficiently solving controller output pulse that controller clock frequency difference brought can not wink Time synchronize problem；It addition, the present invention utilizes the decision-making compensating controller in DSP master controller to miss frequency and the phase place of feedback Difference is estimated, it was predicted that the regulation trend of the frequency of inverter output voltage and the phase place of output voltage, draws optimizations, quick Control strategy, it is achieved the Fast synchronization of inverter output voltage, to realize the different photovoltaic inversion of distributed existence in micro-capacitance sensor The dynamic synchronization of device output voltage, suppresses instantaneous circulation, promotes the stable and high effective operation of micro-capacitance sensor.

The invention enables each distributed photovoltaic inverter can either realize the distribution of accurate power, ensure that again photovoltaic is inverse Become the global synchronization of device output voltage, but also have the advantage that

(1) present invention sets Synchronization Control threshold value, decreases unnecessary regulation process；

(2) present invention sets security control threshold value, improves the reliability and stability that photovoltaic micro controls；

(3) present invention combines the regulated variable that is mutually related (output voltage frequency side-play amount and output voltage phase place is inclined Shifting amount), and predict regulation trend, finally draw control strategy more rapid, that optimize；

(4) invention introduces step-out early warning to control, the impact of recognizable bursty interference, improve the appearance of photovoltaic micro Wrong ability；

(5) present invention is by realizing triangular wave frequency and the synchronization of triangular wave phase place, eliminates controller oscillation frequency rate variance The different adverse effect to synchronizing process, provides guarantee for realizing the Instantaneous Control of circulation.

Finally, under the effect of the present invention, the photovoltaic DC-to-AC converter output voltage pulse of each distributed operation has reached to synchronize, Achieve the Instantaneous Control to circulation, promote stability and high efficiency and the reliability service of micro-capacitance sensor.

Accompanying drawing explanation

Fig. 1 is the schematic block circuit diagram of one embodiment of the present of invention；

Fig. 2 is the photovoltaic DC-to-AC converter main circuit of one embodiment of the present of invention and former with the circuit of its outfan connected component Reason figure；

Fig. 3 is the circuit theory diagrams of the wireless standard time base circuit of one embodiment of the present of invention；

Fig. 4 is the circuit theory diagrams of the voltage sampling circuit of one embodiment of the present of invention；

Fig. 5 is the circuit theory diagrams of the current sampling circuit of one embodiment of the present of invention；

Fig. 6 is the circuit theory diagrams of the protection circuit of one embodiment of the present of invention；

Fig. 7 is the circuit theory diagrams of the RS232 communicating circuit of one embodiment of the present of invention；

Fig. 8 is the circuit theory diagrams of the digital I/O circuit of one embodiment of the present of invention；

Fig. 9 is the circuit theory diagrams of the simulation I/O circuit of one embodiment of the present of invention；

Figure 10 is the circuit theory diagrams of the DSP of one embodiment of the present of invention；

Figure 11 is the circuit theory diagrams of the PWM drive circuit of one embodiment of the present of invention；

Figure 12 is the flow chart of an embodiment of the control method of the present invention；

Figure 13 is the structure chart of the embodiment controlling device of the present invention；

Figure 14 is the program flow diagram of the wireless second base clock controller of one embodiment of the present of invention；

Figure 15 is the structure chart of the wireless second base clock controller of one embodiment of the present of invention；

Figure 16 is the program flow diagram of the decision-making compensating controller of one embodiment of the present of invention；

Figure 17 is the structure chart of the decision-making compensating controller of one embodiment of the present of invention；

Figure 18 is the oscillogram (before wave filter) after the inverter parallel output impulsive synchronization of one embodiment of the present of invention；

Figure 19 be one embodiment of the present of invention inverter output impulsive synchronization after the oscillogram (wave filter of partial enlargement Before)；

In figure: 1-pulse control circuit, 2-governor circuit, 3 wireless standard time base circuits, 4-DSP.

Detailed description of the invention

The present invention is described in further detail with specific embodiment below in conjunction with the accompanying drawings.

As it is shown in figure 1, the photovoltaic micro inverter sync control device of a kind of band decision-making device, including photo-voltaic power supply, light Volt converter main circuit, cutting-in control switch, voltage sensor, current sensor, PWM drive circuit and governor circuit 2；Described The outfan of photo-voltaic power supply is connected with the input of photovoltaic DC-to-AC converter main circuit, outfan one tunnel of photovoltaic DC-to-AC converter main circuit Being connected with public exchange bus through cutting-in control switch, another road is connected with load；Described voltage sensor and electric current pass The input of sensor outfan with photovoltaic DC-to-AC converter main circuit respectively is connected, voltage sensor and the output of current sensor End is connected with the voltage sampling circuit of governor circuit 2 and the input of current sampling circuit respectively, described governor circuit 2 defeated Go out end to be connected with the input of PWM drive circuit, the outfan of PWM drive circuit and the control end of photovoltaic DC-to-AC converter main circuit It is connected；Described control device also includes wireless standard time base circuit 3, the outfan of described wireless standard time base circuit 3 and master The communication interface of control circuit 2 is connected, and wireless standard time base circuit 3 and governor circuit 2 collectively form pulse control circuit 1.

Described wireless standard time base circuit 3 includes wireless signal receiving antenna, coax signal cable, reception of wireless signals electricity Road and level process circuit, and the outfan of wireless signal receiving antenna is defeated through coax signal cable and wireless signal receiving circuit Entering end to be connected, the input that the outfan of wireless signal receiving circuit processes circuit with level is connected, and level processes circuit Outfan as the outfan of wireless standard time base circuit 3.

Described governor circuit 2 includes voltage sampling circuit, current sampling circuit, protection circuit, simulation I/O circuit, numeral I/O circuit, RS232 communicating circuit, alarm device and DSP, the outfan one of described voltage sampling circuit and current sampling circuit Road is connected with the A/D sampling module of DSP respectively, and another road is connected with the input of protection circuit respectively, protection circuit Outfan is connected with the simulation I/O interface of DSP through simulation I/O circuit；The input of described RS232 communicating circuit and numeral I/ The input of O circuit is as the SCI communication interface of the communication interface of governor circuit 2, the outfan of RS232 communicating circuit and DSP Being connected, the outfan of numeral I/O circuit is connected with alarm device, the communication interface of numeral I/O circuit and the digital I/ of DSP O Interface is connected, and the outfan of the SPWM generation module of DSP is as the outfan of governor circuit 2.

The photo-voltaic power supply of the present invention converts the solar into direct current energy, provides electric energy, the sun for whole photovoltaic micro Energy cell panel is the important component part of photo-voltaic power supply, and the present invention has selected current general solar panel.

The circuit theory diagrams of the photovoltaic DC-to-AC converter main circuit in the present embodiment, as in figure 2 it is shown, by DC bus capacitor C_dc、S₁ To S₆IGBT switch module, filter inductance L_fWith filter capacitor C_fComposition；Wherein, u_dcFor DC voltage value, i_la、i_lb、i_lc For inductor current value, i_oa、i_ob、i_ocFor output current value, u_oa、u_ob、u_ocFor output voltage values.In the present embodiment, photovoltaic inversion The outfan of device main circuit connects local load, and by Guan Bi cutting-in control switch, electric energy is delivered to public exchange bus, real The parallel running of existing distributed inverter.Pulse control circuit 1 needs to export driving pulse according to parallel Operation Control, controls six The break-make of individual switching tube, output meets the electric energy of needs.Cutting-in control switch in the present embodiment uses STS-1116 type general Cutting-in control switchs, and the model that voltage sensor uses is PE4113-M, and the model that current sensor uses is LT108-S7.

The circuit theory diagrams of the wireless standard time base circuit 3 in the present embodiment, as it is shown on figure 3, this circuit includes wireless communication Number reception antenna, coax signal cable, wireless signal receiving circuit and level process circuit.The effect of this circuit is by wireless Signal receiving antenna receives Wireless clock signal, transmits signals to wireless signal receiving circuit through coax signal cable and carries out letter Number processing, the signal of output sends and processes circuit conversion to level is the signal that governor circuit 2 can receive.The nothing of the present embodiment Line signal receiving circuit is mainly made up of general GPS.The circuit theory diagrams of the voltage sampling circuit in the present embodiment, As shown in Figure 4；The effect of voltage sampling circuit be the inverter three-phase output voltage that voltage sensor is collected be filtered, Amplify and voltage increase, be converted to DSP and the manageable signal of protection circuit.

The circuit theory diagrams of the current sampling circuit in the present embodiment, as shown in Figure 5；The effect of current sampling circuit be by The current signal that current sensor collects is converted to voltage signal, then carries out shaping, filtering and voltage increase, is converted to DSP Signal manageable with protection circuit.

The circuit theory diagrams of the protection circuit in the present embodiment, as shown in Figure 6, wherein circuit (a) is overcurrent protection electricity Road, triggers circuit including current signal shaping circuit, comparison circuit and protection, and the effect of circuit overcurrent protection is to receive three-phase Sampling inductive current and three-phase sampled output current and through process output overcurrent protection signal, then through simulate I/O circuit Send to DSP.Circuit (b) is excess voltage protection, triggers electricity including voltage signal shaping circuit, comparison circuit and protection Road, the effect of excess voltage protection is to receive three-phase sampling and outputting voltage and through processing output over-voltage protection signal, so Send to DSP by simulation I/O circuit.

The circuit theory diagrams of the RS232 communicating circuit in the present embodiment, as it is shown in fig. 7, the effect of this circuit is to receive To the level conversion of UTC time signal be the level signal that DSP can identify.

The circuit theory diagrams of the digital I/O circuit in the present embodiment, as shown in Figure 8, wherein circuit (a) is that digital signal is defeated Going out circuit, the digital alarm signal that DSP is exported by this circuit is amplified driving, and is converted to the signal that can export.Circuit (b) For digital signal input circuit, this circuit receives the pps pulse per second signal that wireless standard time base circuit sends, and is filtered and puts Big process, is converted to the manageable signal of DSP.

Circuit theory diagrams such as Fig. 9 of simulation I/O circuit in the present embodiment, this circuit receives overvoltage protection signal and mistake Current protection signal is also filtered and level conversion, and the signal of acquisition is sent to the analog input end of DSP.

The circuit theory diagrams of DSP such as Figure 10 in the present embodiment, DSP use the TMS320F28335 series DSP of TI company. DSP is the kernel control module of governor circuit 2, and the effect of this module is to receive voltage, current feedback signal and command signal, raw PWM is become to trigger signal and send to PWM drive circuit.

The circuit theory diagrams of the PWM drive circuit in the present embodiment, as shown in figure 11, the PWM of input triggers signal, first It is driven through 74AHCT245 circuit, then isolates through 2QD32R-S, obtain PWM drive signal and send to photovoltaic Converter main circuit, controls the break-make of switching tube.

The control method of the photovoltaic micro inverter sync control device of described band decision-making device, such as Figure 12, including such as Lower step:

Step one: control the structure chart of device, as shown in figure 13, utilize voltage sensor to gather photovoltaic DC-to-AC converter main circuit The three-phase output voltage of outfan, and the three-phase output voltage gathered is transmitted to the voltage sampling circuit of governor circuit；With Shi Liyong current sensor gathers three pole reactor electric current and the three-phase output electric current of photovoltaic DC-to-AC converter main circuit outfan, and will adopt The three pole reactor electric current of collection and three-phase output electricity are streamed in the current sampling circuit of governor circuit；

Step 2: the UTC time signal received and pps pulse per second signal are sent to governor circuit by wireless standard time base circuit In, governor circuit UTC time signal, pps pulse per second signal, three-phase output voltage, three pole reactor electric current and three-phase to receiving Output electric current process, generate PWM trigger signal, and PWM is triggered signal send to PWM drive circuit, it specifically includes Following steps:

Step A: utilize voltage sampling circuit three-phase output voltage to be filtered and amplitude transformation, obtain three phase samplers defeated Go out voltage and send to protection circuit and DSP；Utilize current sampling circuit that three pole reactor electric current and three-phase are exported electric current to enter Row signal type is changed, and is filtered and amplitude transformation, obtains three phase sampler inductive currents and three-phase sampled output current, and Signal after conversion is sent to protection circuit and DSP；

Step B: protection circuit receives three-phase sampling and outputting voltage, three phase sampler inductive currents and three-phase sampled output current And process, respectively obtain overvoltage protection signal and overcurrent protection signal, overvoltage protection signal and overcurrent protection Signal sends to DSP after simulation I/O processing of circuit；The DSP overvoltage protection signal to receiving and overcurrent protection letter Number process, it is judged that whether it meets protection act condition: when meeting protection act condition, DSP output pulse blocking letter Number, block PWM triggers signal, and when being unsatisfactory for protection act condition, DSP does not export pulse blocking signal, and normal output PWM touches Signal；

Meanwhile, DSP receives three-phase sampling and outputting voltage, three phase sampler inductive currents and three-phase sampled output current, and leads to The A/D sampling module crossing DSP therein processes, and correspondence obtains output voltage sampled value, inductive current sampled value respectively With output current sampling data, then to the output voltage sampled value obtained, inductive current sampled value and output current sampling data Carry out abc/dq coordinate transform, obtain the biphase output voltage sampled value under biphase rotating coordinate system, biphase inductive current is adopted Sample value and biphase output current sampling data；

Step C: by the biphase output voltage sampled value under the biphase rotating coordinate system of dq and biphase output current sampling data Calculating the instantaneous active power p and instantaneous reactive power q of photovoltaic DC-to-AC converter output, concrete accounting equation is as follows:

$\left\{\begin{array}{c}q=\frac{3}{2}(u_{oq}{i}_{od}-u_{od}{i}_{oq})\\ p=\frac{3}{2}(u_{od}{i}_{od}+u_{oq}{i}_{oq})\end{array}\right.---\left(8\right)$

After instantaneous active power p and instantaneous reactive power q determines, obtain actual output through low pass filter filtering and gain merit Power P and actual output reactive power Q, the filtering equations of described low pass filter is as follows:

$\left\{\begin{array}{c}P=\frac{{\mathrm{\ω}}_c}{s+{\mathrm{\ω}}_c}p\\ Q=\frac{{\mathrm{\ω}}_c}{s+{\mathrm{\ω}}_c}q\end{array}\right.---\left(9\right)$

In formula, s is complex frequency domain variable；ω_cFor according to the device calculated low-pass filter frequency of filtering performance demand Bandwidth；

Step D: by the biphase output voltage sampled value under biphase rotating coordinate system and biphase output current sampling data meter Calculate photovoltaic DC-to-AC converter output voltage frequency and output voltage phase place；

Step E: UTC time signal is sent to RS232 communicating circuit by wireless standard time base circuit, RS232 communication electricity After road carries out level conversion to UTC time signal, send the SCI communication interface to DSP；Wireless standard time base circuit is by pulse per second (PPS) Signal sends to numeral I/O circuit, and pps pulse per second signal is filtered and after integer process, sends to DSP by numeral I/O circuit Digital I/O interface；

Step F: by the wireless second base clock controller in DSP master controller to UTC time signal, pps pulse per second signal (1PPS) calculate with real-time clock frequency of oscillation value, generate global synchronization frequencies omega^*, revised triangular wave output frequency ω_triPhase theta is exported with revised triangular wave_tri；In view of in photovoltaic micro, each inverter that there is distributed operation lacks The problem of few stable reference synchronization point, in the present embodiment, provides high accuracy with wireless second base clock controller for each inverter Overall reference frequency and phase place, it is achieved the unification of each inverter reference synchronization point apart from each other, for realize accurately synchronize Control to provide guarantee, the structure chart of wireless second base clock controller, as shown in figure 15；

Step G: according to the overall situation determined in output voltage frequency, output voltage phase place and step F of photovoltaic DC-to-AC converter The actual active power of output determined in synchronizing frequency and step C and actual output reactive power, determining in DSP master controller Plan compensating controller calculates and obtains output voltage frequency reference value and output voltage amplitude reference value；

Step H: according to the output voltage frequency reference value determined in step G and output voltage amplitude reference value, Jing Guo electricity It is pressed into acquisition output voltage reference valueWith

Step I: by poor to output voltage reference value and biphase output voltage sampled value, it is thus achieved that voltage controller set-point, And by the voltage controller in voltage controller set-point input to DSP master controller, obtain after voltage controller processes Output current reference value；

Described voltage controller adoption rate integration (PI) control method, applies PI control method, chooses suitable voltage Proportionality coefficient and voltage integrating meter coefficient, it is possible to achieve good voltage follow control performance.

The expression formula of voltage controller is as follows:

$\left\{\begin{array}{c}{i}_{ld}^{*}=k_{pv}(u_{od}^{*}-u_{od})+k_{iv}\∫(u_{od}^{*}-u_{od})dt+i_{od}-{\mathrm{\ωC}}_f{u}_{oq}\\ i_{lq}^{*}=k_{pv}(u_{oq}^{*}-u_{oq})+k_{iv}\∫(u_{oq}^{*}-u_{oq})dt+i_{oq}-{\mathrm{\ωC}}_f{u}_{od}\end{array}\right.---\left(10\right)$

In formula, k_pvFor voltage ratio coefficient；k_ivFor voltage integrating meter coefficient；WithIt is respectively the d of inductive current reference value Axle and q axle component；i_odAnd i_oqIt is respectively d axle and the q axle component of output current sampling data；WithIt is respectively output voltage values D axle and q axle component；u_odAnd u_oqIt is respectively d axle and the q axle component of output voltage sampled value；ω is inverter output voltage Frequency；C_fFor filtering capacitance.

Step J: by poor with biphase output current sampling data for output current reference value, it is thus achieved that current controller set-point, And by the current controller in current controller set-point input to DSP master controller, it is thus achieved that command voltage reference value；

Described current controller is also adopted by PI control method, and the expression formula of current controller is as follows:

$\left\{\begin{array}{c}{u}_d^{*}=k_{pi}(i_{ld}^{*}-i_{ld})+k_{ii}\∫(i_{ld}^{*}-i_{ld})dt-{\mathrm{\ωL}}_f{i}_{lq}\\ u_q^{*}=k_{pi}(i_{lq}^{*}-i_{lq})+k_{ii}\∫(i_{lq}^{*}-i_{lq})dt-{\mathrm{\ωL}}_f{i}_{ld}\end{array}\right.---\left(11\right)$

In formula, k_piFor current ratio coefficient；k_iiFor current integration coefficient；WithIt is respectively the d of inductive current reference value Axle and q axle component；i_ldAnd i_lqIt is respectively d axle and the q axle component of inductive current sampled value；WithIt is respectively command voltage ginseng Examine d axle and the q axle component of value；ω is the frequency of inverter output voltage；L_fFor filter inductance value.

Step K: obtain PWM according to command voltage reference value and revised triangular wave output frequency and trigger signal, and will PWM triggers signal and sends to PWM drive circuit；

Step 3: by PWM drive circuit, PWM is triggered signal and carry out level conversion, it is thus achieved that start pulse signal is concurrent Deliver in photovoltaic DC-to-AC converter main circuit, control its switching tube S₁～S₆Break-make, it is achieved photovoltaic DC-to-AC converter output voltage and other light The synchronization of volt inverter output voltage.

Described in step F by the wireless second base clock controller in DSP master controller to UTC time signal, second arteries and veins Rush signal and real-time clock frequency of oscillation value calculate, generate global synchronization frequency, revised triangular wave output frequency and Revised triangular wave output phase place, as shown in figure 14, it specifically comprises the following steps that

Step f1: utilize UTC time signal and pps pulse per second signal, it is thus achieved that global synchronization frequency signal ω^*, clock frequency survey Amount signal ω_MWith triangular wave phase reset signal s_TPR；Step f2: utilize global synchronization frequency signal to determine global synchronization frequency, And utilizing clock frequency measurement signal to determine oscillation frequency clock value of calculation, described oscillation frequency clock value of calculation is true by following formula Fixed:

${\mathrm{\ω}}_{cry}=\frac{\underset{i=1}{\overset{n}{\mathrm{\Σ}}}{\mathrm{\ω}}_{cryo}}{n}---\left(1\right)$

In formula, ω_cryoFor real-time clock frequency of oscillation value；ω_cryFor the clock oscillation frequency obtained after average value filtering Rate value of calculation；I is the variable representing pulse per second (PPS) number, i ∈ [1, n]；

Step f3: given oscillation frequency clock rated value and global synchronization triangular wave frequency rated value, and use clock oscillation Frequency rated value, divided by global synchronization triangular wave frequency rated value, obtains triangular wave clock division rated value, is shown below:

$M_0=\frac{{\mathrm{\ω}}_{cry}^{*}}{{\mathrm{\ω}}_{tri}^{*}}---\left(2\right)$

In formula, M₀For triangular wave clock division rated value；For oscillation frequency clock rated value；For global synchronization three Angle wave frequency rated value；

Step f4: by poor to oscillation frequency clock rated value and the oscillation frequency clock value of calculation obtained, obtain clock Oscillation frequency shifts amount, then be multiplied by deviation ratio and obtain triangular wave clock division value correction；By specified for triangular wave clock division Value is poor with the triangular wave clock division value correction obtained, and obtains revised triangular wave clock division value, such as following formula institute Show:

$M^{*}=M_0-k({\mathrm{\ω}}_{cry}^{*}-{\mathrm{\ω}}_{cry})---\left(3\right)$

In formula, M₀For triangular wave clock division rated value；M^*For revised triangular wave clock division value；Shake for clock Swing frequency rated value；K is deviation ratio；ω_cryFor the oscillation frequency clock value of calculation obtained after average value filtering；

Step f5: by the oscillation frequency clock value of calculation that obtained divided by revised triangular wave clock division value, obtain Revised triangular wave output frequency, i.e. triangular wave actual output frequency, can be written as:

${\mathrm{\ω}}_{tri}=\frac{{\mathrm{\ω}}_{cry}}{M^{*}}---\left(12\right)$

In formula, ω_triFor triangular wave actual output frequency；ω_cryFor oscillation frequency clock value of calculation；M^*For revised three Angle ripple clock division value；

Step f6: be integrated revised triangular wave output frequency, obtains triangular wave original real-time phase value；By institute The triangular wave original real-time phase value obtained processes through triangular wave Phase synchronization control function, obtains the output of revised triangular wave Phase place.

Triangular wave Phase synchronization control function described in step f6, is shown below:

θ_tri=sgn (s_TPR)·θ_trio (4)

In formula, θ_trioFor triangular wave original real-time phase value；s_TPRFor triangular wave phase reset signal；θ_triFor revised Triangular wave output phase place；sgn(s_TPR) it is with s_TPRSign function for variable.

In the present embodiment, the reason mainly droop control causing sine wave freuqency and phase offset is a kind of isolated basis Ground control method, and existence can make output voltage frequency and phase place with the defect of power swing.In order to make up these defects, this Invention uses decision-making compensating controller to realize stablizing of output voltage frequency and phase place.

The output voltage frequency according to photovoltaic DC-to-AC converter described in step G, output voltage phase place and step F determine Global synchronization frequency and step C in the actual active power of output that determines and actual output reactive power, through decision-making compensation Controller calculates and obtains output voltage frequency reference value and output voltage amplitude reference value, and such as Figure 16, it specifically comprises the following steps that

The structure chart of described decision-making compensating controller, as shown in figure 17.

Step g1: to global synchronization frequencies omega^*It is integrated, obtains global synchronization phase theta^*；

Step g2: by global synchronization frequencies omega^*Poor with output voltage frequency ω of photovoltaic DC-to-AC converter, obtain output voltage Frequency offset Δ e_ω, by global synchronization phase theta^*Poor with the output voltage phase theta of photovoltaic DC-to-AC converter, obtain output voltage phase Position offset Δ e_θ, it is shown below:

$\left\{\begin{array}{c}{\mathrm{\Δe}}_{\mathrm{\ω}}={\mathrm{\ω}}^{*}-\mathrm{\ω}\\ {\mathrm{\Δe}}_{\mathrm{\θ}}={\mathrm{\θ}}^{*}-\mathrm{\θ}\end{array}\right.---\left(13\right)$

Step g3: preset synchronization controls threshold value and security control threshold value, and described Synchronization Control threshold value includes sine wave freuqency Difference is the upper limit threshold Δ e of zero_ωminWith lower threshold-Δ e_ωmin, sine wave phase difference be zero upper limit threshold Δ e_θminUnder with Limit threshold value-Δ e_θmin；Described security control threshold value includes sine wave freuqency difference upper limit threshold Δ e during stable operation_ωmaxAnd lower limit Threshold value-Δ e_ωmax, stable operation time sine wave phase difference upper limit threshold Δ e_θmaxWith lower threshold-Δ e_θmax；And according to output electricity Pressure frequency offset and output voltage phase pushing figure determine Synchronization Control state table；Described Synchronization Control state table, is shown in Table 1.

Table 1 Synchronization Control state table

Step g4: according to output voltage frequency side-play amount, output voltage phase pushing figure and Synchronization Control threshold value and peace Entirely control threshold value, determine that the functional value of valuation functions, described valuation functions include frequency estimation function, phase evaluation function, phase Position bit switch valuation functions and step-out Forewarn evaluation function, as follows:

$\left\{\begin{array}{c}{s}_{\mathrm{\ω}}=g({\mathrm{\Δe}}_{\mathrm{\ω}},{\mathrm{\Δe}}_{\mathrm{\θ}})\\ s_{\mathrm{\θ}}=h({\mathrm{\Δe}}_{\mathrm{\ω}},{\mathrm{\Δe}}_{\mathrm{\θ}})\\ s_{SPR}=\mathrm{sgn}\left({\mathrm{\Δe}}_{\mathrm{\θ}}\right)\\ s_{warn}=\mathrm{sgn}\left({\mathrm{\Δe}}_{\mathrm{\ω}}\right)*f\left(t\right)\end{array}\right.---\left(5\right)$

In formula, s_ωThe entitled g of representative function, with Δ e_ωWith Δ e_θFrequency estimation function for variable；s_θThe entitled h of representative function, With Δ e_ωWith Δ e_θPhase evaluation function for variable；s_SPRFor phase position bit switch valuation functions, s_warnFor step-out Forewarn evaluation Function, sgn is sign function, and f (t) represents the function with time t as variable；

The Decision Evaluation method of described valuation functions, specifically includes following steps:

Step X1: according to output voltage frequency offset Δ e_ω, sine wave freuqency in preset Synchronization Control threshold value poor It is the upper limit threshold Δ e of zero_ωminWith lower threshold-Δ e_ωminAnd it is sinusoidal wave during stable operation in preset security control threshold value Difference on the frequency upper limit threshold Δ e_ωmaxWith lower threshold-Δ e_ωmax, it is judged that FREQUENCY CONTROL state now:

If | Δ e_ω| ＜ Δ e_ωmin, then output voltage frequency side-play amount is less than Synchronization Control threshold value, and sine wave freuqency synchronizes, The now FREQUENCY CONTROL state that defines is state one；

If Δ e_ωmin＜ Δ e_ω＜ Δ e_ωmax, then output voltage frequency side-play amount is more than Synchronization Control threshold value but not less than peace Entirely controlling threshold value, the frequency shift (FS) of output voltage is forward migration, and the now FREQUENCY CONTROL state that defines is state two；

If-Δ e_ωmax＜ Δ e_ω＜-Δ e_ωmin, then output voltage frequency side-play amount exceed Synchronization Control threshold value but not less than Security control threshold value, the frequency shift (FS) of output voltage is negative offset, and the now FREQUENCY CONTROL state that defines is state three；

If Δ e_ω＞ Δ e_ωmax, then output voltage frequency side-play amount exceedes security control threshold value, and the frequency of output voltage is inclined Moving is forward migration, and the now FREQUENCY CONTROL state that defines is state four；

If Δ e_ω＜-Δ e_ωmax, then output voltage frequency side-play amount exceedes security control threshold value, and the frequency of output voltage is inclined Moving is negative offset, and the now FREQUENCY CONTROL state that defines is state five；

If FREQUENCY CONTROL state is state one, then:

If | Δ e_θ| ＜ Δ e_θmin, the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=0；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, the functional value of valuation functions is: s_θ=1, s_ω=0, s_SPR=0, s_warn=0；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, the functional value of valuation functions is: s_θ=1, s_ω=0, s_SPR=0, s_warn=0；

If | Δ e_θ| ＞ Δ e_θmax, the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=1, s_warn=0,；

If FREQUENCY CONTROL state is state two, then:

If | Δ e_θ| ＜ Δ e_θmin, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=0；

If Δ e_θmiN ＜ Δ e_θ＜ Δ e_θmax, the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=0；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=0；

If | Δ e_θ| ＞ Δ e_θmax, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=1, s_warn=0；

If FREQUENCY CONTROL state is state three, then:

If | Δ e_θ| ＜ Δ e_θmin, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=0；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=0；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=0；

If | Δ e_θ| ＞ Δ e_θmax, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=1, s_warn=0；

If FREQUENCY CONTROL state is state four, then:

If | Δ e_θ| ＜ Δ e_θmin, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=1；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1；

If | Δ e_θ| ＞ Δ e_θmax, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=1, s_warn=1；

If FREQUENCY CONTROL state is state five, then:

If | Δ e_θ| ＜ Δ e_θmin, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1；If Δ e_θmin ＜ Δ e_θ＜ Δ e_θmax, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1,；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=1；

If | Δ e_θ| ＞ Δ e_θmax, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=1, s_warn=1；

Step X2: according to the FREQUENCY CONTROL state drawn in step X1, and output voltage phase pushing figure Δ e_θ, preset Synchronization Control threshold value in the upper limit threshold Δ e that sine wave phase difference is zero_θminWith lower threshold-Δ e_θmin, preset safety Control sine wave phase difference upper limit threshold Δ e during the stable operation in threshold value_θmaxWith lower threshold-Δ e_θmax, through selecting assessment Determine the functional value of valuation functions:

Step X3: utilize the output voltage frequency side-play amount obtained, uses PI to control (i.e. proportional, integral control) and obtains Amount of frequency compensation initial value, is shown below:

Δ ω=k_pω(ω^*-ω)+k_iω∫(ω^*-ω)dt (14)

In formula, Δ ω is amount of frequency compensation initial value, k_pω、k_iωIt is respectively frequency proportions coefficient and frequency integrator coefficient；

Step X4: set meritorious sagging coefficient according to equipment energy characteristic, and determine output voltage frequency reference value, described output Electric voltage frequency reference value is determined by following formula:

ω_ref=(ω^*+s_ω·Δω)-k_p·P (6)

In formula, ω_refFor output voltage frequency reference value, ω^*For global synchronization frequency, k_pFor meritorious sagging coefficient, P is real Border active power of output, Δ ω is amount of frequency compensation initial value, s_ωFunctional value for frequency estimation function；

Step X5: the functional value that the output voltage phase pushing figure obtained is multiplied by phase evaluation function obtains phase place benefit Repay value, add the phase place intermediate value that frequency reference is integrated to be obtained and obtain phase place initial value；By logical value 1 and phase place The functional value of setting switch valuation functions is poor, and difference is multiplied by phase place initial value, it is thus achieved that sinusoidal wave real-time phase value, completes Adjustment to phase place；Described sinusoidal wave real-time phase value is determined by following formula:

θ=(1-s_SPR)(θ_p+s_θ*Δe_θ) (7)

In formula, θ is sinusoidal wave real-time phase value；θ_pFor phase place intermediate value；s_SPRLetter for phase position bit switch valuation functions Numerical value；s_θFunctional value for phase evaluation function；Δe_θFor output voltage phase pushing figure；

Step X6: set output voltage amplitude rated value E according to equipment energy characteristic^*With idle sagging coefficient k_q, by output voltage Amplitude rated value and idle sagging coefficient and actual output reactive power long-pending poor, obtains output voltage amplitude reference value E_ref, It is shown below:

E_ref=E^*-k_qQ (15)

In formula, k_qFor idle sagging coefficient；E^*For output voltage amplitude rated value；E_refFor output voltage amplitude reference value；Q For actual output reactive power.

In the present embodiment, Figure 18 is the experimental waveform figure after inverter parallel output impulsive synchronization, and Figure 19 is that its local is put Big oscillogram, two figures are the output voltage waveform before wave filter.As can be seen from the figure: the photovoltaic of distributed operation Inverter output voltage pulse is achieved that synchronization within a very short time, it is achieved that the Instantaneous Control of circulation, promotes micro-capacitance sensor Stability and high efficiency and reliability service.

Claims (7)

1. a photovoltaic micro inverter sync control device for band decision-making device, including photo-voltaic power supply, the main electricity of photovoltaic DC-to-AC converter Road, cutting-in control switch, voltage sensor, current sensor, PWM drive circuit and governor circuit；Described photo-voltaic power supply defeated Going out end to be connected with the input of photovoltaic DC-to-AC converter main circuit, outfan one tunnel of photovoltaic DC-to-AC converter main circuit is left through cutting-in control Closing and be connected with public exchange bus, another road is connected with load；Described voltage sensor and the input of current sensor Outfan with photovoltaic DC-to-AC converter main circuit is connected respectively, the outfan of voltage sensor and current sensor respectively with master control The voltage sampling circuit of circuit is connected with the input of current sampling circuit, and the outfan of described governor circuit drives with PWM The input of circuit is connected, and the outfan of PWM drive circuit is connected with the control end of photovoltaic DC-to-AC converter main circuit；Its feature Being, described control device also includes wireless standard time base circuit, the outfan of described wireless standard time base circuit and master control electricity The communication interface on road is connected.

The photovoltaic micro inverter sync control device of band decision-making device the most according to claim 1, it is characterised in that institute State wireless standard time base circuit to include at wireless signal receiving antenna, coax signal cable, wireless signal receiving circuit and level Reason circuit, the outfan of wireless signal receiving antenna is connected with the input of wireless signal receiving circuit through coax signal cable Connecing, the input that the outfan of wireless signal receiving circuit processes circuit with level is connected, and level processes the outfan of circuit Outfan as wireless standard time base circuit.

The photovoltaic micro inverter sync control device of band decision-making device the most according to claim 1, it is characterised in that institute State governor circuit include voltage sampling circuit, current sampling circuit, protection circuit, simulation I/O circuit, numeral I/O circuit, RS232 communicating circuit, alarm device and DSP, outfan one tunnel of described voltage sampling circuit and current sampling circuit respectively with The A/D sampling module of DSP is connected, and another road is connected with the input of protection circuit respectively, the outfan warp of protection circuit Simulation I/O circuit is connected with the simulation I/O interface of DSP；The input of described RS232 communicating circuit and numeral I/O circuit Input is connected with the SCI communication interface of DSP as the communication interface of governor circuit, the outfan of RS232 communicating circuit, number The outfan of word I/O circuit is connected with alarm device, and the numeral communication interface of I/O circuit is connected with the digital I/O interface of DSP Connecing, the outfan of the SPWM generation module of DSP is as the outfan of governor circuit.

4. the control method of the photovoltaic micro inverter sync control device of the band decision-making device described in claim 1, its feature It is, comprises the steps:

Step one: utilize voltage sensor to gather the three-phase output voltage of photovoltaic DC-to-AC converter main circuit outfan, and transmit to main In the voltage sampling circuit of control circuit；Utilize current sensor to gather the three pole reactor of photovoltaic DC-to-AC converter main circuit outfan simultaneously Electric current and three-phase output electric current, and transmit to the current sampling circuit of governor circuit；

Step 2: the UTC time signal received and pps pulse per second signal are sent to governor circuit by wireless standard time base circuit, main UTC time signal, pps pulse per second signal, three-phase output voltage, three pole reactor electric current and the three-phase output to receiving of the control circuit Electric current processes, generate PWM trigger signal, and PWM is triggered signal send to PWM drive circuit, it specifically includes as follows Step:

Step A: utilize voltage sampling circuit to be filtered three-phase output voltage and amplitude transformation, obtains three phase sampler output electricity Press and send to protection circuit and DSP；Utilize current sampling circuit that three pole reactor electric current and three-phase are exported electric current and carry out letter The conversion of number type, and be filtered and amplitude transformation, obtain three phase sampler inductive currents and three-phase sampled output current, and send To protection circuit and DSP；

Step B: protection circuit receives three-phase sampling and outputting voltage, three phase sampler inductive currents and three-phase sampled output current and goes forward side by side Row processes, and respectively obtains overvoltage protection signal and overcurrent protection signal, overvoltage protection signal and overcurrent protection signal Send to DSP after simulation I/O processing of circuit；The DSP overvoltage protection signal to receiving and overcurrent protection signal enter Row processes, it is judged that whether it meets protection act condition: when meeting protection act condition, and DSP exports pulse blocking signal, envelope Lock PWM triggers signal, and when being unsatisfactory for protection act condition, DSP does not export pulse blocking signal, and normal output PWM triggers letter Number；

Meanwhile, DSP receives three-phase sampling and outputting voltage, three phase sampler inductive currents and three-phase sampled output current, and passes through DSP The A/D sampling module of therein processes, and correspondence obtains output voltage sampled value, inductive current sampled value and output respectively Current sampling data, then carries out abc/dq coordinate transform, obtain the biphase output voltage sampled value under biphase rotating coordinate system, Biphase inductive current sampled value and biphase output current sampling data；

Step C: calculate light by the biphase output voltage sampled value under biphase rotating coordinate system and biphase output current sampling data After the instantaneous active power of volt inverter output and instantaneous reactive power, instantaneous active power and instantaneous reactive power determine, warp Cross low pass filter filtering and obtain actual active power of output and actual output reactive power；

Step D: calculate light by the biphase output voltage sampled value under biphase rotating coordinate system and biphase output current sampling data Volt inverter output voltage frequency and output voltage phase place；

Step E: UTC time signal is sent to RS232 communicating circuit by wireless standard time base circuit, RS232 communicating circuit pair After UTC time signal carries out level conversion, send the SCI communication interface to DSP；Wireless standard time base circuit is by pps pulse per second signal Sending to numeral I/O circuit, pps pulse per second signal is filtered and after integer process, sends the number to DSP by numeral I/O circuit Word I/O interface；

Step F: by the wireless second base clock controller in DSP master controller to UTC time signal, pps pulse per second signal and in real time Oscillation frequency clock value calculates, and generates global synchronization frequency, revised triangular wave output frequency and revised triangle Ripple output phase place；

Step G: according to the global synchronization determined in output voltage frequency, output voltage phase place and step F of photovoltaic DC-to-AC converter The actual active power of output determined in frequency and step C and actual output reactive power, the decision-making in DSP master controller is mended Repay controller and calculate acquisition output voltage frequency reference value and output voltage amplitude reference value；

Step H: according to the output voltage frequency reference value determined in step G and output voltage amplitude reference value, close through overvoltage Become to obtain output voltage reference value；

Step I: by poor to output voltage reference value and biphase output voltage sampled value, it is thus achieved that voltage controller set-point, and will Voltage controller set-point inputs the voltage controller to DSP master controller, obtains output after voltage controller processes Current reference value；

Step J: by poor with biphase output current sampling data for output current reference value, it is thus achieved that current controller set-point, and will Current controller set-point inputs the current controller to DSP master controller, it is thus achieved that command voltage reference value；

Step K: obtain PWM according to command voltage reference value and revised triangular wave output frequency and trigger signal, and PWM is touched Signal and send to PWM drive circuit；

Step 3: by PWM drive circuit, PWM is triggered signal and carry out level conversion, it is thus achieved that start pulse signal also sends extremely In photovoltaic DC-to-AC converter main circuit, control the break-make of its switching tube, it is achieved photovoltaic DC-to-AC converter output voltage and other photovoltaic DC-to-AC converters The synchronization of output voltage.

The control method of the photovoltaic micro inverter sync control device of band decision-making device the most according to claim 4, its Be characterised by described in step F by the wireless second base clock controller in DSP master controller to UTC time signal, second arteries and veins Rush signal and real-time clock frequency of oscillation value calculate, generate global synchronization frequency, revised triangular wave output frequency and Revised triangular wave output phase place, it specifically comprises the following steps that

Step f1: utilize UTC time signal and pps pulse per second signal, it is thus achieved that global synchronization frequency signal, clock frequency measure signal With triangular wave phase reset signal；

Step f2: utilize global synchronization frequency signal to determine global synchronization frequency, and when utilizing clock frequency measurement signal to determine Clock frequency of oscillation value of calculation, described oscillation frequency clock value of calculation is determined by following formula:

${\mathrm{\ω}}_{cry}=\frac{\underset{i=1}{\overset{n}{\Σ}}{\mathrm{\ω}}_{cryo}}{n}---\left(1\right)$

In formula, ω_cryoFor real-time clock frequency of oscillation value；ω_cryFor the oscillation frequency clock meter obtained after average value filtering Calculation value；I is the variable representing pulse per second (PPS) number, i ∈ [1, n]；

Step f3: given oscillation frequency clock rated value and triangular wave frequency rated value, and remove with oscillation frequency clock rated value With triangular wave frequency rated value, obtain triangular wave clock division rated value, be shown below:

$M_0=\frac{{\mathrm{\ω}}_{cry}^{*}}{{\mathrm{\ω}}_{tri}^{*}}---\left(2\right)$

In formula, M₀For triangular wave clock division rated value；For oscillation frequency clock rated value；Specified for triangular wave frequency Value；

Step f4: by poor to oscillation frequency clock rated value and the oscillation frequency clock value of calculation obtained, obtain clock oscillation Frequency offset, then be multiplied by deviation ratio and obtain triangular wave clock division value correction；By triangular wave clock division rated value with The triangular wave clock division value correction obtained is poor, obtains revised triangular wave clock division value, is shown below:

$M^{*}=M_0-k({\mathrm{\ω}}_{cry}^{*}-{\mathrm{\ω}}_{cry})---\left(3\right)$

In formula, M₀For triangular wave clock division rated value；M^*For revised triangular wave clock division value；For clock oscillation frequency Rate rated value；K is deviation ratio；ω_cryFor the oscillation frequency clock value of calculation obtained after average value filtering；

Step f5: by the oscillation frequency clock value of calculation that obtained divided by revised triangular wave clock division value, revised After triangular wave output frequency；

Step f6: be integrated revised triangular wave output frequency, obtains triangular wave original real-time phase value；To be obtained Triangular wave original real-time phase value through triangular wave Phase synchronization control function process, obtain revised triangular wave output phase Position.

The control method of the photovoltaic micro inverter sync control device of band decision-making device the most according to claim 5, its It is characterised by the triangular wave Phase synchronization control function described in step f6, is shown below:

θ_tri=sgn (s_TPR)·θ_trio (4)

In formula, θ_trioFor triangular wave original real-time phase value；S_TPRFor triangular wave phase reset signal；θ_triFor revised triangle Ripple output phase place；sgn(s_TPR) it is with s_TPRSign function for variable.

The control method of the photovoltaic micro inverter sync control device of band decision-making device the most according to claim 4, its It is characterised by the output voltage frequency according to photovoltaic DC-to-AC converter described in step G, output voltage phase place and step F determining Global synchronization frequency and step C in the actual active power of output that determines and actual output reactive power, through decision-making compensation Controller calculates and obtains output voltage frequency reference value and output voltage amplitude reference value, and it specifically comprises the following steps that

Step g1: be integrated global synchronization frequency, obtains global synchronization phase place；

Step g2: by poor for the output voltage frequency of global synchronization frequency Yu photovoltaic DC-to-AC converter, obtains output voltage frequency skew Amount Δ e_ω, by poor for the output voltage phase place of global synchronization phase place Yu photovoltaic DC-to-AC converter, obtain output voltage phase pushing figure Δ e_θ；

Step g3: preset synchronization controls threshold value and security control threshold value, and described Synchronization Control threshold value includes that sine wave freuqency difference is The upper limit threshold Δ e of zero_ωminWith lower threshold-Δ e_ωmin, sine wave phase difference be zero upper limit threshold Δ e_θminWith lower limit threshold Value-Δ e_θmin；Described security control threshold value includes sine wave freuqency difference upper limit threshold Δ e during stable operation_ωmaxWith lower threshold- Δe_ωmax, stable operation time sine wave phase difference upper limit threshold Δ e_θmaxWith lower threshold-Δ e_θmax；

Step g4: according to output voltage frequency side-play amount, output voltage phase pushing figure and Synchronization Control threshold value and safety control Threshold value processed, determines that the functional value of valuation functions, described valuation functions include frequency estimation function, phase evaluation function, phase position Bit switch valuation functions and step-out Forewarn evaluation function, as follows:

$\left\{\begin{array}{c}{s}_{\mathrm{\ω}}=g({\mathrm{\Δe}}_{\mathrm{\ω}},{\mathrm{\Δe}}_{\mathrm{\θ}})\\ s_{\mathrm{\θ}}=h({\mathrm{\Δe}}_{\mathrm{\ω}},{\mathrm{\Δe}}_{\mathrm{\θ}})\\ s_{SPR}=\mathrm{sgn}\left({\mathrm{\Δe}}_{\mathrm{\θ}}\right)\\ s_{warn}=\mathrm{sgn}\left({\mathrm{\Δe}}_{\mathrm{\ω}}\right)*f\left(t\right)\end{array}\right.---\left(5\right)$

In formula, s_ωThe entitled g of representative function, with Δ e_ωWith Δ e_θFrequency estimation function for variable；s_θThe entitled h of representative function, with Δ e_ωWith Δ e_θPhase evaluation function for variable；s_SPRFor phase position bit switch valuation functions, s_warnFor step-out Forewarn evaluation function, Sgn is sign function, and f (t) represents the function with time t as variable；

The Decision Evaluation method of described valuation functions, specifically includes following steps:

Step X1: according to output voltage frequency offset Δ e_ω, sine wave freuqency difference in preset Synchronization Control threshold value be zero Upper limit threshold Δ e_ωminWith lower threshold-Δ e_ωminAnd sine wave freuqency during stable operation in preset security control threshold value Difference upper limit threshold Δ e_ωmaxWith lower threshold-Δ e_ωmax, it is judged that FREQUENCY CONTROL state now:

If | Δ e_ω| ＜ Δ e_ωmin, then output voltage frequency side-play amount is less than Synchronization Control threshold value, and sine wave freuqency synchronizes, definition Now FREQUENCY CONTROL state is state one；

If Δ e_ωmin＜ Δ e_ω＜ Δ e_ωmax, then output voltage frequency side-play amount is more than Synchronization Control threshold value but not less than safety control Threshold value processed, the frequency shift (FS) of output voltage is forward migration, and the now FREQUENCY CONTROL state that defines is state two；

If-Δ e_ωmax＜ Δ e_ω＜-Δ e_ωmin, then output voltage frequency side-play amount exceedes Synchronization Control threshold value but not less than safety Controlling threshold value, the frequency shift (FS) of output voltage is negative offset, and the now FREQUENCY CONTROL state that defines is state three；

If Δ e_ω＞ Δ e_ωmax, then output voltage frequency side-play amount exceedes security control threshold value, and the frequency shift (FS) of output voltage is Forward migration, the now FREQUENCY CONTROL state that defines is state four；

If Δ e_ω＜-Δ e_ωmax, then output voltage frequency side-play amount exceedes security control threshold value, and the frequency shift (FS) of output voltage is Negative offset, the now FREQUENCY CONTROL state that defines is state five；

Step X2: according to the FREQUENCY CONTROL state drawn in step X1, and output voltage phase pushing figure Δ e_θ, preset same Step controls the upper limit threshold Δ e that sine wave phase difference is zero in threshold value_θminWith lower threshold-Δ e_θmin, preset security control Sine wave phase difference upper limit threshold Δ e during stable operation in threshold value_θmaxWith lower threshold-Δ e_θmax, through selecting assessment to determine The functional value of valuation functions:

If FREQUENCY CONTROL state is state one, then:

If | Δ e_θ| ＜ Δ e_θmin, then output voltage phase pushing figure is less than Synchronization Control threshold value, illustrates that the frequency of output voltage is same Step, the phase place of output voltage also synchronizes, and is not required to start any control, and the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR= 0, s_warn=0；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, then output voltage phase pushing figure is more than Synchronization Control threshold value but not less than safety control Threshold value processed, the phase offset of output voltage is forward migration, and the Frequency Synchronization of output voltage is described, the phase place of output voltage surpasses Before, needing to carry out phase controlling, the functional value of valuation functions is: s_θ=1, s_ω=0, s_SPR=0, s_warn=0；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, then output voltage phase pushing figure exceedes Synchronization Control threshold value but not less than safety Controlling threshold value, the phase offset of output voltage is negative offset, and the Frequency Synchronization of output voltage is described, the phase steric retardation of output voltage After, needing to carry out phase controlling, the functional value of valuation functions is: s_θ=1, s_ω=0, s_SPR=0, s_warn=0；

If | Δ e_θ| ＞ Δ e_θmax, then output voltage phase pushing figure exceedes security control threshold value, illustrates that the frequency of output voltage is same Step, the serious step-out of phase place of output voltage, need to carry out phase position bit switch control, i.e. sinusoidal wave starting point controls to reactivate Controlling, the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=1, s_warn=0；

If FREQUENCY CONTROL state is state two, then:

If | Δ e_θ| ＜ Δ e_θmin, then output voltage phase pushing figure is less than Synchronization Control threshold value, illustrates that the frequency of output voltage increases Greatly, the Phase synchronization of output voltage, need to carry out FREQUENCY CONTROL, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=0；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, then output voltage phase pushing figure is more than Synchronization Control threshold value but not less than safety control Threshold value processed, the phase offset of output voltage is forward migration, illustrates that the frequency of output voltage increases, and the phase place of output voltage surpasses Before, phase place can be adjusted by the frequency of increase, is not required to start any control, and the functional value of valuation functions is: s_θ=0, s_ω =0, s_SPR=0, s_warn=0；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, then output voltage phase pushing figure exceedes Synchronization Control threshold value but not less than safety Controlling threshold value, the phase offset of output voltage is negative offset, illustrates that the frequency of output voltage increases, the phase steric retardation of output voltage After, the frequency of increase can make phase contrast continue to increase, and needs to carry out FREQUENCY CONTROL, and the functional value of valuation functions is: s_θ=0, s_ω =1, s_SPR=0, s_warn=0；

If | Δ e_θ| ＞ Δ e_θmax, then output voltage phase pushing figure exceedes security control threshold value, illustrates that the frequency of output voltage increases Greatly, the serious step-out of phase place of output voltage, now need to carry out FREQUENCY CONTROL and phase position bit switch controls, the letter of valuation functions Numerical value is: s_θ=0, s_ω=1, s_SPR=1, s_warn=0；

If FREQUENCY CONTROL state is state three, then:

If | Δ e_θ| ＜ Δ e_θmin, then output voltage phase pushing figure is less than Synchronization Control threshold value, illustrates that the frequency of output voltage subtracts Little, the Phase synchronization of output voltage, need to carry out FREQUENCY CONTROL, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=0；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, then output voltage phase pushing figure is more than Synchronization Control threshold value but not less than safety control Threshold value processed, the phase offset of output voltage is forward migration, illustrates that the frequency of output voltage reduces, and the phase place of output voltage surpasses Before, the frequency of reduction can make phase contrast continue to increase, and needs to carry out FREQUENCY CONTROL, and the functional value of valuation functions is: s_θ=0, s_ω =1, s_SPR=0, s_warn=0；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, then output voltage phase pushing figure exceedes Synchronization Control threshold value but not less than safety Controlling threshold value, the phase offset of output voltage is negative offset, illustrates that the frequency of output voltage reduces, the phase steric retardation of output voltage After, phase place can be adjusted by the frequency of reduction, is not required to start any control, and the functional value of valuation functions is: s_θ=0, s_ω =0, s_SPR=0, s_warn=0；

If | Δ e_θ| ＞ Δ e_θmax, then output voltage phase pushing figure exceedes security control threshold value, illustrates that the frequency of output voltage subtracts Little, the serious step-out of phase place of output voltage, now need to carry out FREQUENCY CONTROL and phase position bit switch controls, the letter of valuation functions Numerical value is: s_θ=0, s_ω=1, s_SPR=1, s_warn=0；

If FREQUENCY CONTROL state is state four, then:

If | Δ e_θ| ＜ Δ e_θmin, then output voltage phase pushing figure is less than Synchronization Control threshold value, illustrates that the frequency of output voltage increases Greatly, and exceed security control threshold value, the Phase synchronization of output voltage, need to carry out FREQUENCY CONTROL and step-out early warning controls, assessment The functional value of function is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, then output voltage phase pushing figure is more than Synchronization Control threshold value but not less than safety control Threshold value processed, the phase offset of output voltage is forward migration, illustrates that the frequency of output voltage increases, and exceedes security control threshold Value, the phase place of output voltage is advanced, and phase place can be adjusted by the frequency of increase, affects for exclusive PCR, the most only carries out Step-out early warning controls, and the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=1；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, then output voltage phase pushing figure exceedes Synchronization Control threshold value but not less than safety Controlling threshold value, the phase offset of output voltage is negative offset, illustrates that the frequency of output voltage increases, and exceedes security control threshold Value, the delayed phase of output voltage, the frequency of increase can make phase contrast continue to increase, need to carry out FREQUENCY CONTROL and step-out early warning Controlling, the functional value of valuation functions is: s_θ=0, s_ω=1, s_sPR=0, s_warn=1；

If | Δ e_θ| ＞ Δ e_θmax, then output voltage phase pushing figure exceedes security control threshold value, illustrates that the frequency of output voltage increases Greatly, and exceed security control threshold value, the serious step-out of phase place of output voltage, now need to carry out FREQUENCY CONTROL, phase place set is opened Closing and control and step-out early warning control, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=1, s_warn=1；

If FREQUENCY CONTROL state is state five, then:

If | Δ e_θ| ＜ Δ e_θmin, then output voltage phase pushing figure is less than Synchronization Control threshold value, illustrates that the frequency of output voltage subtracts Little, and exceed security control threshold value, the Phase synchronization of output voltage, need to carry out FREQUENCY CONTROL and step-out early warning controls, assessment The functional value of function is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1；

If Δ e_θmin＜ Δ e_θ＜ Δ e_θmax, then output voltage phase pushing figure is more than Synchronization Control threshold value but not less than safety control Threshold value processed, the phase offset of output voltage is forward migration, illustrates that the frequency of output voltage reduces, and exceedes security control threshold Value, the phase place of output voltage is advanced, and the frequency of reduction can make phase contrast continue to increase, and needs to carry out FREQUENCY CONTROL and step-out early warning Controlling, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=0, s_warn=1；

If-Δ e_θmax＜ Δ e_θ＜-Δ e_θmin, then output voltage phase pushing figure exceedes Synchronization Control threshold value but not less than safety Controlling threshold value, the phase offset of output voltage is negative offset, illustrates that the frequency of output voltage reduces, and exceedes security control threshold Value, the delayed phase of output voltage, phase place can be adjusted by the frequency of reduction, affects for exclusive PCR, the most only carries out Step-out early warning controls, and the functional value of valuation functions is: s_θ=0, s_ω=0, s_SPR=0, s_warn=1；

If | Δ e_θ| ＞ Δ e_θmax, then output voltage phase pushing figure exceedes security control threshold value, illustrates that the frequency of output voltage subtracts Little, and exceed security control threshold value, the serious step-out of phase place of output voltage, now need to carry out FREQUENCY CONTROL, phase place set is opened Closing and control and step-out early warning control, the functional value of valuation functions is: s_θ=0, s_ω=1, s_SPR=1, s_warn=1；

Step X3: utilize the output voltage frequency side-play amount obtained, uses PI to control to obtain amount of frequency compensation initial value；

Step X4: set meritorious sagging coefficient according to equipment energy characteristic, and determine output voltage frequency reference value, described output voltage Frequency reference is determined by following formula:

ω_ref=(ω^*+s_ω·Δω)-k_p·P (6)

In formula, ω_refFor output voltage frequency reference value, ω^*For global synchronization frequency, k_pFor meritorious sagging coefficient, P is actual defeated Going out active power, Δ ω is amount of frequency compensation initial value, s_ωFunctional value for frequency estimation function；

Step X5: determine sinusoidal wave real-time phase value, completes the adjustment to phase place, and described sinusoidal wave real-time phase value is true by following formula Fixed:

θ=(1-s_SPR)(θ_p+s_θ*Δe_θ) (7)

In formula, θ is sinusoidal wave real-time phase value；θ_pFor phase place intermediate value；s_SPRFunctional value for phase position bit switch valuation functions； s_θFunctional value for phase evaluation function；Δe_θFor output voltage phase pushing figure；

Step X6: set output voltage amplitude rated value and idle sagging coefficient according to equipment energy characteristic, by output voltage amplitude volume Definite value and idle sagging coefficient and actual output reactive power long-pending poor, obtains output voltage amplitude reference value.