CN106153029A - Two frequency machine shaking laser gyroscope shaking signal cancellation devices - Google Patents
Two frequency machine shaking laser gyroscope shaking signal cancellation devices Download PDFInfo
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- G01C—MEASURING DISTANCES, LEVELS OR BEARINGS; SURVEYING; NAVIGATION; GYROSCOPIC INSTRUMENTS; PHOTOGRAMMETRY OR VIDEOGRAMMETRY
- G01C19/00—Gyroscopes; Turn-sensitive devices using vibrating masses; Turn-sensitive devices without moving masses; Measuring angular rate using gyroscopic effects
- G01C19/58—Turn-sensitive devices without moving masses
- G01C19/64—Gyrometers using the Sagnac effect, i.e. rotation-induced shifts between counter-rotating electromagnetic beams
- G01C19/66—Ring laser gyrometers
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- G01C19/664—Ring laser gyrometers details signal readout; dither compensators means for removing the dither signal
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Abstract
The present invention relates to a kind of two frequency machine shaking laser gyroscope shaking signal cancellation devices, it is technically characterized by comprising the steps as follows: and includes gyro data acquisition module, calculus of differences module, low order FIR filter module, summation operation module, high frequency clock module, low order iir filter module, IIR high pass filter block, the first digital phase shifter module, shake estimation module, digital dock conversion module, the second digital phase shifter module, band filter module, digital dock management module, the 3rd digital phase shifter module and LMS weight coefficient more new module.The present invention is reasonable in design, it uses adaptive interference cancelling technology based on LMS algorithm to carry out shaking laser gyroscope signal cancellation, offset use just, cosine reference signal Dui You mono-road sampled differential signal obtains through signal phase shift, system input and output response is constant when approximating, can reduce to tremble and offset except time delays, can be widely used for eliminating the mechanical shaking signal in two frequency mechanical shaking lasergyro outputs in real time.
Description
Technical field
The invention belongs to two frequency machine laser gyroscope shaking technical fields, especially a kind of two frequency machine shaking laser gyroscope shaking signals
Canceller.
Background technology
Quickly following the tracks of occasion, it is desirable to control system real-time output angle rate information.For mechanical shaking laser gyro, its
Output signal had both comprised the carrier angular movement information that gyro sensitivity arrives, and also comprised mechanical shaking angular movement.In order to obtain carrier angle
Movable information, it is necessary to gyro output signals is demodulated.Typical demodulation scheme mainly has high-speed sampling low-pass filtering and trembles
Dynamic counteracting method, high-speed sampling low-pass filtering is generally completed by FIR low pass filter, the FIR filter exponent number that design obtains
Higher, filtering delay-time is relatively big, is not suitable for quickly following the tracks of applications, and the feature with zero propagation is offset in shake, can be the most defeated
Go out angular rate information, be only applicable to stability contorting etc. and quickly follow the tracks of occasion.
The dither reference signal of existing shake device for stripping is obtained by shake pick-up circuit, before this method needs to be provided with
End modulate circuit, also wants additional A/D conversion chip, adds the complexity of hardware.Generally use the pickup shakes such as piezoelectric ceramics
Signal, piezoelectric ceramics has lagging characteristics, creep properties and dither nonlinear characteristic, piezoelectric ceramics the signal picked up toward
Toward being not real dither signal, show as signal and have non-linear, from frequency spectrum, wherein contain higher harmonic components.
Existing obtaining dither signal from phase-lock technique by gyro, gyro output sampling frequency rate is by fixing sampling clock
Completing, it is impossible to just realizing, cosine dither reference signal strictly differs 90 °, therefore, it is poor that shake divests effect.
Existing obtaining dither signal from phase-lock technique by the logical iir filter of band, when gyro, to be operated in output amplitude bigger
Occasion time, the band filter exponent number designed is higher, be easily caused IIR output dissipate;Further, since iir filter has
Feedback element, it is impossible to realizing full precision cut position during fixed-point calculation, the cut position improper IIR of also resulting in output dissipates, and causes filtering
Failure.
Gyro output is directly carried out after calculus of differences by existing shake device for stripping through adaptive jitter device for stripping
Shake divests, and LMS algorithm is with feedback element, it is impossible to realize the full precision data cut position of fixed-point calculation, in order to improve system
Shake divests effect, it usually needs more word length represents operational data, takies more hardware logic resource, and cut position is not simultaneously
When LMS output can be caused to dissipate, shake divests inefficacy.
Existing shake device for stripping all use two-way phase 90 ° just, cosine dither reference signal is for shaking
Signal estimation and LMS weight coefficient update, and it is not ideal enough that the shake obtained divests effect.
Summary of the invention
It is an object of the invention to overcome the deficiency of existing design, it is provided that a kind of two frequency machine shaking laser gyroscope shaking signals support
Disappear device, solves following problem: 1, existing LMS adaptive jitter divests technology and obtained through band filter by gyro output signals
To dither reference signal, in the bigger occasion of angle increment signal amplitude of gyro output, in order to obtain accurate dither reference signal
Nd, it is higher that the band designed leads to iir filter exponent number, and the iir filter of high-order is computationally intensive, and when realizing in FPGA, cuts
Position is dealt with improperly, and the output of wave filter dissipates, and causes filter normally to work;2, existing LMS adaptive jitter divests
Technology shake estimatorPrecision is poor, and the carrier angular movement precision of information after shake divests is poor, it usually needs increase low order
The exponent number of low-pass FIR filter improves the precision of gyro output carrier angular movement information, and this invention has redesigned shake and estimated
Calculating method, while ensureing Gyro Precision, reduce further the exponent number of low-pass FIR filter, reduces at gyro data
The time delay of reason, improves the real-time of system;3, dither reference signal is obtained through gyro, it is not necessary to outside shake pick-up circuit obtains
Take dither reference signal, simplify the hardware designs that shake is offset, when gyro obtains dither reference signal, devise low order
IIR high pass filter obtains dither reference signal, and devises digital dock transducer (DCC) and realize digital signal and believe to clock
Number conversion, to the clock signal obtained 4M frequency multiplication in FPGA, obtain and the sampling clock of same frequency Tong Bu with dither signal
Gyro output signals is sampled by signal, obtains phase place and strictly differs the dither reference signal of 90 °, thus improves the effect that shake is offset
Really.
The present invention solves it and technical problem is that and take techniques below scheme to realize:
A kind of two frequency machine shaking laser gyroscope shaking signal cancellation devices, including gyro data acquisition module, calculus of differences mould
Block, low order FIR filter module, summation operation module, high frequency clock module, low order iir filter module, IIR high-pass filtering
Device module, the first digital phase shifter module, shake estimation module, digital dock conversion module, the second digital phase shifter module,
Band filter module, digital dock management module, the 3rd digital phase shifter module and LMS weight coefficient more new module;Described top
Spiral shell data acquisition module, low order iir filter module, digital dock conversion module, digital dock management module is sequentially connected
Connecing, another input of low order iir filter module connects high frequency clock module, and described gyro data acquisition module is according to number
Dither signal is sampled by the employing frequency of word clock management module output, and sampled data is the lowest through the output of calculus of differences module
Rank FIR filter module, low order FIR filter module outfan connects IIR high pass filter block and summation operation respectively
Module, the outfan of this IIR high pass filter block connect respectively the first digital phase shifter module, shake estimation module, second
Digital phase shifter module and LMS weight coefficient more new module, the outfan of this first digital phase shifter module connects shake respectively and estimates
Meter module and LMS weight coefficient more new module, the outfan of this second digital phase shifter module connect respectively shake estimation module, the
Three digital phase shifter modules and LMS weight coefficient more new module, the outfan of the 3rd digital phase shifter module connects shake respectively
Estimation module and LMS weight coefficient more new module, the outfan of this shake estimation module connects another input of summation operation module
End, the outfan of this summation operation module connects the input of band filter module, and this band filter module connects LMS power
Coefficient updating module, this LMS weight coefficient more new module output LMS algorithm updates weight coefficient to shaking estimation module.
Described digital dock conversion module is arranged in FPGA, and the sample clock frequency of its output is 4Mfs, wherein, M
For the integer more than or equal to 1, fsFor gyro chattering frequency.
Pulse increment Δ N (the n)=Δ N of described calculus of differences module outputb(n)+ΔNd(n), wherein, Δ Nb(n)、Δ
NdN () represents the gyro base corner motion change in the kth sampling period and mechanical shaking angular movement change respectively;Described low order
Angular movement pulse increment Δ N after FIR filter processlpf(n) be:
ΔNlpf(n)=Δ Nb′(n)+ΔNd' (n):
Wherein, Δ Nb' (n) represents the gyro base corner increment of motion through low order FIR filter, Δ Nd' (n) represents warp
The mechanical shaking angular movement increment signal of overdamping, K is the exponent number representing FIR filter.
Described IIR high pass filter filters the gyro base corner increment of motion Δ N of low order FIR filter outputbAfter ' (n)
Obtain the first dither reference signal Δ Nd1(n): described first digital phase shift module is to Δ Nd1N () obtains the second tunnel after processing and trembles
Dynamic reference signal Δ Nd2(n), Δ Nd2(n)=Δ Nd1(n-1);Described second digital phase shift module is to Δ Nd1N () obtains after processing
With Δ Nd1The 3rd tunnel dither reference signal Δ N of (n) phase 90 °d3(n), this Δ Nd3(n)=Δ Nd1(n-M), M is for being more than
Integer equal to 1;Described 3rd digital phase shift module is to the 3rd tunnel dither reference signal Δ Nd3N () obtains the 4th tunnel after processing and trembles
Dynamic reference signal Δ Nd4(n), Δ Nd4(n)=Δ Nd3(n-1)。
Described LMS weight coefficient more new module is according to four tunnel dither reference signal Δ Nd1(n)、ΔNd2(n)、ΔNd3(n)、Δ
Nd4(n) and band filter output valve ε (n) output LMS algorithm renewal weight coefficient:
h11(n+1)=h11(n)+2×μ×ε(n)×ΔNd2(n)
h12(n+1)=h12(n)+2×μ×ε(n)×ΔNd1(n)
h21(n+1)=h21(n)+2×μ×ε(n)×ΔNd4(n)
h22(n+1)=h22(n)+2×μ×ε(n)×ΔNd3(n)。
Described shake estimation module is according to four tunnel dither reference signal Δ Nd1(n)、ΔNd2(n)、ΔNd3(n)、ΔNd4(n)
And four LMS weight coefficients are to Δ Nd' (n) carries out the estimation estimating to obtain shaking angular movement increment
Wherein h11(n)、h12(n)、h21(n)、h22N () is the weight coefficient in the n-th sampling period.
Advantages of the present invention and good effect be:
1, the present invention obtains dither reference signal by gyroscope, it is no longer necessary to outside shake pick-up circuit obtains shake ginseng
Examine signal, simplify and shake the hardware designs offset, and improve the accuracy of the dither signal of acquisition, thus improve shake
The effect offset.
2, after the present invention uses gyro to obtain dither reference signal, during by design low order IIR high pass filter and numeral
Clock transducer, obtains and the clock signal of same frequency Tong Bu with dither signal, and the chattering frequency for different gyros is different, can make
Sample frequency is the integral multiple of dither signal frequency, shake offset need phase 90 ° just, cosine shake with reference to
In FPGA, phase shift obtains, and can improve shake neutralization effect.
3, the iir filter that the present invention uses is IIR filter, there is feedback element, pinpoints in FPGA
Cannot ensure full precision cut position during computing, the low order FIR filter that can realize full precision fixed-point calculation in FPGA is defeated to gyro
The pulse increment gone out carries out pre-filtering, reduces the amplitude entering high-pass IIR filter pulse increment signal, thus reduces data and exist
Expression figure place in FPGA, improves the figure place of significance bit in the case of identical data figure place, improves shake and offsets precision.
4, the dither reference signal of the present invention obtains through high-pass IIR filter, compares the logical iir filter of band and obtains shake ginseng
Examine the mode of signal, the exponent number of iir filter can be substantially reduced, thus solve High Order IIR Filter for Fix-Point and easily dissipate, cause shake to be supported
Disappear the problem lost, simultaneously the available high-frequency interferencing signal relevant to gyro output medium-high frequency interference, according to adaptive disturbance
Principle of cancellation, offsets part High-frequency Interference when shake is offset, and is beneficial to improve shake neutralization effect.
5, the present invention uses three digital phase shifter modules, available four tunnel dither reference signal, by four LMS power is
Several estimating shaking interference, signal is estimated in available more accurate shake, improves shake neutralization effect further.
6, the present invention is reasonable in design, and it uses adaptive interference cancelling technology based on LMS algorithm to carry out laser gyro and trembles
Dynamic signal cancellation, it is the integral multiple of chattering frequency that sample frequency is offset in shake, offset use just, cosine reference signal is to by one
Road sampled differential signal obtains through signal phase shift, constant during system input and output response approximation, thus reduces and tremble counteracting except the time
Time delay, can be widely used for eliminating the mechanical shaking signal in two frequency mechanical shaking lasergyro outputs in real time.
Accompanying drawing explanation
Fig. 1 is the circuit theory diagrams of the present invention.
Detailed description of the invention
Below in conjunction with accompanying drawing, the embodiment of the present invention is further described:
A kind of two frequency machine shaking laser gyroscope shaking signal cancellation devices, as it is shown in figure 1, include gyro data acquisition module 1,
Calculus of differences module 2, low order FIR filter module 3, summation operation module 4, high frequency clock module 5, low order iir filter mould
Block 6, IIR high pass filter block the 7, first digital phase shifter module 8, shake estimation module 9, digital dock conversion module
10, the second digital phase shifter module 11, band filter module 12, digital dock management module the 13, the 3rd digital phase shifter mould
Block 14, LMS weight coefficient more new module 15.Described gyro data acquisition module 1, low order iir filter module 6, digital dock turn
Parallel operation module 10, digital dock management module 13 is sequentially connected and connects, and another input of low order iir filter module 6 connects
High frequency clock module 5, described gyro data acquisition module 1 exports the employing frequency of 4M frequency multiplication according to digital dock management module 13
Sampling, sampled data exports to low order FIR filter module 3, low order FIR filter module 3 through calculus of differences module 2
Outfan connects IIR high pass filter block 7 and summation operation module 4, the outfan of this IIR high pass filter block 7 respectively
Connect the first digital phase shifter module 8 respectively, shake estimation module the 9, second digital phase shifter module 11 and LMS weight coefficient updates
Module 15, the outfan of this second digital phase shifter module 11 connects shake estimation module the 9, the 3rd digital phase shifter module respectively
14 and LMS weight coefficients more new module 15, the outfan of this first digital phase shifter module 8 connects shake estimation module 9 He respectively
LMS weight coefficient more new module 15, the outfan of the 3rd digital phase shifter module 14 connects shake estimation module 9 and LMS respectively
Weight coefficient more new module 15, the outfan of shake estimation module 9 connects another input of summation operation module 4, summation operation
The outfan of module 4 connects the input of band filter module 12, and this band filter module 12 outfan connects LMS power and is
Number more new module 15, this LMS weight coefficient more new module 15 exports LMS algorithm and updates weight coefficient to shake estimation module 9.
The operation principle of the present invention is: count pulse is sampled in laser gyro output, obtain comprising gyro pedestal after difference
Angular movement and pulse increment Δ N (n) of mechanical shaking angular movement;Pulse increment Δ N (n) is through low order FIR low pass filter 3 pre-flock
Obtain after ripple shaking the gyro base corner motion of pre-decay and the mechanical shaking angular movement pulse increment Δ N of decaylpf(n);Machinery
Shake angular movement pulse increment Δ NlpfN () obtains the reference jitter increment signal after pre-decay after high-pass IIR filter 7
ΔNd1(n);Reference jitter increment signal Δ N after pre-decayd1N () obtains and Δ N after digital phase shifter 11d1N () differs
The reference jitter increment signal Δ N of 90 °d3(n), the reference jitter increment signal Δ N after pre-decayd1N () is through digital phase shifter 8
After obtain reference jitter increment signal Δ Nd2(n), reference jitter increment signal Δ Nd3N () is joined after digital phase shifter 14
Examine shake increment signal Δ Nd4(n);Shake estimation module 9 is according to four tunnel dither reference signal Δ Nd1(n)、ΔNd2(n)、ΔNd3
(n)、ΔNd4N () obtains shaking the estimation of angular movement incrementAnd with Δ NlpfN () is subtracted each other and is obtained inertia angular movement increment
Δs(n);Inertia angular movement increment Delta s (n) passes through LMS weight coefficient more new module 15 and by optimizing after band filter 12
LMS algorithm update weight coefficient h11(n)、h12(n)、h21(n)、h22(n).Laser gyro output counting pulse signal N is through low order
Dither signal N is obtained after IIR high pass filter 6d(n), dither signal NdN () obtains and shake through digital dock transducer 10
Signal synchronizes and the tune width ripple signal f of same frequencys, adjust wide ripple signal fsFrequency signal digital dock manager in FPGA
13 carry out 4M frequency multiplication after obtain the sampling clock Tong Bu with dither reference signal to gyro output signals sample.ΔNd1N () is through letter
Obtain and Δ N after M single sampling delayd1N () differs the increment signal Δ N of 90 °d2N (), the shake so obtained is with reference to letter
Number Δ Nd1(n)、ΔNd2N (), close to preferable cosine and sine signal, inputs Δ NlpfN () offsets the response of output Δ s (n) to shake
When being approximately constant, comparatively ideal shake neutralization effect can be obtained.
Below some key points in the present invention are designed and illustrate:
(1) sampling clock design
Gyro output obtains dither reference signal N through low order IIR high pass filter 6d(n), dither reference signal Nd(n)
Can obtain and dither signal Δ N through digital dock conversion module 10dN () synchronizes and clock signal f of same frequencys:
y1(n)=bl10×(N(n)+bl11×N(n-1)+bl12×N(n-2))+al11×y1(n-1)+al12×y1(n-2)
Nd(n)=y1(n)+bl21×y1(n-1)+bl22×y1(n-2)+al21×Nd(n-1)+al22×Nd(n-2)
fsObtain Tong Bu with dither reference signal after carrying out 4M frequency multiplication by the digital dock management module 13 in FPGA
Sampling clock, sample clock frequency is 4Mfs(M is the integer more than or equal to 1, fsFor gyro chattering frequency).Shake canceller
With 4MfsSample frequency to gyro output signals sample.
(2) design of low pass FIR prefilter
Laser gyro output count pulse is obtained by gyro data acquisition module 1, and its sampled value obtains through calculus of differences module 2
To pulse increment:
Δ N (n)=N (n)-N (n-1)=Δ Nb(n)+ΔNd(n)
Wherein, Δ Nb(n)、ΔNdN () represents the gyro base corner motion change in the kth sampling period and machinery respectively
Shake angular movement change.
Gyro angular movement pulse increment Δ N (n) carries out pre-filtering through low order FIR filter, obtains declining through once shake
The angular movement pulse increment Δ N subtractedlpf(n), Δ NlpfN desired signal that () offsets as shake:
ΔNlpf(n)=h0×ΔN(n)+h1×ΔN(n-1)+h2×ΔN(n-2)+…+hK-1×ΔN(n-K+1)+hK×
Δ N (n-K)=Δ Nb′(n)+ΔNd′(n)
Wherein, Δ Nb' (n) represents the gyro base corner increment of motion through FIR filter, Δ Nd' (n) represents through declining
The mechanical shaking angular movement increment signal subtracted, K is the exponent number representing FIR filter, designs difference according to the actual demand of system
The FIR filter of exponent number, the preferred recommendation of K may be selected to be K=35.
(3) acquisition of dither reference signal
Dither reference signal Δ Nd1N () is given by high pass filter 7.ΔNlpfN () filters gyro base through high pass filter 7
Seat angular movement increment Delta Nb' (n), obtains gyro mechanical shaking angular movement increment Delta N that a road is more satisfactoryd1(n):
order1(n)=b10×(ΔNlpf(n)+b11×ΔNlpf(n-1)+b12×ΔNlpf(n-2))+a11×order1
(n-1)+a12×order1(n-2)
order2(n)=order1(n)+b21×order1(n-1)+b22×order1(n-2)+a21×order2(n-1)+
a22×order2(n-2)
order3(n)=order2(n)+b31×order2(n-1)+b32×order2(n-2)+a31×order3(n-1)+
a32×order3(n-2)
order4(n)=order3(n)+b41×order3(n-1)+b42×order3(n-2)+a41×order4(n-1)+
a42×order4(n-2)
ΔNd1(n)=order4(n)+b51×order4(n-1)+b52×order4(n-2)+a51×ΔNd1(n-1)+a52
×ΔNd1(n-2)
ΔNd1N () obtains the second tunnel dither reference signal Δ N after digital phase shift module 8 phase shiftd2(n):
ΔNd2(n)=Δ Nd1(n-1)
ΔNd1N () obtains and Δ N after digital phase shift module 11 phase shiftd1The 3rd tunnel shake ginseng of (n) phase 90 °
Examine signal delta Nd3(n):
ΔNd3(n)=Δ Nd1(n-M)
Owing to sample frequency is 4Mfs, the most no matter gyro chattering frequency fsHow to change, Δ Nd1(n)、ΔNd3Between (n)
Phase place differ 90 ° all the time, correspondingly shake offset be input to shake offset output response approximation time constant, shake can be improved
Neutralization effect.
ΔNd3N () obtains the 4th tunnel dither reference signal Δ N after digital phase shift module 14 phase shiftd4(n):
ΔNd4(n)=Δ Nd3(n-1)
(4) design of algorithm for estimating is shaken
Shake estimation module 9 passes through four tunnel dither reference signal and four LMS weight coefficients to Δ Nd' (n) estimates
Obtain
Wherein h11(n)、h12(n)、h21(n)、h22N () is the weight coefficient in the n-th sampling period, they are updated by weight coefficient
Algoritic module 15 determines.
(5) the weight coefficient update algorithm design of LMS
The weight coefficient update algorithm of LMS passes through four tunnel dither reference signal Δ Nd1(n)、ΔNd2(n)、ΔNd3(n)、ΔNd4
N ε (n) that the output of () and band filter obtains is updated, and its concrete update algorithm is as follows:
h11(n+1)=h11(n)+2×μ×ε(n)×ΔNd2(n)
h12(n+1)=h12(n)+2×μ×ε(n)×ΔNd1(n)
h21(n+1)=h21(n)+2×μ×ε(n)×ΔNd4(n)
h22(n+1)=h22(n)+2×μ×ε(n)×ΔNd3(n)
(6) gyro base corner increment of motion
Increment Delta NlpfN () is estimated with shakeObtain shake through summation operation module 4 and offset output Δ s (n), Δ s
N () is gyro base corner increment of motion, the gyro output useful signal that i.e. filters solutions is to be obtained, shake is offset output s (n) and is
Gyro base corner increment of motion Δ NbThe approximation of (n).Shake cancellation algorithms is as follows:
(7) design of band filter
Updating and shake neutralization effect for preventing low frequency or the motion of constant gyro base corner from affecting weight coefficient, shake is offset
Output s (n) will be used further to weight coefficient after band filter 12 eliminates the motion of gyro base corner and update.Band filter algorithm is such as
Under:
ε (n)=-Δ s (n)+Δ s (n-1)+Δ s (n-2)-Δ s (n-3)
8, complete shake cancellation algorithms
The shake cancellation algorithms that the present invention is complete is:
y1(n)=bl10×(N(n)+bl11×N(n-1)+bl12×N(n-2))+al11×y1(n-1)+al12×y1(n-2)
Nd(n)=y1(n)+bl21×y1(n-1)+bl22×y1(n-2)+al21×Nd(n-1)+al22×Nd(n-2)
ΔNlpf(n)=h0×ΔN(n)+h1×ΔN(n-1)+h2×ΔN(n-2)+…+hK-1×ΔN(n-K+1)+hK×
ΔN(n-K)
order1(n)=b10×(ΔNlpf(n)+b11×ΔNlpf(n-1)+b12×ΔNlpf(n-2))+a11×order1
(n-1)+a12×order1(n-2)
order2(n)=order1(n)+b21×order1(n-1)+b22×order1(n-2)+a21×order2(n-1)+
a22×order2(n-2)
order3(n)=order2(n)+b31×order2(n-1)+b32×order2(n-2)+a31×order3(n-1)+
a32×order3(n-2)
order4(n)=order3(n)+b41×order3(n-1)+b42×order3(n-2)+a41×order4(n-1)+
a42×order4(n-2)
ΔNd1(n)=order4(n)+b51×order4(n-1)+b52×order4(n-2)+a51×ΔNd1(n-1)+a52
×ΔNd1(n-2)
ΔNd2(n)=Δ Nd1(n-1)
ΔNd3(n)=Δ Nd1(n-M)
ΔNd4(n)=Δ Nd3(n-1)
ε (n)=-Δ s (n)+Δ s (n-1)+Δ s (n-2)-Δ s (n-3)
h11(n+1)=h11(n)+2×μ×ε(n)×ΔNd2(n)
h12(n+1)=h12(n)+2×μ×ε(n)×ΔNd1(n)
h21(n+1)=h21(n)+2×μ×ε(n)×ΔNd4(n)
h22(n+1)=h22(n)+2×μ×ε(n)×ΔNd3(n)
It is emphasized that embodiment of the present invention is illustrative rather than determinate, bag the most of the present invention
Include the embodiment being not limited to described in detailed description of the invention, every by those skilled in the art according to technical scheme
Other embodiments drawn, also belong to the scope of protection of the invention.
Claims (6)
1. a frequency machine shaking laser gyroscope shaking signal cancellation device, it is characterised in that: include gyro data acquisition module, difference
Divide computing module, low order FIR filter module, summation operation module, high frequency clock module, low order iir filter module, IIR
High pass filter block, the first digital phase shifter module, shake estimation module, digital dock conversion module, the second numeral are moved
Phase device module, band filter module, digital dock management module, the 3rd digital phase shifter module and LMS weight coefficient update mould
Block;Described gyro data acquisition module, low order iir filter module, digital dock conversion module, digital dock management module
Being sequentially connected and connect, another input of low order iir filter module connects high frequency clock module, and described gyro data gathers mould
Dither signal is sampled by block according to the employing frequency of digital dock management module output, and sampled data is through calculus of differences module
Output to low order FIR filter module, low order FIR filter module outfan connect respectively IIR high pass filter block and
Summation operation module, the outfan of this IIR high pass filter block connects the first digital phase shifter module respectively, mould is estimated in shake
Block, the second digital phase shifter module and LMS weight coefficient more new module, the outfan of this first digital phase shifter module connects respectively
Shake estimation module and LMS weight coefficient more new module, the outfan of this second digital phase shifter module connects shake respectively and estimates
Module, the 3rd digital phase shifter module and LMS weight coefficient more new module, the outfan of the 3rd digital phase shifter module connects respectively
Connecing shake estimation module and LMS weight coefficient more new module, the outfan of this shake estimation module connects the another of summation operation module
One input, the outfan of this summation operation module connects the input of band filter module, and this band filter module is even
Connecing LMS weight coefficient more new module, this LMS weight coefficient more new module output LMS algorithm updates weight coefficient to shaking estimation module.
Two frequency machine shaking laser gyroscope shaking signal cancellation devices the most according to claim 1, it is characterised in that: described numeral
Clock converter module is arranged in FPGA, and the sample clock frequency of its output is 4Mfs, wherein, M is whole more than or equal to 1
Number, fsFor gyro chattering frequency.
Two frequency machine shaking laser gyroscope shaking signal cancellation devices the most according to claim 1, it is characterised in that: described difference
Pulse increment Δ N (the n)=Δ N of computing module outputb(n)+ΔNd(n), wherein, Δ Nb(n)、ΔNdN () represents kth respectively
Gyro base corner motion change in the individual sampling period and mechanical shaking angular movement change;After described low order FIR filter processes
Angular movement pulse increment Δ Nlpf(n) be:
ΔNlpf(n)=Δ N 'b(n)+ΔN′d(n):
Wherein, Δ N 'bN () represents the gyro base corner increment of motion through low order FIR filter, Δ N 'dN () represents through declining
The mechanical shaking angular movement increment signal subtracted, K is the exponent number representing FIR filter.
Two frequency machine shaking laser gyroscope shaking signal cancellation devices the most according to claim 1, it is characterised in that: described IIR
High pass filter filters the gyro base corner increment of motion Δ N ' of low order FIR filter outputbThe first shake reference is obtained after (n)
Signal delta Nd1(n): described first digital phase shift module is to Δ Nd1N () obtains the second tunnel dither reference signal Δ N after processingd2
(n), Δ Nd2(n)=Δ Nd1(n-1);Described second digital phase shift module is to Δ Nd1N () obtains and Δ N after processingd1(n) phase place
Differ the 3rd tunnel dither reference signal Δ N of 90 °d3(n), this Δ Nd3(n)=Δ Nd1(n-M), M is the integer more than or equal to 1;
Described 3rd digital phase shift module is to the 3rd tunnel dither reference signal Δ Nd3N () obtains the 4th tunnel dither reference signal Δ after processing
Nd4(n), Δ Nd4(n)=Δ Nd3(n-1)。
Two frequency machine shaking laser gyroscope shaking signal cancellation devices the most according to claim 1, it is characterised in that: described LMS
Weight coefficient more new module is according to four tunnel dither reference signal Δ Nd1(n)、ΔNd2(n)、ΔNd3(n)、ΔNd4The logical filter of (n) and band
Ripple device output valve ε (n) output LMS algorithm renewal weight coefficient:
h11(n+1)=h11(n)+2×μ×ε(n)×ΔNd2(n)
h12(n+1)=h12(n)+2×μ×ε(n)×ΔNd1(n)
h21(n+1)=h21(n)+2×μ×ε(n)×ΔNd4(n)
h22(n+1)=h22(n)+2×μ×ε(n)×ΔNd3(n)。
Two frequency machine shaking laser gyroscope shaking signal cancellation devices the most according to claim 1, it is characterised in that: described shake
Estimation module is according to four tunnel dither reference signal Δ Nd1(n)、ΔNd2(n)、ΔNd3(n)、ΔNd4(n) and four LMS weight coefficients
To Δ N 'dN () carries out the estimation estimating to obtain shaking angular movement increment
Wherein h11(n)、h12(n)、h21(n)、h22N () is the weight coefficient in the n-th sampling period.
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CN114838720A (en) * | 2021-02-02 | 2022-08-02 | 湖南二零八先进科技有限公司 | Self-adaptive jitter stripping method and device for laser gyroscope |
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