CN105991033A - Power converter without electrolytic capacitor at input side - Google Patents
Power converter without electrolytic capacitor at input side Download PDFInfo
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- CN105991033A CN105991033A CN201510060040.XA CN201510060040A CN105991033A CN 105991033 A CN105991033 A CN 105991033A CN 201510060040 A CN201510060040 A CN 201510060040A CN 105991033 A CN105991033 A CN 105991033A
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- voltage
- pulsating
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- produce
- ocp
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- 239000003990 capacitor Substances 0.000 title claims abstract description 57
- 239000010409 thin film Substances 0.000 claims description 46
- 239000000411 inducer Substances 0.000 claims description 13
- 230000009286 beneficial effect Effects 0.000 abstract 1
- 238000005868 electrolysis reaction Methods 0.000 description 16
- 239000004973 liquid crystal related substance Substances 0.000 description 9
- 238000010586 diagram Methods 0.000 description 8
- 230000005611 electricity Effects 0.000 description 8
- 238000004146 energy storage Methods 0.000 description 8
- 230000000694 effects Effects 0.000 description 5
- 230000010349 pulsation Effects 0.000 description 5
- 238000001914 filtration Methods 0.000 description 4
- 230000008859 change Effects 0.000 description 3
- 239000003792 electrolyte Substances 0.000 description 3
- 101100464779 Saccharomyces cerevisiae (strain ATCC 204508 / S288c) CNA1 gene Proteins 0.000 description 2
- 238000000034 method Methods 0.000 description 2
- 230000008569 process Effects 0.000 description 2
- 230000002159 abnormal effect Effects 0.000 description 1
- 210000001367 artery Anatomy 0.000 description 1
- 230000008901 benefit Effects 0.000 description 1
- 238000006243 chemical reaction Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 239000010408 film Substances 0.000 description 1
- 239000012528 membrane Substances 0.000 description 1
- 239000002985 plastic film Substances 0.000 description 1
- 229920006255 plastic film Polymers 0.000 description 1
- 230000008439 repair process Effects 0.000 description 1
- 230000009466 transformation Effects 0.000 description 1
- 210000003462 vein Anatomy 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4258—Arrangements for improving power factor of AC input using a single converter stage both for correction of AC input power factor and generation of a regulated and galvanically isolated DC output voltage
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Physics & Mathematics (AREA)
- Electromagnetism (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention relates to a power converter, which comprises a bridge rectifier, a film capacitor and a direct current-direct current (DC/DC) converter. The bridge rectifier rectifies an input voltage of an AC power source to generate a full-wave rectified voltage. The film capacitor filters the full-wave rectified voltage to generate a first pulsating direct current voltage. The control circuit of the DC/DC converter attenuates the first pulsating direct current voltage to generate a second pulsating direct current voltage, detects the wave crest value and the wave trough value of the second pulsating direct current voltage, and accordingly generates an over-current protection (OCP) compensation value of- (Vx-VH) + PH, wherein Vx is the second pulsating direct current voltage, and VH and PH are the wave trough value and the wave crest value of the second pulsating direct current voltage respectively. The control circuit adds the compensated OCP set value generated by the OCP compensation value to the OCP set value to limit the OCP and the constant power output of the DC/DC converter. The invention has the beneficial effect of realizing OCP and constant power output limitation.
Description
Technical field
The invention relates to a kind of power supply changeover device, and particularly a kind of input side does not use electrochemical capacitor
The power supply changeover device of device, is applicable to small-size liquid crystal displays.
Background technology
Refer to the circuit of the power supply changeover device that Fig. 1, Fig. 1 are a kind of existing small-size liquid crystal displays
Block chart.Existing power supply changeover device 1 include electromagnetic interference (electromagnetic interference,
EMI) wave filter 11, bridge rectifier 12, electrolysis condenser 13 and direction flyback converter (flyback
converter)14.Alternating current power supply first passes through electromagnetic interface filter 11 and filters Conducted EMI noise therein,
Its input voltage is rectified into full-wave rectified voltage through bridge rectifier 12 again, then by electrolysis condenser
13 filtering and energy storage become a galvanic current pressure Vdc.This is because the capacitance of electrolysis condenser 13
Relatively big, the energy storage effect compared with multi-energy can be stored preferable so that the two ends cross-pressure Vdc of electrolysis condenser 13
Ripple minimum and can be considered a galvanic current potential source.This DC voltage Vdc is again through flyback
Formula transducer 14 is converted into rated output voltage Vo1 and Vo2.Output voltage Vo1 e.g. 12V or 16V,
Light emitting diode (light-emitting diode, the LED) backlight drive of liquid crystal display can be supplied electricity to
Circuit and display panel, drive circuit, and output voltage Vo2 e.g. 5V, can supply electricity to liquid crystal display
Mainboard.
Direction flyback converter 14 includes change-over circuit and control circuit thereof, and wherein, change-over circuit includes transformation
Device T1, power transistor Q1, diode D1 and D2 and capacitor C1 and C2, and control circuit includes
PWM (pulse-width modulation, PWM) controller U1, resistor R1 and R2, two
Pole pipe D3, capacitor C3 and C4 and output feedback circuit FB1.In order to make the output of power supply changeover device 1
Power (i.e. the output of direction flyback converter 14) can be protected and limited, direction flyback converter
The control circuit of 14 can add overcurrent detecting function, use in this example and there is overcurrent protection (over
Current protection, OCP) PWM controller U1 of function, the e.g. collection of model EM8672
Becoming circuit, it has seven foot positions CT, COMP, CS, GND, OUT, VCC, HV, does not goes to live in the household of one's in-laws on getting married
State each foot bit function.PWM controller U1 built-in OCP comparator CMP1 realizes OCP function, and it leads to
Cross the two ends cross-pressure Vr1 of the resistor R1 of concatenation below foot position CS crawl power transistor Q1 to come with fixing
OCP setting value Vset compare, if the voltage Vr1 captured is more than OCP setting value Vset, then table
Showing that the output of direction flyback converter 14 has been above rated value, control circuit is required for change-over circuit
Protecting, the control logic circuit CTRL1 of such as PWM controller U1 can limit and export from foot position OUT
To the responsibility cycle (duty cycle) of the pwm control signal of power transistor Q1 or directly close power
Transistor Q1, to reach OCP and to determine power export-restriction.In the occasion of different rated output powers,
Also have only to the resistance value size revising resistor R1 limit to change rated output power.
Existing power supply changeover device 1 uses electrolysis condenser 13 by front end bridge rectifier 12 at input side
Full-wave rectified voltage filtering and energy storage that rectifier obtains become a galvanic current pressure Vdc, therefore electrolysis is electric
Container 13 its two ends cross-pressure Vdc in normal operation is i.e. the peak value of power input voltage.With 220Vrms
As a example by city's power supply, the two ends cross-pressure Vdc of electrolysis condenser 13 is about 311V.Such high voltage meeting
It is greatly increased on electrolysis condenser 13 electrode the electrostatic energy gathered, and accumulates in electrolysis condenser 13
Interior electrostatic energy (such as power input voltage is abnormal to be raised) under certain conditions can directly pass through
Between electrode, arcing sparks over, and then causes the electrolyte in electrolysis condenser 13 and element paper combustible
Burn.
Summary of the invention
The purpose of the present invention is exactly to propose a kind of power supply changeover device, and it does not use electrochemical capacitor at input side
Device, escapable cost and avoid electrolysis condenser it may happen that the problem of burning, and OCP and fixed can be realized
Power export-restriction.
In order to reach above-mentioned purpose and other purpose, the present invention proposes a kind of power supply changeover device, and it includes bridge
Formula commutator, thin film capacitor and dc-dc (direct-current to direct-current,
DC/DC) transducer, wherein, DC/DC transducer includes control circuit.Bridge rectifier receives alternating current
Source input voltage, and power input voltage is carried out rectification to produce full-wave rectified voltage.Thin film capacitor
Receive full-wave rectified voltage, and be filtered full-wave rectified voltage producing the first pulsating dc voltage.
Control circuit receives the first pulsating dc voltage, decays to produce second to the first pulsating dc voltage
Pulsating dc voltage, detects crest value and the valley value of the second pulsating dc voltage, and according to the second pulsation
DC voltage, crest value and valley value are to produce OCP offset, and this OCP offset is
-(Vx-VH)+PH, wherein, Vx is the second pulsating dc voltage, and VH is valley value, and PH is crest value.
Control circuit according to OCP setting value plus OCP setting value through overcompensation produced by OCP offset,
DC/DC transducer is carried out OCP and determines power export-restriction.
In one embodiment of this invention, control circuit include attenuator, peak valley holding circuit, subtractor,
Phase inverter and adder.First pulsating dc voltage is decayed to produce the second pulsating direct current by attenuator
Voltage.Peak valley holding circuit detects crest value and the valley value of the second pulsating dc voltage.Subtractor is by
Two pulsating dc voltages deduct valley value to produce the first voltage.Phase inverter by the first voltage inversion with produce
Second voltage.Second voltage is added that crest value and OCP setting value are to produce the OCP through overcompensation by adder
Setting value.
In another embodiment of the invention, control circuit includes attenuator, peak valley holding circuit, subtraction
Device, phase inverter and adder.First pulsating dc voltage is decayed to produce the second pulsation by attenuator
DC voltage.Peak valley holding circuit detects crest value and the valley value of the second pulsating dc voltage.Subtractor
Second pulsating dc voltage is deducted crest value to produce the first voltage.Phase inverter by the first voltage inversion with
Produce the second voltage.Second voltage is added that valley value and OCP setting value are to produce through overcompensation by adder
OCP setting value.
In another embodiment of the invention, control circuit includes attenuator, peak valley holding circuit, anti-phase
Device and adder.First pulsating dc voltage is decayed to produce the second pulsating dc voltage by attenuator.
Peak valley holding circuit detects crest value and the valley value of the second pulsating dc voltage.Phase inverter is pulsed second
DC voltage is anti-phase to produce a voltage.The voltage that phase inverter is exported by adder adds crest value, trough
Value and OCP setting value are to produce the OCP setting value through overcompensation.
In one embodiment of this invention, power supply changeover device also includes electromagnetic interface filter, and bridge rectifier leads to
Cross electromagnetic interface filter and receive power input voltage.
In one embodiment of this invention, power supply changeover device also includes inducer, described inducer and described
Thin film capacitor forms the LC low pass filter being coupled between bridge rectifier and DC/DC transducer.
In another embodiment of the invention, power supply changeover device also includes inducer and another thin film capacitor,
Described inducer, described thin film capacitor and another thin film capacitor described composition are coupled to bridge rectifier
And the π type low pass filter between DC/DC transducer.
In one embodiment of this invention, DC/DC transducer includes direction flyback converter.
The power supply changeover device of the present invention uses thin film capacitor to instead of existing conventional electrolysis electricity at input side
Container, because of thin film capacitor without electrolyte and element paper combustible, so will not as electrolysis condenser has can
The problem that burning can occur, and thin film capacitor cost is also below electrolysis condenser, additionally, the present invention
The control circuit of power supply changeover device also captures the two ends cross-pressure (the i.e. first pulsating dc voltage) of thin film capacitor
And carry out decaying, anti-phase etc. process after is added with OCP setting value with generation through the OCP setting value of overcompensation,
This is transformator primary side in the DC/DC transducer that the OCP setting value of overcompensation captures with control circuit again
Voltage corresponding to electric current is compared to OCP and can reach and determine power export-restriction, can be because of difference
Load causes the first Rectified alternating current still can realize in the case of being pressed with different ripple size determining power output limit
System.
For the above-mentioned purpose of the present invention, feature and advantage more can be become apparent, hereafter will with embodiment also
Coordinate institute's accompanying drawings, be described in detail below.It is noted that each assembly in institute's accompanying drawings only shows
Meaning, does not illustrate according to the actual ratio of each assembly.
Accompanying drawing explanation
Fig. 1 is the circuit block diagram of the power supply changeover device of a kind of existing small-size liquid crystal displays.
Fig. 2 is the circuit side of the power supply changeover device of the small-size liquid crystal displays according to one embodiment of the invention
Block figure.
Fig. 3 is the oscillogram of two ends cross-pressure when weight carries of thin film capacitor shown in Fig. 2.
Fig. 4 is the oscillogram that OCP shown in Fig. 2 compensates each node voltage of circuit.
Fig. 5 is the circuit block diagram that OCP shown in Fig. 2 compensates another embodiment of circuit.
Fig. 6 is the circuit block diagram that OCP shown in Fig. 2 compensates the another embodiment of circuit.
Fig. 7 is the circuit diagram of another embodiment of thin film capacitor shown in Fig. 2.
Fig. 8 is the circuit diagram of the another embodiment of thin film capacitor shown in Fig. 2.
Embodiment
Refer to the power supply that Fig. 2, Fig. 2 are the small-size liquid crystal displays according to one embodiment of the invention turn
The circuit block diagram of parallel operation.The power supply changeover device 2 of the present invention includes electromagnetic interface filter 11, bridge rectifier
12, thin film capacitor (film capacitor) 23 and DC/DC transducer 24, wherein, thin-film capacitor
Device is also known as plastic film capacitor.Power supply first passes through electromagnetic interface filter 11 and filters Conducted EMI therein and make an uproar
Sound, its input voltage is rectified into full-wave rectified voltage through bridge rectifier 12 again, then by thin-film capacitor
Device 23 filters and energy storage becomes a first pulsating dc voltage Va.This is because the electricity of thin film capacitor 23
Capacitance is less, it is impossible to store too many energy and energy storage effect is poor so that the two ends of thin film capacitor 23 across
The waveform of pressure Va is illustrated in figure 3 a pulsating direct current waveform and its ripple size can be along with load weight
Difference, therefore the two ends cross-pressure Va of thin film capacitor 23 is also called the first pulsating dc voltage.
Referring to Fig. 3, when loading light when, power supply input stores the energy to thin film capacitor 23
More than the demand of output loading, now thin film capacitor 23 starts to store energy so that its two ends cross-pressure is (i.e.
First pulsating dc voltage) waveform of Va is the pulsating direct current waveform that a ripple is less, has shallower
Trough.When load weight when, thin film capacitor 23 is because of energy storage weak effect so that its two ends cross-pressure is (i.e.
First pulsating dc voltage) waveform of Va is the pulsating direct current waveform that a ripple is bigger, have relatively deep and
Significantly trough, especially when loading the heaviest when, the ripple of the two ends cross-pressure Va of thin film capacitor 23
Shape can be closer to the waveform of full-wave rectified voltage.Therefore, although the ripple of the first pulsating dc voltage Va is big
Little being as loading weight and different, but the crest value of the first pulsating dc voltage Va is changeless
(being i.e. the peak value of power input voltage), variation is its valley value.
Continuing with seeing Fig. 2, the present invention uses thin film capacitor 23 to instead of electrolysis electricity as shown in Figure 1
Container 13, because thin film capacitor 23 is without electrolyte and element paper combustible, so will not be as electrochemical capacitor
The problem that device 13 is likely to occur burning.First pulsating dc voltage Va is again through DC/DC transducer 24
It is converted into rated output voltage Vo1 and Vo2.Output voltage Vo1 e.g. 12V or 16V, can supply electricity to
The LED backlight drive circuit of liquid crystal display and display panel, drive circuit, and output voltage Vo2 is such as
It is 5V, the mainboard of liquid crystal display can be supplied electricity to.In the present embodiment, DC/DC transducer 24 uses such as
Direction flyback converter 14 shown in Fig. 1, but nowadays it is to receive the first arteries and veins due to DC/DC transducer 24
Dynamic DC voltage Va rather than galvanic current pressure Vdc as shown in Figure 1, in order to make DC/DC transducer 24
Output decapacitation protected and limit outer and must also be to determine power export-restriction, the therefore present invention
Direction flyback converter 14 has inside PWM controller U1 of OCP function and add for OCP merit
The compensation circuit 25 of energy, in order to PWM controller U2 adding OCP compensation circuit 25 can reach OCP
And determine power export-restriction.Specifically, in the present embodiment, DC/DC transducer 24 turns for flyback
Parallel operation, it includes change-over circuit and control circuit thereof, and wherein, change-over circuit includes transformator T1, power
Transistor Q1, diode D1 and D2 and capacitor C1 and C2, and control circuit includes PWM controller
U2, resistor R1 and R2, diode D3, capacitor C3 and C4 and output feedback circuit FB1.
The most referring also to Fig. 2 and Fig. 4, Fig. 4 are each node voltage that OCP shown in Fig. 2 compensates circuit 25
Oscillogram.PWM controller U2 is in PWM controller U1 (the e.g. model with OCP function
The integrated circuit of EM8672) internal add the compensation circuit 25 for OCP function, it has seven feet
Position CT, COMP, CS, GND, OUT, VCC, HV, the most do not repeat each foot bit function.OCP compensates
Circuit 25 includes attenuator 251, peak valley holding circuit 252, subtractor 253, phase inverter 254 and adds
Musical instruments used in a Buddhist or Taoist mass 255.The bleeder circuit that the resistor that attenuator 251 is e.g. coupled by multiple connection in series-parallel is formed,
It receives the first pulsating dc voltage Va by foot position HV and resistor R2, and to the first Rectified alternating current
Pressure Va carry out decay X times to produce the second pulsating dc voltage Vx, i.e. Vx=Va/X, X is real number.
It is to reduce its voltage quasi position by the first pulsating dc voltage Va decay X times to allow OCP compensate circuit
25 internal follow-up circuit are carried out calculation process, and the second pulsating direct current of generation after X times that decays
Voltage Vx and the first proportional example of pulsating dc voltage Va, the i.e. second pulsating dc voltage Vx contains first
Pulsating dc voltage Va is caused the information of different ripple sizes (or valley value) because of different loads.
The crest value PH of peak valley holding circuit 252 Cycle by Cycle ground detecting the second pulsating dc voltage Vx and valley value
VH also keeps with output.
Second pulsating dc voltage Vx is deducted valley value VH to produce the first voltage Vc by subtractor 253,
I.e. Vc=Vx-VH.It is to pulse second that second pulsating dc voltage Vx deducts valley value VH
Valley value different because different loads is caused for DC voltage Vx compensates, therefore produced first voltage
Vc is one does not has DC level and along with the second pulsating dc voltage Vx (or the first pulsating dc voltage
Va) pulsating waveform changed and change.Phase inverter 254 by anti-phase for the first voltage Vc to produce the second voltage
Vi, i.e. Vi=-Vc, therefore produced second voltage Vi is one does not has DC level and along with second
The pulsating waveform that pulsating dc voltage Vx (or first pulsating dc voltage Va) changes and reversely changes.
Second voltage Vi is added that crest value PH and fixing OCP setting value Vset are to produce by adder 255
Raw OCP setting value Vocp through overcompensation, i.e. Vocp=Vi+PH+Vset.By the second voltage Vi
Plus crest value PH (being i.e. the peak value of power input voltage) be in order to produce one can be to fixing OCP
Setting value Vset compensates to reach to determine the OCP offset Vcp, i.e. Vcp=Vi of power export-restriction
+PH.First, OCP offset Vcp is as the first pulsating dc voltage Va variation and reversely changes,
Therefore at the first pulsating dc voltage Va crest, make through overcompensation with less OCP offset Vcp
OCP setting value Vocp is less, and the electric current that transformator T1 primary side is flow through in its restriction is less, and first
At pulsating dc voltage Va trough, the OCP through overcompensation is made to set with bigger OCP offset Vcp
Value Vocp is relatively big, and it limits, and to flow through the electric current of transformator T1 primary side relatively big, therefore can reach OCP and
Determine power export-restriction.Secondly, will there is no DC level and along with the first pulsating dc voltage Va variation
Reversely the second voltage Vi of variation is plus crest value PH (being i.e. the peak value of power input voltage), can make
It sets the rated output power limited under the same conditions can be suitable with that shown in Figure 1.
PWM controller U2 built-in OCP comparator CMP1 realizes OCP function, and it is grabbed by foot position CS
Take the two ends cross-pressure Vr1 of the resistor R1 of concatenation below power transistor Q1 to come and the OCP through overcompensation
Setting value Vocp compares, if the voltage Vr1 captured is more than OCP setting value Vocp through overcompensation,
Then representing that the output of DC/DC transducer 24 has been above rated value, control circuit is required for conversion
Circuit is protected, and the control logic circuit CTRL1 of such as PWM controller U2 can limit from foot position OUT
Output is arrived the responsibility cycle of the pwm control signal of power transistor Q1 or directly closes power transistor Q1,
To reach OCP and to determine power export-restriction.In the occasion of different rated output powers, also have only to repair
The resistance value size changing resistor R1 limits to change rated output power.
It should be noted that in the present embodiment, OCP setting value Vset is to be pre-set in PWM control
Unmodifiable fixed value in device U2, but it is not limited only to this；Such as, OCP setting value Vset is also
May be designed to the foot position by PWM controller be set by outside, but after once external setting-up completes,
Its OCP setting value Vset is also a fixed value.Additionally, OCP offset Vcp=Vi+PH=-Vc
+ PH=-(Vx-VH)+PH.This formula of Vcp=-(Vx-VH)+PH can be merely from mathematics
Viewpoint is changed, such as Vcp=-(Vx-PH)+VH, the most such as Vcp=-Vx+PH+VH,
Therefore the embodiment of OCP compensation circuit is not limited only to the OCP compensation circuit 25 described in the present embodiment.
Referring to Fig. 5, Fig. 5 is the circuit box that OCP shown in Fig. 2 compensates another embodiment of circuit 25
Figure.OCP compensates circuit 35 and includes attenuator 351, peak valley holding circuit 352, subtractor 353, anti-phase
Device 354 and adder 355.Attenuator 351 carries out decay X times to produce to the first pulsating dc voltage Va
Raw second pulsating dc voltage Vx, i.e. Vx=Va/X.The detecting of peak valley holding circuit 352 Cycle by Cycle ground
The crest value PH and valley value VH of the second pulsating dc voltage Vx also keep with output.Subtractor 353 will
Second pulsating dc voltage Vx deducts crest value PH to produce along with the first pulsating dc voltage Va variation
First voltage V1, i.e. V1=Vx-PH of variation.Phase inverter 354 by anti-phase for the first voltage V1 with produce
Raw the second voltage V2, i.e. V2=-V1 reversely changed along with the first pulsating dc voltage Va variation.
Second voltage V2 is added that valley value VH and fixing OCP setting value Vset are to produce warp by adder 355
OCP setting value Vocp of overcompensation, i.e. Vocp=V2+VH+Vset=-V1+VH+Vset=
-(Vx-PH)+VH+Vset, now OCP offset Vcp=-(Vx-PH)+VH.
Referring to Fig. 6, Fig. 6 is the circuit box that OCP shown in Fig. 2 compensates the another embodiment of circuit 25
Figure.OCP compensates circuit 45 and includes attenuator 451, peak valley holding circuit 452, phase inverter 453 and add
Musical instruments used in a Buddhist or Taoist mass 454.Attenuator 451 carries out decay X times to produce the second pulsation to the first pulsating dc voltage Va
DC voltage Vx, i.e. Vx=Va/X.Detecting the second pulsation in peak valley holding circuit 452 Cycle by Cycle ground is straight
Flow the crest value PH and valley value VH of voltage Vx and keep with output.Phase inverter 453 is by straight for the second pulsation
Stream voltage Vx is anti-phase to produce the voltage V3 reversely changed along with the first pulsating dc voltage Va variation,
I.e. V3=-Vx.Voltage V3 is added crest value PH, valley value VH and fixing OCP by adder 454
Setting value Vset is to produce OCP setting value Vocp through overcompensation, i.e. Vocp=V3+PH+VH+
Vset=-Vx+PH+VH+Vset, now OCP offset Vcp=-Vx+PH+VH.
Referring to Fig. 7, Fig. 7 is the circuit diagram of another embodiment of thin film capacitor 23 shown in Fig. 2.?
In the present embodiment, thin film capacitor 23 is with the replacement of a LC low pass filter 33.LC low pass filter
33 are made up of inducer L1 and thin film capacitor C5, and LC low pass filter 33 is coupled to bridge rectifier
Between device 12 and DC/DC transducer 24.Wherein, thin film capacitor C5 can be i.e. thin shown in Fig. 2
Membrane capacitance 23, in other words, LC low pass filter 33 can be at the thin film capacitor shown in Fig. 2
23 front one inducer L1 of concatenation realize.LC low pass filter 33 has than single thin film capacitor
23 preferably filter and energy storage effect.
Refer to the circuit diagram of the another embodiment that Fig. 8, Fig. 8 are thin film capacitor 23 shown in Fig. 2.?
In the present embodiment, thin film capacitor 23 is with π type low pass filter 43 replacement.π type low-pass filtering
Device 43 is made up of thin film capacitor C6, inducer L1 and thin film capacitor C5, and π type low-pass filtering
Device 43 is coupled between bridge rectifier 12 and DC/DC transducer 24.Wherein, thin film capacitor C5
Can be i.e. the thin film capacitor 23 shown in Fig. 2, in other words, π type low pass filter 43 can be
Concatenate in thin film capacitor 23 front shown in Fig. 2 after an inducer L1 again and connect a thin-film electro
Container C6 realizes.π type low pass filter 43 have preferably filter than LC low pass filter 33 and
Energy storage effect, also can filter because the produced Conducted EMI noise of power transistor Q1 switching is to avoid passing
Deliver to power supply and pollute the electrical network at its place.
Whether the thin film capacitor 23 shown in Fig. 2, or the LC low pass filter 33 shown in Fig. 7,
Or the π type low pass filter 43 shown in Fig. 8, can be by adjusting the electricity of thin film capacitor therein
The inductance value size of capacitance size and/or inducer carrys out micro-whole first pulsating dc voltage Va under weight carries
The depth of trough.
Above-described embodiment explanation merely for convenience and illustrate, though suffer person of ordinary skill in the field appoint
Meaning is modified, all without departing from the scope as protected in claims.
Above-described embodiment explanation merely for convenience and illustrate, though suffer person of ordinary skill in the field appoint
Meaning is modified, all without departing from the scope as protected in claims.
Claims (8)
1. a power supply changeover device, it is characterised in that including:
One bridge rectifier, receives an alternating current power supply input voltage, and this alternating current power supply input voltage carries out rectification to produce a full-wave rectified voltage；
One thin film capacitor, receives this full-wave rectified voltage, and is filtered this full-wave rectified voltage producing one first pulsating dc voltage；And
One DC-DC converter, including a control circuit, this control circuit receives this first pulsating dc voltage, it is sampled producing one second pulsating dc voltage to this first pulsating dc voltage, detect a crest value and a valley value of this second pulsating dc voltage, and according to this second pulsating dc voltage, this crest value and this valley value are to produce an overcurrent protection offset, this overcurrent protection offset is-(Vx-VH)+PH, wherein, Vx is this second pulsating dc voltage, VH is this valley value, PH is this crest value, this control circuit according to an overcurrent protection setting value plus produced by this overcurrent protection offset once the overcurrent protection setting value of overcompensation this DC-DC converter is carried out overcurrent protection and determines power export-restriction.
2. power supply changeover device as claimed in claim 1, it is characterised in that this control circuit includes:
One attenuator, decays to produce this second pulsating dc voltage to this first pulsating dc voltage；
One peak valley holding circuit, detects this crest value and this valley value of this second pulsating dc voltage；
One subtractor, deducts this valley value to produce one first voltage by this second pulsating dc voltage；
One phase inverter, by this first voltage inversion to produce one second voltage；And
One adder, adds that by this second voltage this crest value and this overcurrent protection setting value are to produce this overcurrent protection setting value through overcompensation.
3. power supply changeover device as claimed in claim 1, it is characterised in that this control circuit includes:
One attenuator, decays to produce this second pulsating dc voltage to this first pulsating dc voltage；
One peak valley holding circuit, detects this crest value and this valley value of this second pulsating dc voltage；
One subtractor, deducts this crest value to produce one first voltage by this second pulsating dc voltage；
One phase inverter, by this first voltage inversion to produce one second voltage；And
One adder, adds that by this second voltage this valley value and this overcurrent protection setting value are to produce this overcurrent protection setting value through overcompensation.
4. power supply changeover device as claimed in claim 1, it is characterised in that this control circuit includes:
One attenuator, decays to produce this second pulsating dc voltage to this first pulsating dc voltage；
One peak valley holding circuit, detects this crest value and this valley value of this second pulsating dc voltage；
One phase inverter, by anti-phase for this second pulsating dc voltage to produce a voltage；And
One adder, by this voltage plus this crest value, this valley value and this overcurrent protection setting value to produce this overcurrent protection setting value through overcompensation.
5. power supply changeover device as claimed in claim 1, it is characterised in that also including an Electromagnetic interference filter, this bridge rectifier receives this alternating current power supply input voltage by this Electromagnetic interference filter.
6. the LC low pass filter that power supply changeover device as claimed in claim 1, it is characterised in that also include an inducer, this inducer and this thin film capacitor composition one are coupled between this bridge rectifier and this DC-DC converter.
7. power supply changeover device as claimed in claim 1, it is characterized in that, also include an inducer and another thin film capacitor, the π type low pass filter that this inducer, this thin film capacitor and this another thin film capacitor composition one are coupled between this bridge rectifier and this DC-DC converter.
8. power supply changeover device as claimed in claim 1, it is characterised in that this DC-DC converter includes a direction flyback converter.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| TW104101918 | 2015-01-21 | ||
| TW104101918A TWI521841B (en) | 2015-01-21 | 2015-01-21 | Power supply without electrolytic capacitor at input side |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN105991033A true CN105991033A (en) | 2016-10-05 |
| CN105991033B CN105991033B (en) | 2018-08-28 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201510060040.XA Active CN105991033B (en) | 2015-01-21 | 2015-02-05 | Power converter without electrolytic capacitor at input side |
Country Status (3)
| Country | Link |
|---|---|
| US (1) | US9209699B1 (en) |
| CN (1) | CN105991033B (en) |
| TW (1) | TWI521841B (en) |
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| KR20150139289A (en) * | 2014-06-03 | 2015-12-11 | 삼성전기주식회사 | Off signal generator and power conveter including for the same |
| TWI617122B (en) * | 2016-06-15 | 2018-03-01 | 泰達國際控股有限公司 | Ripple compensation circuit of power supply and compensating method thereof |
| US9899905B2 (en) | 2016-06-15 | 2018-02-20 | Det International Holding Limited | Ripple compensation circuit of power supply and compensation method thereof |
| FI128052B (en) | 2018-04-16 | 2019-08-30 | Lappeenrannan Teknillinen Yliopisto | A power converter for a bioelectrochemical system |
| US10861639B2 (en) * | 2018-09-17 | 2020-12-08 | Infineon Technologies Austria Ag | Adaptive control loop gain for switching mode power supply |
| CN114616738A (en) * | 2019-12-13 | 2022-06-10 | Oppo广东移动通信有限公司 | Adapter and charging method |
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| JP2010029039A (en) * | 2008-07-24 | 2010-02-04 | Sanken Electric Co Ltd | Power factor improving converter |
| CN104253535A (en) * | 2013-06-25 | 2014-12-31 | 冠捷投资有限公司 | Power supply without high-voltage electrolysis electrolytic capacitor |
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| JP4867500B2 (en) * | 2006-06-29 | 2012-02-01 | 富士電機株式会社 | Switching power supply |
| JP5212016B2 (en) * | 2008-10-28 | 2013-06-19 | 富士電機株式会社 | Switching power supply control circuit |
| US8098506B2 (en) * | 2009-06-02 | 2012-01-17 | Power Integrations, Inc. | Single-stage power supply with power factor correction and constant current output |
| JP5526857B2 (en) * | 2010-02-24 | 2014-06-18 | ミツミ電機株式会社 | Semiconductor integrated circuit for power control and isolated DC power supply |
| JP5785710B2 (en) * | 2010-12-14 | 2015-09-30 | ローム株式会社 | DC / DC converter, power supply device using the same, and electronic device |
| JP2012161117A (en) * | 2011-01-28 | 2012-08-23 | Rohm Co Ltd | Dc/dc converter, and power supply device and electronic apparatus using the same |
| GB2490918B (en) * | 2011-05-18 | 2013-05-15 | Ikon Semiconductor Ltd | A switched mode power supply |
| US9287784B2 (en) * | 2011-09-23 | 2016-03-15 | Power Integrations, Inc. | Adaptive biasing for integrated circuits |
| JP5873293B2 (en) * | 2011-10-31 | 2016-03-01 | キヤノン株式会社 | Power supply device and image forming apparatus |
| CN102638169B (en) * | 2012-05-08 | 2014-11-05 | 矽力杰半导体技术(杭州)有限公司 | Control circuit and control method of flyback convertor and alternating current-direct current power converting circuit applying control circuit of flyback convertor |
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2015
- 2015-01-21 TW TW104101918A patent/TWI521841B/en active
- 2015-02-04 US US14/613,410 patent/US9209699B1/en active Active
- 2015-02-05 CN CN201510060040.XA patent/CN105991033B/en active Active
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| Publication number | Priority date | Publication date | Assignee | Title |
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| JP2010029039A (en) * | 2008-07-24 | 2010-02-04 | Sanken Electric Co Ltd | Power factor improving converter |
| CN104253535A (en) * | 2013-06-25 | 2014-12-31 | 冠捷投资有限公司 | Power supply without high-voltage electrolysis electrolytic capacitor |
Also Published As
| Publication number | Publication date |
|---|---|
| US9209699B1 (en) | 2015-12-08 |
| CN105991033B (en) | 2018-08-28 |
| TW201628321A (en) | 2016-08-01 |
| TWI521841B (en) | 2016-02-11 |
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