CN105896987A - Flyback converter bootstrap type synchronous rectification drive circuit - Google Patents
Flyback converter bootstrap type synchronous rectification drive circuit Download PDFInfo
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- CN105896987A CN105896987A CN201510130019.2A CN201510130019A CN105896987A CN 105896987 A CN105896987 A CN 105896987A CN 201510130019 A CN201510130019 A CN 201510130019A CN 105896987 A CN105896987 A CN 105896987A
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
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- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
A flyback power supply converter employ a voltage transformer driving winding to realize bootstrap type synchronization rectification driving. The flyback converter bootstrap type synchronous rectification drive circuit comprises a primary side switch tube, a voltage transformer, a bootstrap circuit, a drive circuit, a synchronous rectifier and an output filtering capacitor. Driven by PWM signals, an original side winding and an original side power switch tube of a voltage transformer convert an input power source into a pulse mode which is then transmitted to a secondary side, output of a secondary side drive winding passes through a bootstrap circuit and therefore voltage is improved, a synchronous rectifier is enabled to work when the output of the secondary side drive winding passes through the drive circuit, and output voltage is obtained after output of a secondary side main output winding passes through the synchronous rectifier and is filtered.
Description
Art:
This patent relates to how driving winding to realize bootstrap type synchronous rectification driving circuit with transformer in flyback sourse converter.
Background technology
In order in supply convertor in order to reduce power attenuation, improve conversion efficiency, use synchronous rectification be an extraordinary solution, especially
It is for low-voltage, the application of big electric current.This is because use MOSFET (Metal-Oxide-Semiconductor Field-Effect
Transistor) voltage drop as rectifying device is far below corresponding diode component.
Anti exciting converter is because its circuit structure is simple, adapt to wide input voltage range and be widely used in middle low power converter.Corresponding
Synchronous rectification anti exciting converter is equally widely applied therewith.Secondary (outlet side) synchronous rectification scheme in anti exciting converter is generally speaking
It is divided into external drive, self-driven and combination drive etc. three kinds.
External drive refers to that the signal that drives of secondary-side switch pipe is directly produced by former limit signal, the method for generation can pass through transformer, high speed photo coupling,
PWM (Pulse Width Modulator) driving signal is delivered to secondary from former limit by the various isolating device such as digital isolator, direct or warp
Driving secondary synchronous rectification device again after crossing reinforcement, Fig. 1 is this scheme typical structure.This scheme uses isolating device 104 transmission to drive signal,
For exporting the occasion that electric current is bigger, owing to the Qg of corresponding secondary synchronous rectification MOSFET (106) is the biggest, therefore secondary needs
Extra drive circuit (105) is strengthened driving signal with high-speed switch synchronous rectification MOSFET, reduces the loss caused in switching process (also known as
Switching loss)；When output voltage amplitude is not suitable for use in driving voltage, operating voltage VCC of drive circuit needs extra transformers winding to produce；
The high level delay circuit (101) on former limit is for preventing former secondary MOSFET from having common process, it is ensured that as former limit main switch MOSFET
(102), during conducting, secondary synchronous rectification MOSFET has been switched off.In order to ensure the driving force enough to synchronous rectifier, secondary must have phase
The accessory power supply answered provides driving voltage.
Self-driven refer to drive signal be directly taken from transformer (202) secondary a winding and with its drive secondary synchronous rectification device (206),
This winding the most referred to as drives winding (Nd), and Fig. 2 is the basic circuit of this type of drive, transformer including at least primary side winding (Np),
Secondary output main winding (Ns) and driving winding (Nd) three windings, one end that definition Np and switching tube 102 are joined directly together is Same Name of Ends.
This drive scheme is simple, and the high level of secondary synchronous rectification device drives signal amplitude stable, be proportional to drive winding and the no-load voltage ratio of output winding,
Output voltage, equal to Vout*Nd/Ns, drives winding can meet the driving force requirement of synchronous rectifier.It should be noted that 2 points, one is
Owing to driving resistance (203) when the positive negative level of driving voltage all in work, therefore it is lost higher；Two is the negative voltage owing to driving signal
Signal amplitude is Vin*Nd/Np, input voltage range is the widest when, needs clamps (205) to carry out negative clamping, it is ensured that to synchronize whole
Will not damaging because the Vgs voltage of negative sense is higher of stream MOSFET (206), it is therefore desirable to the carefully no-load voltage ratio between the balance each winding of transformer,
The loss produced during to reduce clamp circuit work.Owing to, only after 201 former limit main switch MOSFET open, the Nd winding of 202 is electric
Pressure just can be reverse, and therefore the shutoff of 206 can lag behind 201 open-minded, there is former secondary and simultaneously turns on process phenomena (the most common process), thus
Also extra power attenuation is brought.
Combination drive is to drive the signal of secondary synchronous rectification device to be divided into two parts, and wherein high level is taken from transformer and drives the output of winding
Because it has enough driving forces, and cut-off signals is delivered to secondary by former limit pwm signal by isolating device and is controlled, transformer (303)
Including at least primary side winding (Np), secondary output main winding (Ns) and driving winding (Nd) three windings, concrete such as Fig. 3.Secondary synchronizes whole
The high level of stream MOSFET (308) drives signal amplitude stable, equal to Vout*Nd/Ns；And cut-off signals is by primary-side-control (304,307),
Due to the effect of high level delay circuit (301), when the main switch (302) on former limit turns on, secondary synchronous rectification MOSFET has been closed
Disconnected.The MOSFET common time of the most former secondary both sides is controlled, can reach both without common process, reduce common loss；Simultaneously because drive
The effect of dynamic circuit connected in series diode (306) reverse blocking, drives winding will not be shorted when being in negative voltage, makes to drive resistance simultaneously
(305) it is not at duty, reduces its power consumption；Drive voltage amplitude is the most relevant to output voltage, and the no-load voltage ratio between each winding of transformer is held
Easily design, and need not have driving accessory power supply.Shortcoming is to need the isolating device the same with outer driving, and circuit is more complicated.
In self-driven and combination drive scheme, the drive voltage amplitude of secondary synchronous rectification MOSFET is all Vout*Nd/Ns, and its negative sense electricity
Pressure is not utilized, and the source that even will also become loss or the selection affecting no-load voltage ratio between each winding of transformer or needs manage to evade
Unfavorable factor.
Summary of the invention
The present invention is the novel synchronous rectified drive circuit of one used in anti exciting converter, referred to as bootstrap type, exists by making full use of driving winding
The voltage produced when former limit MOSFET turns on and off so that drive circuit designs simple, effective and low-power consumption, reduces transformer and drives winding
Number of turn requirement；In conjunction with combination drive mode, the common problem of former secondary can be solved.
Anti exciting converter bootstrap type synchronous rectification driving circuit is made up of three parts, and respectively secondary drives winding, voltage raise circuit and driving electricity
Road, theory diagram such as Fig. 4.In Fig. 4, flyback transformer 402 comprises former limit Np, secondary main output Ns and secondary drives three windings such as Nd,
Input power, under pwm signal drives, is converted to pulse mode and is delivered to secondary by its primary side winding Np and former limit power switch pipe 401；Secondary
Limit drives the output of winding through boostrap circuit 403, and voltage gets a promotion, and orders about synchronous rectifier 405 via drive circuit 404 and works；Secondary
The output of main output winding Ns obtains output voltage after synchronous rectifier after 406 filtering.
Implementing of Fig. 4 circuit can have various ways, is exemplified below several way of realization.
In Fig. 5, the Same Name of Ends of transformer (502) secondary main output winding Ns is connected to synchronize the source electrode (S-Source) of homogeneous tube 508, and 508
Output filter capacitor 509, the two ends of 509 is had to be output voltage between drain electrode (D-Drain) and the different name end of Ns.
Boostrap circuit constitutes as follows: diode 505 is connected to the Same Name of Ends of Ns and drives between winding Nd different name end, wherein the P pole of 505 and
The Same Name of Ends of Ns is connected, N pole is connected with the different name end of Nd；The two ends of Nd connect electric capacity 503 and diode 504 series circuit, Qi Zhong electricity
Hold 503 one end and connect the different name end driving the Same Name of Ends of winding, the N knot of 504 to be connected to Nd.The series connection node of 503 and 504 is boostrap circuit
Output.
Drive circuit is then made up of resistance 506 and NPN type triode 507.One end of 506 is connected to the output of boostrap circuit, and the other end connects
Grid (G-Gate) to 508；The colelctor electrode (C-Collector) of 507 is connected to G pole, emitter (E-Emitter) connection of 508
To the S pole of 508, its base stage is connected to the different name end of Nd.This NPN type triode can also substitute with the MOSFET of N-channel.
When former limit MOSFET (501) turns on, the Same Name of Ends of Ns be negative voltage, the different name end of Nd be positive voltage, the be pole conducting of 507,
The Vgs of 508 is zero, and 508 turn off.Nd both end voltage is Vin*Nd/Np, and owing to 504 are in forward bias, therefore 503 both end voltage are
Vin*Nd/Np-Vfd, Vfd are the forward PN junction pressure drop of 504, and wherein 503 sides that are connected with Nd Same Name of Ends are low, with 504 P pole phase
Even side is high.Although the CE of 507 is conducting, but owing to there is no direct current loop, so 506 do not have electric current to flow through, in this phase
Between also would not produce power consumption, the electric charge at the GS two ends of 508 by 507 release.Such 507 just constitute the pass power-off that secondary synchronous rectification drives
Road.
When 501 turn off, the Same Name of Ends of Ns and Nd is positive voltage, and the different name end of Nd is negative voltage.Due to the positive clamping effect of 505,507
Be pole be reverse biased and turn off.The terminal voltage at Nd two ends is Vout*Nd/Ns, due to the reverse cut-off effect of 504, obtains at 503 two ends
It is Vin*Nd/Np-Vfd+Vout*Nd/Ns voltage to an amplitude, remains 503 and be extremely connected side for high with the P of 504.Voltage on 503
508 conductings are made by 506.The Vgs both end voltage of 508 is the loop being made up of 504～506, is therefore
Vin*Nd/Np+Vout*Nd/Ns-2Vfd.Such 506 resistance just constitute secondary synchronous rectification drive open circuit.
The above, former limit drives the port voltage amplitude of winding when opening due to superposition to open the driving voltage of 508, therefore far above standard from
Drive type synchronous rectification driving voltage amplitude.503 electric capacity are driven winding charge voluntarily via 504 and voltage amplitude is maintained when each former limit is opened
For Vin*Nd/Np-Vfd, 503 it is referred to as bootstrap capacitor for this.
It is as noted previously, as the effect of 503,504 and 505, when this bootstrap type circuit takes full advantage of 501 turn-on and turn-off on Nd winding
The voltage magnitude produced, under conditions of same Nd umber of turn, is greatly improved driving voltage amplitude；Otherwise, for suitable driving voltage,
The required number of turn of Nd winding can be greatly decreased during design.
In the king-sized application of input voltage vin range, the ratio of such as VinmaxNinmin reaches 5 times, then in order to meet
During low input, there are enough driving voltages at GS two ends, can cause again the maximum that driving voltage specifies when maximum input voltage beyond device.For this
The drive circuit of the band clamper function shown in Fig. 6 can be used.Fig. 6 is only to have done slight change on the basis of Fig. 5, adds NPN tri-pole
Pipe 610 and 611 two devices of Zener diode, 601～609 corresponding to the 501～509 of Fig. 5.Both differences are that the driving of 608 is no longer
By 606 but jointly complete by 606,610 and 611, wherein the C pole of 610 and one end of 606 link the output of boostrap circuit, 610
E pole be connected to 608 G pole, the N of B pole, the other end of 606 and 611 of 610 is the most connected, and the P pole of 611 is connected to the source of 608
Pole, simultaneously also it is the Same Name of Ends of Ns.When PWM level is low, if the clamp voltage Vz (611) that 603 both end voltage Vc (603) are higher than 611
Time, the Vgs driving voltage of the emitter terminal of 610 that is 608 is Vz (611)-Vbe (610), and wherein Vbe (610) is the PN of b, e of 610
Electrode drop；If during the clamp voltage that 603 both end voltage are less than 611, the Vgs driving voltage of 608 is Vc (603)-Vfd-Vbe (610),
Vfd is the forward drop of 605.So input voltage vin excursion is the biggest when, do not worry for driving when taking low side input into account
Move magnitude of voltage and cause the Vgs of high-end input beyond device limit value.610 can also replace, when clamp circuit action with N-channel MOS FET
Time, drive voltage amplitude is Vz (611)-Vth (610), and Vth (610) is the threshold voltage of 510.What so secondary synchronous rectification drove opens circuit
Constituted by 606,610 and 611；And breaking circuit process is the same with Fig. 5, just completed by 607.
In order to solve the common phenomenon of former secondary existed when the former limit of self-driven mode is opened, in bootstrap type circuit of synchronous rectification, close power-off plus outside
Road, i.e. can solve relevant issues.Fig. 7 show the improvement on the basis of Fig. 5.Wherein 701～709 correspond to 501～509, add 710
High level delay circuit and 711 isolators.The base stage of 707 is no longer directly connected with the different name end of Nd, but is driven by 711.Work as PWM
Signal once becomes high level directly by 711 shutoffs 707 and just can open 701 after time delay a period of time, so guarantee 701 and 708 it
Between will not simultaneously turn on.The breaking circuit that so secondary synchronous rectification drives just is constituted by 707,711, opens circuit and is constituted by 706.
External drive breaking circuit shown in Fig. 7 can also combine with circuit shown in Fig. 6, reaches driving voltage and is clamped and former secondary is without common existing
As.
Above example circuit secondary synchronous rectification device is all to illustrate as a example by flash rectification and N-channel MOS FET, is equally easy to lead to
Cross corresponding conversion be applied to the N-channel synchronous rectification of low limit and use in the P-channel MOSFET respective design as synchronous rectification device.
Accompanying drawing explanation
Fig. 1 is the synchronous rectification scheme that anti exciting converter uses external drive mode.
Fig. 2 is the synchronous rectification scheme that anti exciting converter uses self-driven mode.
Fig. 3 is the synchronous rectification scheme that anti exciting converter uses combination drive mode.
Fig. 4 is anti exciting converter bootstrap type synchronous rectification scheme theory diagram of the present invention.
Fig. 5 is the synchronous rectification scheme of the self-driven mode of anti exciting converter bootstrap type of the present invention.
Fig. 6 is the anti exciting converter of the present invention synchronous rectification scheme with the self-driven mode of bootstrap type of clamp circuit.
Fig. 7 is that anti exciting converter of the present invention is with the outer bootstrap type synchronous rectification scheme driving and turning off.
Detailed description of the invention
Fig. 1 is the synchronous rectification scheme that anti exciting converter uses external drive mode.PWM drive signal drives 102 former through delay circuit 101
Limit MOSFET, arrives secondary by 104 isolation circuit simultaneously, 105 synchronous rectification driving circuits drives 106 secondary synchronous rectification MOSFET.
When PWM is in high level, due to the effect of high level delay circuit, when 102 turn on, 106 already at off state, therefore 102 He
106 will not be simultaneously in conducting state；When PWM is in low level, 102 immediately turn off, and 106 turn on the most immediately, adjust related circuit ginseng
Number, it can be ensured that 102 and 106 will not be common.Power is delivered to secondary from former limit by 103 transformers, and 107 is output filter capacitor.
Fig. 2 is the synchronous rectification scheme that anti exciting converter uses self-driven mode.Pwm signal directly drives 201 former limit MOSFET, transformer
(202) a winding Nd is added.The Same Name of Ends output of Nd synchronizes whole by 203 resistance and 205 diodes in parallel circuit drives 206 secondary
The non-same polarity of stream MOSFET, Nd is attached directly to the source electrode of 206.207 is output filter capacitor.When 201 open, Nd Same Name of Ends is
Negative, non-same polarity is just, its port voltage is Vin*Nd/Np, and 206 turn off for bearing because of Vgs, and the clamp circuit being made up of 203 and 205 is protected
The card voltage Vgs limit value not over 206.When 201 turn off, Nd Same Name of Ends is just, Nd port voltage is Vout*Nd/Ns, and 206 open
Logical.
Fig. 3 is the synchronous rectification scheme that anti exciting converter uses combination drive mode.PWM drive signal drives through high level delay circuit 301
302 former limit MOSFET, arrive secondary by 304 isolation circuit simultaneously, drive 307--to control the MOSFET of secondary synchronous rectification signal.
When PWM is high level, due to the time delay of 301, when 302 turn on, 307 have been turned in advance, 308 secondary synchronous rectification MOSFET
Vgs be zero to be off state, therefore 302 and 308 will not simultaneously turn on；The Nd Motor Winding Same Name of Ends of 303 transformers is negative voltage, company
The non-same polarity connecing 308 source electrodes is just, but due to the reverse cut-off effect of drive circuit 306 diode, 305 drive resistance not have any damage
Consumption.When PWM is low level, 302 and 307 all immediately turn off, and the Nd Motor Winding Same Name of Ends of 303 transformers is that high level, non-same polarity are
Negative, port voltage is Vout*Nd/Ns, drives 308 conductings by 305 and 306, therefore 302 and 308 will not be common.309 is output filter
Ripple electric capacity.
Fig. 4 is anti exciting converter bootstrap type synchronous rectification scheme theory diagram of the present invention.Comprise primary side switch pipe 401, transformer 402, bootstrapping electricity
Road 403, synchronous rectification driving circuit 404 and synchronous rectifier 405, output filter capacitor 406.Its primary side winding Np is opened with former limit power
Input power, under pwm signal drives, is converted to pulse mode and is delivered to secondary by pass pipe 401；Secondary drives the output of winding through bootstrapping electricity
Road 403, voltage gets a promotion, and orders about synchronous rectifier 405 via drive circuit 404 and works；The output of secondary main output winding Ns is through same
After 406 filtering, output voltage is obtained after step rectifier.
Fig. 5 is the synchronous rectification scheme of the self-driven mode of anti exciting converter bootstrap type of the present invention.Pwm signal directly drives 501 former limit MOSFET；
Diode 505 is connected to the Same Name of Ends of Ns and drives between winding Nd different name end, wherein the P pole of 505 be connected with the Same Name of Ends of Ns, N pole
It is connected with the different name end of Nd；The two ends of Nd connect electric capacity 503 and diode 504 series circuit, wherein electric capacity 503 one end connect drive around
The Same Name of Ends of group, the N knot of 504 are connected to the different name end of Nd.One end of 506 is connected to the series connection node of 503 and 504, and the other end is connected to
The grid (G-Gate) of 508；The colelctor electrode (C-Collector) of 507 is connected to the G pole of 508, emitter (E-Emitter) is connected to
The S pole of 508, its base stage is connected to the different name end of Nd.The Same Name of Ends of transformer 502 secondary main output winding Ns is connected to synchronous rectification
The source electrode (S-Source) of MOSFET (508), has output filter capacitor 509 between drain electrode (D-Drain) and the different name end of Ns of 508,
The two ends of 509 are output voltage.When pwm signal is high level, 501 is open-minded, and it is 507 open-minded that Nd different name end is that high level makes, and 508
Vgs be zero to turn off, 503 both end voltage are Vin*Nd/Np-Vfd, and wherein 503 sides that are connected with Nd Same Name of Ends are negative, and Vfd is 504
Forward conduction voltage drop, owing to there is no current loop, 506 not power consumptions；When pwm signal is low level, 501 turn off, and Nd Same Name of Ends is
High level, 507 turn off, and 503 both end voltage are Vout*Nd/Ns+Vin*Nd/Np-Vfd, and the side that is connected with Nd Same Name of Ends is for just, opening by 506
Logical 508.
Fig. 6 is the anti exciting converter of the present invention synchronous rectification scheme with the self-driven mode of bootstrap type of clamp circuit.In figure, 601～609 correspond to
The 501～509 of Fig. 5, add NPN type triode 610 and Zener diode 611.Boostrap circuit is linked in the C pole of 610 and one end of 606
Output, the E pole of 610 be connected to 608 G pole, the N of B pole, the other end of 606 and 611 of 610 is the most connected, and the P pole of 611 is even
Receive the source electrode of 608, be simultaneously also the Same Name of Ends of Ns.When PWM is high level, owing to Nd different name end is high level, 607 conductings,
The Vgs of 608 is zero to turn off；When PWM is low level, 603 both end voltage Vc (603) are Vout*Nd/Ns+Vin*Nd/Np-Vfd, when
When this voltage is less than Vz (611), the E pole tension i.e. Vgs of 608 of 610 is Vc (603)-Vfd-Vbe (610), and Vfd is diode 605
Forward conduction voltage drop；If Vc (603) voltage is higher than Vz (611), the E pole tension i.e. Vgs of 808 of 610 is Vz (611)-Vbe (610),
And do not affected by the change of Vin.
Fig. 7 is that anti exciting converter of the present invention is with the outer bootstrap type synchronous rectification scheme driving and turning off.701～709 corresponding to the 501～509 of Fig. 5,
Add 710 and 711 circuit.Corresponding connection change has, and pwm signal is through the 710 former limits of high level delay circuit rear drive 701
MOSFET；The base stage of 707 has 711 isolator drive.When pwm signal is high level, 707 will be the most open-minded, and the Vgs of 708 is zero
And turn off, and 701 can time delays open-minded, therefore 701 and 708 without common, and 703 both end voltage are Vin*Nd/Np-Vfd, wherein 703 and Nd
The Same Name of Ends side that is connected is negative, and Vfd is the forward conduction voltage drop of 704, owing to there is no current loop, and 706 not power consumptions；When pwm signal is
During low level, 701,707 immediately turn off, and Nd Same Name of Ends is high level, and 703 both end voltage are Vout*Nd/Ns+Vin*Nd/Np-Vfd, with
The Nd Same Name of Ends side that is connected for just, opens 708 by 706.
Claims (12)
1. anti exciting converter bootstrap type synchronous rectification driving circuit,
A) transformer is including at least three windings such as former limit, secondary output, secondary drivings.
B) bootstrap type synchronous rectification driving circuit is driven winding, boostrap circuit and drive circuit to constitute by secondary.
2. it is configured to according to the boostrap circuit described in anti exciting converter bootstrap type synchronous rectification driving circuit right 1: the secondary that diode is connected to is defeated
Go out the Same Name of Ends of winding and secondary drive between winding different name end, the P pole of this diode is connected with the Same Name of Ends of secondary output winding, N pole and
Secondary drives the different name end of winding to be connected；Secondary drives winding two ends to connect electric capacity and diode series circuit, and wherein one end of electric capacity connects
Drive the different name end of winding to driving the Same Name of Ends of winding, the N pole of diode to be connected to, electric capacity and Diode series node are boostrap circuit
Output.
3. according to the drive circuit described in anti exciting converter bootstrap type synchronous rectification driving circuit right 1 by opening circuit and breaking circuit is constituted.
4. the circuit of opening according to the drive circuit described in anti exciting converter bootstrap type synchronous rectification driving circuit right 3 is that a resistance is connected to bootstrapping electricity
The output on road and the grid of secondary synchronous rectification MOSFET.
5. according in the drive circuit described in anti exciting converter bootstrap type synchronous rectification driving circuit right 3 open circuit can by NPN type triode,
The clamp circuit that resistance and Zener diode are constituted is constituted.Wherein the colelctor electrode of NPN type triode and one end of resistance are connected to boostrap circuit
Output, the N pole of the base stage of NPN type triode, the other end of resistance and Zener diode connects together, and the emitter stage of NPN type triode is even
Receiving the grid of secondary synchronous rectification MOSFET, the P pole of Zener diode is connected to the source electrode of secondary synchronous rectification MOSFET.Described NPN
Type triode can be replaced with N-channel MOS FET.
6. according to the breaking circuit in the drive circuit described in anti exciting converter bootstrap type synchronous rectification driving circuit right 3 by a NPN type triode structure
Become.The base stage of triode is connected to secondary and drives the different name end of winding, and colelctor electrode is connected to the grid of secondary synchronous rectification MOSFET, launches
Pole is connected to the source electrode of secondary synchronous rectification MOSFET.This NPN type triode can substitute with N-channel MOS FET.
7. according to the breaking circuit in the drive circuit described in anti exciting converter bootstrap type synchronous rectification driving circuit right 3 by a NPN type triode and
External drive breaking circuit is constituted.The base stage of triode is connected to the output of outside breaking circuit, and colelctor electrode is connected to secondary synchronous rectification
The grid of MOSFET, emitter stage is connected to the source electrode of secondary synchronous rectification MOSFET.This NPN type triode can use N-channel MOS FET
Substitute.
8. according to external drive breaking circuit described in anti exciting converter bootstrap type synchronous rectification driving circuit right 7 and pwm signal, former limit drive signal it
Between relation as follows: pwm signal no-delay through external drive breaking circuit turn off secondary synchronous rectification MOSFET, through high level time delay electricity
The rear drive former limit MOSFET on road, so that it is guaranteed that secondary synchronous rectification MOSFET is first turned off, open after former limit MOSFET and do not have former secondary altogether
Pass through journey.
9. can also may be used with N-channel device according to the secondary synchronous rectification MOSFET described in anti exciting converter bootstrap type synchronous rectification driving circuit right 1
To be P-channel device.
10. can be by corresponding PNP type triode according to NPN type triode circuit described in anti exciting converter bootstrap type synchronous rectification driving circuit right 5
Circuit is constituted.
11. can be by corresponding PNP type triode according to NPN type triode circuit described in anti exciting converter bootstrap type synchronous rectification driving circuit right 6
Circuit is constituted.
12. can use phase according to NPN type triode described in anti exciting converter bootstrap type synchronous rectification driving circuit right 7 or N-channel MOS FET circuit
Corresponding PNP type triode or P-channel MOSFET circuit are constituted.
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| CN201510130019.2A CN105896987A (en) | 2015-03-24 | 2015-03-24 | Flyback converter bootstrap type synchronous rectification drive circuit |
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| CN201510130019.2A CN105896987A (en) | 2015-03-24 | 2015-03-24 | Flyback converter bootstrap type synchronous rectification drive circuit |
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Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN106533137A (en) * | 2016-12-30 | 2017-03-22 | 天水七四九电子有限公司 | Synchronous rectification drive circuit suitable for wide input voltage range and wide output range |
| CN106712551A (en) * | 2016-12-02 | 2017-05-24 | 中惠创智无线供电技术有限公司 | Synchronous rectifier switch, synchronous rectifier chip and synchronous rectifier circuit |
| CN107959423A (en) * | 2017-12-07 | 2018-04-24 | 深圳市华星光电技术有限公司 | Circuit of reversed excitation and flyback sourse |
| CN111049391A (en) * | 2019-12-24 | 2020-04-21 | 普联国际有限公司 | Off-line flyback converter and power supply equipment |
| CN113162441A (en) * | 2020-01-22 | 2021-07-23 | 杭州必易微电子有限公司 | Isolated power supply circuit, primary and secondary side communication control circuit and control method |
| WO2024077527A1 (en) * | 2022-10-12 | 2024-04-18 | Innoscience (Shenzhen) Semiconductor Co., Ltd. | Nitride-based power converter and method for manufacturing thereof |
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| JP2002233144A (en) * | 2001-01-30 | 2002-08-16 | Shindengen Electric Mfg Co Ltd | Synchronous rectifying-type forward converter |
| CN101552558A (en) * | 2008-12-31 | 2009-10-07 | 北京新雷能有限责任公司 | Synchronous rectification driving circuit of flyback circuit |
| CN101917121A (en) * | 2010-07-15 | 2010-12-15 | 电子科技大学 | Active clamp synchronous rectification forward converter |
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| CN106533137B (en) * | 2016-12-30 | 2020-09-04 | 天水七四九电子有限公司 | Synchronous rectification drive circuit suitable for wide input voltage range and wide output range |
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