CN105785295A - Gradient power amplifier based on multistage coupling inductor optimized design - Google Patents
Gradient power amplifier based on multistage coupling inductor optimized design Download PDFInfo
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- CN105785295A CN105785295A CN201610246657.5A CN201610246657A CN105785295A CN 105785295 A CN105785295 A CN 105785295A CN 201610246657 A CN201610246657 A CN 201610246657A CN 105785295 A CN105785295 A CN 105785295A
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R33/00—Arrangements or instruments for measuring magnetic variables
- G01R33/20—Arrangements or instruments for measuring magnetic variables involving magnetic resonance
- G01R33/28—Details of apparatus provided for in groups G01R33/44 - G01R33/64
- G01R33/38—Systems for generation, homogenisation or stabilisation of the main or gradient magnetic field
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
Abstract
The invention relates to a gradient power amplifier based on multistage coupling inductor optimized design. The gradient power amplifier comprises a PWM control circuit, a power change circuit connected with the PWM control circuit, and a low-pass filter circuit connected with the power change circuit and a load, wherein the low-pass filter circuit comprises a coupling inductor portion and a low-pass filtering capacitor portion. The coupling inductor portion is connected between the power change circuit and the low-pass filtering capacitor portion, and the coupling inductor portion has at least two stages of coupling inductors. The gradient power amplifier employs multistage of coupling inductors, maximizes the rapid response capability of the gradient power amplifier, and further realizes low output current ripples.
Description
Technical field
The present invention relates to a kind of for the gradient power amplifier in magnetic resonance imaging system, be specifically related to a kind of gradient power amplifier based on multistage coupling inductance optimization design.
Background technology
Along with improving constantly of medical level, magnetic resonance imaging device is used widely.Gradient power amplifier is one of core component of magnetic resonance imaging system, and along with improving constantly of mr imaging technique, the performance of gradient power amplifier is had higher requirement by system.The patent No. is the United States Patent (USP) " pulse-widthmodulatedcircuitfordrivingaload " of US005070292, wherein namely disclose a kind of similar topological structure for MRI gradient power amplifier, this patent has made common filter inductance into coupling inductance, thus advantageously reducing the ripple of output electric current, improve the bandwidth of system.Application publication number is the Chinese invention patent application " a kind of gradient amplifier applying coupling inductance output filtering " of CN104950273A (application number is 201410120308.X) simultaneously, wherein application coupling inductance output filtering equally, quickly exports response and the imaging system requirement of low output ripple electric current meeting gradient current.But this kind of gradient amplifier is only applicable to mesolow powers in environment, it is not suitable for having in the magnetic resonance imaging system of higher voltage demand.The magnetic resonance gradient system of high voltage supply needs fast-changing big electric current, ultralow current ripples and accurate electric current to control, in order to reach quick curent change, it is necessary to high pressure, high-current semiconductor.The device that voltage is higher generally has higher switching loss, limit the maximum switching frequency being likely to be breached, under high switching loss, enable the interval that high-voltage inverter carries out switching to maintain accurate current waveform with sufficiently high frequency also restrained.Publication number is the Chinese invention patent application " producing the switching amplifier of the continuous free wave shape for MRI coil " of CN1247319A (application number is 99118609.5), wherein disclosed switching amplifier uses two isolated DC power bus, produces the gradient power amplifier of high-voltage great-current.This in actual use, control circuit is complicated, and cost is high.
Summary of the invention
To be solved by this invention first technical problem is that for above-mentioned prior art provide one can reduce output current ripple further, the gradient power amplifier that lifting system quickly responds.
To be solved by this invention second technical problem is that for above-mentioned prior art provide one be both conveniently applied in high pressure working environment, be conveniently applied in again the gradient power amplifier in mesolow working environment.
This invention address that the technical scheme that the problems referred to above adopt is: a kind of gradient power amplifier based on multistage coupling inductance optimization design, including
Pwm control circuit, is connected with the feedback end of gradient control signal outfan and output electric current respectively, for processing gradient control signal and the feedback signal of output electric current, with according to controlling logic output pwm control signal；
Power-varying circuitry, input is connected with the pwm control signal outfan of described pwm control circuit, produces high-voltage pulse according to pwm control signal；
Low-pass filter circuit, input is connected with described power-varying circuitry, is used for filtering generation high-voltage signal and exports load, completes the high-voltage pulse conversion to load end both end voltage difference so that produce intended electric current in load；
It is characterized in that:
Described low-pass filter circuit includes coupling inductance part and low-pass filtering capacitive part, and described coupling inductance part is connected between described power-varying circuitry and described low-pass filtering capacitive part, and described coupling inductance part includes at least two-stage coupling inductance.
Preferably, described power-varying circuitry includes first group of H-bridge circuit, second group of H-bridge circuit, the 3rd group of H-bridge circuit and the 4th group of H-bridge circuit, the PWM sequential respectively 0 degree, 180 degree, 90 degree and 270 degree that first group of H-bridge circuit, second group of H-bridge circuit, the 3rd group of H-bridge circuit are corresponding with the 4th group of H-bridge circuit work；
Described coupling inductance part includes first order coupling inductance and second level coupling inductance；
First order coupling inductance includes the first coupling inductance, the second coupling inductance, the 3rd coupling inductance and the 4th coupling inductance；
Second level coupling inductance includes the 5th coupling inductance and the 6th coupling inductance；
First half-bridge output midpoint of first group of H-bridge circuit and the first half-bridge output midpoint of second group of H-bridge circuit are respectively connecting to two inputs of the first coupling inductance；
First half-bridge output midpoint of the 3rd group of H-bridge circuit and the first half-bridge output midpoint of the 4th group of H-bridge circuit are respectively connecting to two inputs of the second coupling inductance；
Second half-bridge output midpoint of first group of H-bridge circuit and the second half-bridge output midpoint of second group of H-bridge circuit are respectively connecting to two inputs of the 3rd coupling inductance；
Second half-bridge output midpoint of the 3rd group of H-bridge circuit and the second half-bridge output midpoint of the 4th group of H-bridge circuit are respectively connecting to two inputs of the 4th coupling inductance；
The outfan of the first coupling inductance and the outfan of the second coupling inductance are respectively connecting to two inputs of the 5th coupling inductance, and the outfan of the 3rd coupling inductance and the outfan of the 4th coupling inductance are respectively connecting to two inputs of the 6th coupling inductance；
The outfan of the 5th coupling inductance and the outfan of the 6th inductance are connected in described low-pass filtering capacitive part.
Described low-pass filtering capacitive part includes one group or many group high frequency absorption circuit.
Selectively, described high frequency absorption circuit is RC absorbing circuit, C absorbing circuit, LRC absorbing circuit or LRCD absorbing circuit.
In order to facilitate this gradient power amplifier operation in mesolow working environment or high pressure working environment, every switching branches of described H-bridge circuit connects a switching tube or is connected in parallel at least two switching tubes or is at least connected in series two switching tubes.
Compared with prior art, it is an advantage of the current invention that: multistage coupling inductance should be adopted based in the gradient power amplifier of multistage coupling inductance optimization design, at utmost improve the capability of fast response of gradient power amplifier, furthermore achieved that low output current ripple simultaneously.In addition should can greatly improve gradient power amplifier performance indications in High Voltage Power Supply situation based on the topological structure of the gradient power amplifier of multistage coupling inductance optimization design, better meet the requirement to high gradient switching rate of 1.5T and the 3.0T nuclear magnetic resonance imaging system.
Accompanying drawing explanation
Fig. 1 is the structured flowchart of gradient power amplifier in the embodiment of the present invention.
Fig. 2 is the topology diagram of gradient power amplifier in the embodiment of the present invention.
Fig. 3 is the equivalent circuit diagram of the first coupling inductance in the embodiment of the present invention.
Fig. 4 is the voltage oscillogram at the first half-bridge output midpoint of first group of H-bridge circuit the first half-bridge output midpoint and second group of H-bridge circuit in the embodiment of the present invention.
Detailed description of the invention
Below in conjunction with accompanying drawing embodiment, the present invention is described in further detail.
As depicted in figs. 1 and 2, the gradient power amplifier based on multistage coupling inductance optimization design in the present embodiment, including pwm control circuit 1, power-varying circuitry 2 and low-pass filter circuit 3.
Wherein pwm control circuit 1 can adopt general pwm control circuit 1, this pwm control circuit 1 is connected with the feedback end of gradient control signal outfan and output electric current respectively, for processing gradient control signal and the feedback signal of output electric current, with according to controlling logic output pwm control signal.
Power-varying circuitry 2 in the present embodiment includes first group of H-bridge circuit 2A, second group of H-bridge circuit 2B, four groups of H-bridge circuit 2D of the 3rd group of H-bridge circuit 2C and the, the PWM sequential respectively 0 degree, 180 degree, 90 degree and 270 degree that first group of H-bridge circuit 2A, second group of H-bridge circuit 2B, the four groups of H-bridge circuit 2D work of the 3rd group of H-bridge circuit 2C and the are corresponding.
Wherein first group of H-bridge circuit 2A includes switching device K11, K12, K13 and K14, second group of H-bridge circuit 2B includes switching device K21, K22, K23 and K24,3rd group of H-bridge circuit 2C includes switching device K31, K32, K33 and K34, the 4th group of H-bridge circuit 2D includes switching device K41, K42, K43 and K44.Often the switching device in group H-bridge circuit is connected with the pwm control signal outfan of pwm control circuit 1 respectively, produces high-voltage pulse under the control of pwm control signal.
In order to facilitate this gradient power amplifier operation in high pressure working environment, every switching branches of H-bridge circuit is at least connected in series two switching tubes, is set to two switching tubes being connected in series by each switching device.So, this gradient power amplifier can be applied in higher voltage and power in environment, conveniently meets the requirement to high gradient switching rate of 1.5T and the 3.0T nuclear magnetic resonance imaging system.
The input of low-pass filter circuit 3 is connected with power-varying circuitry 2, low-pass filter circuit 3 includes coupling inductance part 31 and low-pass filtering capacitive part 32, coupling inductance part 31 is connected between power-varying circuitry 2 and low-pass filtering capacitive part 32, this coupling inductance part 31 can according to the sequential logic of the high-voltage pulse from power-varying circuitry 2, it is operated in voltage stabilizing state or instantaneous state, the requirement of the low output ripple of electric current is disclosure satisfy that when being operated in voltage stabilizing state, and when being operated in instantaneous state, then can meet the requirement of fast-response.
Low-pass filtering capacitive part 32 couples the inductance formed and constitutes low-pass filter circuit 3 with coupling inductance part 31, the high-voltage signal generated after filtering can be exported load, complete the high-voltage pulse conversion to load end both end voltage difference so that load produces intended electric current.
Coupling inductance part 31 in the present embodiment includes two-stage coupling inductance.Namely coupling inductance part 31 includes first order coupling inductance 31A and second level coupling inductance 31B.First order coupling inductance 31A includes the first coupling inductance 311A, the second coupling inductance 312A, the 3rd coupling inductance 313A and the four coupling inductance 314A.Second level coupling inductance 31B includes the 5th coupling inductance 315B and the six coupling inductance 316B.
The first half-bridge output midpoint of first group of H-bridge circuit 2A and the first half-bridge output midpoint of second group of H-bridge circuit 2B are respectively connecting to two inputs of the first coupling inductance 311A, the output midpoint of the half-bridge that namely switching device K11 and switching device K14 forms is connected with an input of the first coupling inductance 311A, and the output midpoint of the half-bridge that switching device K21 and switching device K24 forms is connected with another input of the first coupling inductance 311A.
The first half-bridge output midpoint of the 3rd group of H-bridge circuit 2C and the first half-bridge output midpoint of the 4th group of H-bridge circuit 2D are respectively connecting to two inputs of the second coupling inductance 312A, the output midpoint of the half-bridge that namely switching device K31 and switching device K34 forms is connected with an input of the second coupling inductance 312A, and the output midpoint of the half-bridge that switching device K41 and switching device K44 forms is connected with another input of the second coupling inductance 312A.
The second half-bridge output midpoint of first group of H-bridge circuit 2A and the second half-bridge output midpoint of second group of H-bridge circuit 2B are respectively connecting to two inputs of the 3rd coupling inductance 313A, the output midpoint of the half-bridge that namely switching device K12 and switching device K13 forms is connected with an input of the 3rd coupling inductance 313A, and the output midpoint of the half-bridge that switching device K22 and switching device K23 forms is connected with another input of the 3rd coupling inductance 313A.
The second half-bridge output midpoint of the 3rd group of H-bridge circuit 2C and the second half-bridge output midpoint of the 4th group of H-bridge circuit 2D are respectively connecting to two inputs of the 4th coupling inductance 314A, the output midpoint of the half-bridge that namely switching device K32 and switching device K33 forms is connected with an input of the 4th coupling inductance 314A, and the output midpoint of the half-bridge that switching device K42 and switching device K43 forms is connected with another input of the 4th coupling inductance 314A.
Work process for the first coupling inductance 311A in first order coupling inductance 31A, the work process of first order coupling inductance 31A is described, second coupling inductance 312A, the 3rd coupling inductance 313A and the four coupling inductance 314A and the first coupling inductance 311A work process identical, difference is only that on work schedule.
H bridge conversion section exports two high-voltage pulses of the first coupling inductance 311A input, when the dutycycle of the two high-voltage pulse is simultaneously greater than 50%, there will be the situation that switching device K11, K21 are closed at or switching device K13, K23 are closed at, now the coupling inductance of the first coupling inductance 311A is equivalent to low value inductance, this low value inductance and low-pass filtering capacitive part 32 form one group of low-pass filtering, for meeting the requirement of higher current-rising-rate.When output to the electromotive force between two high-voltage pulses and the first coupling inductance 311A outfan of the first coupling inductance 311A input is contrary, now coupling inductance and low-pass filtering capacitive part 32 form another group low-pass filtering, for forming the stable gradient output of low ripple electric current.
When H-bridge circuit breaker in middle device K11, K21 work wave dutycycle respectively 50% time, the signal output waveform of corresponding switching device K13 and K23 is corresponding completely the same respectively with switching device K11 and K21 respectively.And the signal output waveform phase contrast of switching device K11, K21 180 degree.
Equivalent circuit Fig. 3 of first coupling inductance 311A, if the monolateral inductance value Lp of the first coupling inductance 311A is sufficiently large, Lp is much larger than the equivalent leakage inductance Ls of the first coupling inductance 311A, coupling inductance can be equivalent to ideal transformer and the model of leakage inductance series connection, and current ripples now is system optimal value.Wherein LS1 and LS2 is the equivalent leakage inductance of two windings, and it is equivalence magnetizing inductance that LS1 and LS2 calculates, according to circuit theory, equivalent leakage inductance Ls, the Lp that obtain the first coupling inductance 311A.
Namely when the dutycycle of the work wave of H-bridge circuit breaker in middle device K11, K21 respectively 50% time, the first group of H-bridge circuit 2A being connected with the first coupling inductance 311A first half-bridge output midpoint Vx1 and second group of H-bridge circuit 2B first half-bridge output midpoint Vx2 voltage waveform as shown in Figure 4.Owing to being ideal transformer, it is equal that circuit design meets LS1 and LS2, and the electric current flowing through the two winding is equal, then Vy1=Vy2, it is possible to prove Vx1-Vy=Vy-Vx2, here Vy=(Vx1+Vx2)/2.Being equivalent to the Vy end at ideal transformer, running voltage is the half of Vx voltage, and operating frequency is that the waveform of twice is in work.As can be seen here, when H-bridge circuit breaker in middle device K11, K21 work wave dutycycle respectively 50% time, the voltage of Vy end is approximate DC, now first coupling inductance 311A output current ripples be almost negligible.During actual design, Lp is unlikely to be infinity, the requirement according to quick correspondence and low ripple, it is possible to choose suitable Lp and Ls, still can farthest ensure very low output ripple.
After the dutycycle of H-bridge circuit breaker in middle device K11, K21 work wave is more than 50%, then arise that the situation that switching device K11, K21 simultaneously turn on.At this moment ideal transformer is absent from, and is only that LS1 and LS2 is working, and for transient response, response speed now is the fastest.In this case, as long as LS1 and LS2 is sufficiently small, the requirement of quickly response just can be met.
After the dutycycle of H-bridge circuit breaker in middle device K11, K21 work wave is more than 50%, the first coupling inductance 311A is equivalent to low value leakage inductance as the above analysis, in order to reduce current ripples now, introduces second level coupling inductance and is highly desirable to.
In the present embodiment, the outfan of the first coupling inductance 311A and the outfan of the second coupling inductance 312A are respectively connecting to two inputs of the 5th coupling inductance 315B, and the outfan of the 3rd coupling inductance 313A and the outfan of the 4th coupling inductance 314A are respectively connecting to two inputs of the 6th coupling inductance 316B.The outfan of the 5th coupling inductance 315B and the outfan of the 6th inductance are connected in described low-pass filtering capacitive part 32.
Consider further that second level coupling inductance 31B, due to the PWM sequential respectively 0 degree, 180 degree, 90 degree and 270 degree that first group of H-bridge circuit 2A, second group of H-bridge circuit 2B, the four groups of H-bridge circuit 2D work of the 3rd group of H-bridge circuit 2C and the are corresponding.Here it is analyzed for the 5th coupling inductance 315B being connected with load end P.When the forward current of load end output dynamically strengthens, now the P input of reference load is forward, the dutycycle of H bridge translation circuit there will be the situation more than 50%, according to design sequential, just there is the phase contrast of 90 degree in the waveform of two inputs of the 5th coupling inductance 315B being connected with load end P, and now the 5th coupling inductance 315B is just operated under good CGCM.Owing to the coefficient of coup is higher, Approximate Equivalent is desirable coupling inductance, then flow through the electric current approximately equal of two windings of the 5th coupling inductance 315B.Now the 5th coupling inductance 315B will work together with low-pass filtering capacitive part 32, significantly reduce output current ripple now.Effect due to the 5th coupling inductance 315B, it is obvious that now each group of H bridge flows through the output current ripple all approximately equals after first order coupling inductance 31A.Requirement according to system bandwidth, optimizes the inductance value of design first order coupling inductance 31A and second level coupling inductance 31B, will obtain optimized output current ripple at final load outputs.
When the dutycycle of H bridge conversion section occurs 100%, the 5th coupling inductance 315B will be equivalent to the form of two independent leakage inductances, and coupling inductance there will be no.Now, first order coupling inductance 31A and second level coupling inductance 31B is equivalent to the form of low value leakage inductance, so can meet the requirement of the maximum quick response of system.
Low-pass filtering capacitive part 32 in the present embodiment includes one group or many group high frequency absorption circuit.High frequency absorption circuit can select to use RC absorbing circuit, C absorbing circuit, LRC absorbing circuit or LRCD absorbing circuit etc. as required.
Claims (5)
1. based on a gradient power amplifier for multistage coupling inductance optimization design, including
Pwm control circuit (1), is connected with the feedback end of gradient control signal outfan and output electric current respectively, for processing gradient control signal and the feedback signal of output electric current, with according to controlling logic output pwm control signal；
Power-varying circuitry (2), input is connected with the pwm control signal outfan of described pwm control circuit (1), produces high-voltage pulse according to pwm control signal；
Low-pass filter circuit (3), input is connected with described power-varying circuitry (2), export load for filtering generation high-voltage signal, complete the high-voltage pulse conversion to load end both end voltage difference so that load produces intended electric current；
It is characterized in that:
Described low-pass filter circuit (3) includes coupling inductance part (31) and low-pass filtering capacitive part (32), described coupling inductance part (31) is connected between described power-varying circuitry (2) and described low-pass filtering capacitive part (32), and described coupling inductance part (31) includes at least two-stage coupling inductance.
2. gradient power amplifier according to claim 1, it is characterized in that: described power-varying circuitry (2) includes first group of H-bridge circuit (2A), second group of H-bridge circuit (2B), the 3rd group of H-bridge circuit (2C) and the 4th group of H-bridge circuit (2D), the PWM sequential respectively 0 degree, 180 degree, 90 degree and 270 degree that first group of H-bridge circuit (2A), second group of H-bridge circuit (2B), the 3rd group of H-bridge circuit (2C) are corresponding with the 4th group of H-bridge circuit (2D) work；
Described coupling inductance part (31) includes first order coupling inductance (31A) and second level coupling inductance (31B)；
First order coupling inductance (31A) includes the first coupling inductance (311A), the second coupling inductance (312A), the 3rd coupling inductance (313A) and the 4th coupling inductance (314A)；
Second level coupling inductance (31B) includes the 5th coupling inductance (315B) and the 6th coupling inductance (316B)；
First half-bridge output midpoint of first group of H-bridge circuit (2A) and the first half-bridge output midpoint of second group of H-bridge circuit (2B) are respectively connecting to two inputs of the first coupling inductance (311A)；
First half-bridge output midpoint of the 3rd group of H-bridge circuit (2C) and the first half-bridge output midpoint of the 4th group of H-bridge circuit (2D) are respectively connecting to two inputs of the second coupling inductance (312A)；
Second half-bridge output midpoint of first group of H-bridge circuit (2A) and the second half-bridge output midpoint of second group of H-bridge circuit (2B) are respectively connecting to two inputs of the 3rd coupling inductance (313A)；
Second half-bridge output midpoint of the 3rd group of H-bridge circuit (2C) and the second half-bridge output midpoint of the 4th group of H-bridge circuit (2D) are respectively connecting to two inputs of the 4th coupling inductance (314A)；
The outfan of the first coupling inductance (311A) and the outfan of the second coupling inductance (312A) are respectively connecting to two inputs of the 5th coupling inductance (315B), and the outfan of the 3rd coupling inductance (313A) and the outfan of the 4th coupling inductance (314A) are respectively connecting to two inputs of the 6th coupling inductance (316B)；
The outfan of the 5th coupling inductance (315B) and the outfan of the 6th inductance are connected on described low-pass filtering capacitive part (32).
3. gradient power amplifier according to claim 1, it is characterised in that: described low-pass filtering capacitive part (32) includes one group or many group high frequency absorption circuit.
4. gradient power amplifier according to claim 3, it is characterised in that: described high frequency absorption circuit is RC absorbing circuit, C absorbing circuit, LRC absorbing circuit or LRCD absorbing circuit.
5. the gradient power amplifier according to Claims 1 to 4 any claim, it is characterised in that: every switching branches of described H-bridge circuit connects a switching tube or is connected in parallel at least two switching tubes or is at least connected in series two switching tubes.
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| CN106772163B (en) * | 2017-01-25 | 2019-07-16 | 上海东软医疗科技有限公司 | A kind of gradient amplifier and its modulator approach |
| US10718834B2 (en) | 2017-01-25 | 2020-07-21 | Shanghai Neusoft Medical Technology Co., Ltd. | Gradient amplifier and drive circuit thereof |
| CN110995181A (en) * | 2019-12-31 | 2020-04-10 | 南京磁晨医疗技术有限公司 | Gradient power amplifier |
| CN110995181B (en) * | 2019-12-31 | 2023-03-24 | 湖南迈太科医疗科技有限公司 | Gradient power amplifier |
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