CN105738887B - The optimization method of airborne radar clutter power spectrum based on the division of Doppler's passage - Google Patents
The optimization method of airborne radar clutter power spectrum based on the division of Doppler's passage Download PDFInfo
- Publication number
- CN105738887B CN105738887B CN201610067201.2A CN201610067201A CN105738887B CN 105738887 B CN105738887 B CN 105738887B CN 201610067201 A CN201610067201 A CN 201610067201A CN 105738887 B CN105738887 B CN 105738887B
- Authority
- CN
- China
- Prior art keywords
- clutter
- phased array
- array radar
- airborne phased
- airborne
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Classifications
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/28—Details of pulse systems
- G01S7/285—Receivers
- G01S7/292—Extracting wanted echo-signals
- G01S7/2923—Extracting wanted echo-signals based on data belonging to a number of consecutive radar periods
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/40—Means for monitoring or calibrating
- G01S7/4052—Means for monitoring or calibrating by simulation of echoes
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
- G01S2013/0236—Special technical features
- G01S2013/0245—Radar with phased array antenna
Landscapes
- Engineering & Computer Science (AREA)
- Radar, Positioning & Navigation (AREA)
- Remote Sensing (AREA)
- Computer Networks & Wireless Communication (AREA)
- Physics & Mathematics (AREA)
- General Physics & Mathematics (AREA)
- Radar Systems Or Details Thereof (AREA)
Abstract
The invention discloses a kind of optimization method of airborne phased array radar clutter power spectrum, its thinking is：Establish airborne phased array radar geometrical model, obtain the land clutter normalization Doppler frequency that airborne phased array radar receives, transmission signal voltage gain and the airborne phased array radar reception voltage signal gain of airborne phased array radar are obtained accordingly, and then obtain the round trip gain voltage signal and round trip signal power gain of airborne phased array radar；Further according to clutter ring oblique distance, the clutter block area in clutter ring grazing angle and clutter ring is obtained, and then obtains the clutter power of airborne phased array radar, then obtains the clutter power and clutter covariance matrix of airborne phased array radar accordingly；Finally obtain airborne phased array radar orientation steering vector and pitching to after steering vector, the spatial domain steering vector and space-time steering vector of airborne phased array radar, and the clutter plus noise covariance matrix of airborne phased array radar and the clutter power spectrum of airborne phased array radar are obtained successively.
Description
Technical Field
The invention belongs to the technical field of radars, and particularly relates to an optimization method of a clutter power spectrum of an airborne radar based on Doppler channel division, which is suitable for the ground clutter power spectrum simulation of the airborne phased array radar.
Background
The radar is indispensable equipment in modern war, and is a device for detecting a target and measuring target information by electromagnetic waves and receiving echoes. However, when a target exists in the natural environment, the natural environment may scatter electromagnetic waves or received echoes, thereby causing interference with target detection, which is referred to as radar clutter. For the airborne phased array radar adopting the downward-looking working mode, the influence of the ground clutter on target detection is very prominent, so that the inhibition capability of the ground clutter becomes an important index for checking the performance of the airborne phased array radar.
In order to obtain an effective clutter suppression method and improve the capability of the airborne phased array radar for detecting weak targets in the ground clutter, the ground clutter characteristics of the working environment of the airborne phased array radar must be fully and completely known. However, the measured ground clutter data is not available in a short time and is extremely expensive. With the improvement of computer technology, relevant researchers can obtain a method for inhibiting ground clutter by using the computer technology so as to research the ground clutter characteristics of the airborne phased array radar, and further provide simulation data for system design and signal processing of the airborne phased array radar, so that the method is very important.
The simulation method comprises the steps of dividing ground clutter into a plurality of clutter units according to equidistant rings and an azimuth angle in a rectangular coordinate system, modeling clutter echoes on any one of the equidistant rings into ground clutter of N independent clutter blocks, wherein N is a natural number larger than 1, the N independent clutter blocks are obtained by uniformly dividing the corresponding distance ring at a set angle interval on the azimuth angle, then calculating power spectrum and Doppler frequency of the uniformly divided N independent clutter blocks respectively, and obtaining corresponding Doppler channels according to the calculated Doppler frequency. Supposing that there are M doppler channels in the simulation, where M is a natural number greater than 1, clutter on a range ring is divided into N independent clutter blocks, generally, N is much greater than M for ensuring that the precision of simulated ground clutter data is high enough, however, there are only M doppler channels in practice, so that the time for running a ground clutter simulation program is too long due to the large number of clutter blocks divided by a range ring, and thus the simulation data of ground clutter cannot be obtained in time, thereby causing great inconvenience to system design and signal processing of a subsequent airborne phased array radar.
Disclosure of Invention
Aiming at the defects in the prior art, the invention aims to provide an optimization method of a clutter power spectrum of an airborne radar based on Doppler channel division, which divides the ground clutter according to equidistant rings in the pitching direction on the basis of the traditional ground clutter suppression method provided by J.Ward, improves the original uniform division method in the Doppler direction, calculates the Doppler frequency range of the clutter on any distance ring, obtains the corresponding Doppler channel range according to the Doppler frequency range, enables the Doppler frequency of the clutter on the distance ring to cover the Doppler channel, and then divides the clutter on the distance ring according to the Doppler number, thereby greatly shortening the time for operating a clutter simulation program.
In order to achieve the technical purpose, the invention adopts the following technical scheme to realize.
An optimization method of an airborne radar clutter power spectrum based on Doppler channel division comprises the following steps:
step 1, establishing a geometric model of an airborne phased array radar, wherein in the geometric model of the airborne phased array radar, the azimuth angle of a main beam of an antenna of the airborne phased array radar is theta 0 The main beam pitch angle of the antenna of the airborne phased array radar isThe number of Doppler channels of the airborne phased array radar is N c And the airborne phased array radar receives the ground clutter in the detection range and uniformly divides the ground clutter into L clutter rings according to the set width delta L, and the corresponding slope distance of the ith clutter ring is R l Dividing each clutter ring into N based on the Doppler channel c Pitch angle of individual clutter block, first clutter ringExpressed as:
wherein L is equal to {1,2, \8230;, L }, k is equal to {1,2, \8230;, N is equal to ∈ {1,2, \8230;) c L is the number of clutter rings contained in the ground clutter in the detection range received by the airborne phased array radar, N c For the number of clutter blocks contained in each clutter ring, acos (-) is an inverse cosine operation, R l Is the slope distance corresponding to the first hetero-wave ring, R e The radius of the earth is shown, and H is the carrier height of the airborne phased array radar;
then, selecting the N c The azimuth angle of the kth clutter block in the clutter blocks is used as the azimuth angle theta of the kth clutter block k And according to the pitch angle of the l-th hetero-wave ringCalculating to obtain the ground clutter normalized Doppler frequency f received by the airborne phased array radar d ；
Step 2, according to the pitch angle of the l-th clutter ringAnd the ground clutter normalized Doppler frequency f received by the airborne phased array radar d Respectively calculating the transmitting signal voltage gain of the airborne phased array radar on the clutter block pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockAnd the airborne phased array radar receives signal voltage gain on the clutter block pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockAnd calculating to obtain the two-way signal voltage gain of the airborne phased array radar on the pitch angle of the l clutter ring and the azimuth angle of the k clutter blockFurther calculating to obtain the onboard phase controlThe two-way signal power gain of the array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockWhere two passes represent transmission and reception, L ∈ {1,2, \8230;, L }, k ∈ {1,2, \8230;, N ∈ {1,2, \8230;, (N;) c L is the number of clutter rings contained in the ground clutter in the detection range received by the airborne phased array radar, N c The number of clutter blocks, θ, contained for each clutter ring k Is the azimuth angle of the k-th spur block,the pitch angle of the l-th clutter ring;
step 3, according to the corresponding slope distance of the first hetero-wave ring as R l Calculating to obtain the ground rubbing angle psi on the first clutter ring l And calculating the area S of the kth clutter block on the l clutter ring lk Then according to the pitch angle of the airborne phased array radar on the l clutter ring and the azimuth angle of the k clutter block, the power gain of the two-way signalCalculating to obtain clutter power of the airborne phased array radar on a pitch angle of the ith clutter ring and an azimuth angle of the kth clutter block
Step 4, according to the azimuth angle theta of the kth clutter block k And pitch angle of the l-th hetero-wave ringRespectively calculating to obtain clutter azimuth guiding vectors of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockAnd clutter pitching of the airborne phased array radar on the pitching angle of the l clutter ring and the azimuth angle of the k clutter blockVector of direction guideCalculating to obtain clutter space domain guide vector s of the kth clutter block on the ith clutter ring lk And then calculating to obtain a clutter space-time guide vector s of a kth clutter block on the ith clutter ring st Then according to the clutter power of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockCalculating to obtain a clutter covariance matrix of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter block
Step 5, according to the antenna main beam azimuth angle theta of the airborne phased array radar 0 And the main beam pitch angle of the antenna of the airborne phased array radarRespectively calculating the azimuth steering vector s of the airborne phased array radar a0 And the pitching steering vector s of the airborne phased array radar e0 And sequentially calculating to obtain the airspace guide vector s of the airborne phased array radar according to the space guide vector s s0 And space-time steering vector s of airborne phased array radar 0 Then according to the clutter covariance matrix of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockCalculating to obtain clutter and noise covariance matrix R of the airborne phased array radar, and obtaining space-time steering vector s of the airborne phased array radar according to the clutter and noise covariance matrix R 0 And calculating to obtain a clutter power spectrum P of the airborne phased array radar c 。
The invention has the beneficial effects that: on the basis of a J.Ward clutter simulation method, the optimization method of the airborne radar clutter power spectrum based on Doppler channel division firstly calculates the Doppler channel number covered by ground clutter in the azimuth direction, and then divides clutter blocks according to the Doppler channels, so that the Doppler frequency of the clutter blocks on a clutter ring only covers few Doppler channels, thereby reducing the block number of clutter division and shortening the time required by clutter simulation on the basis of obtaining vivid clutter simulation data.
Drawings
The invention is further described with reference to the following figures and detailed description.
FIG. 1 is a flow chart of an optimization method of a clutter power spectrum of an airborne radar based on Doppler channel division according to the present invention; in a three-dimensional coordinate system XOYZ, X, Y and Z are coordinate axes respectively, Z and X and Y form a right-hand coordinate system, a carrier and an airborne phased array radar are integrated, the airborne phased array radar is arranged in the carrier, a projection point of the carrier on the ground is used as a coordinate origin O and flies forwards and horizontally along the Y-axis direction at a speed v, and R is l The slope distance corresponding to the l-th clutter ring,is the pitch angle of the l-th hetero-wave ring, θ k Is the azimuth of the kth clutter block;
FIG. 2 is a schematic diagram of a coordinate system of an airborne phased array radar and an airborne vehicle;
fig. 3 is a clutter distance-doppler plot obtained using the clutter simulation method of j.ward; wherein the abscissa represents doppler and the ordinate represents distance;
FIG. 4 is a range-Doppler plot of clutter obtained using the method of the present invention; wherein the abscissa represents doppler and the ordinate represents distance.
Detailed Description
Referring to fig. 1, which is a flowchart of an optimization method of an airborne radar clutter power spectrum based on doppler channel division according to the present invention, the optimization method of the airborne radar clutter power spectrum based on doppler channel division includes the following steps:
step 1, establishing a geometric model of an airborne phased array radar, wherein the azimuth angle of a main beam of an antenna of the airborne phased array radar in the geometric model of the airborne phased array radar is theta 0 The main beam pitch angle of the antenna of the airborne phased array radar isThe number of Doppler channels of the airborne phased array radar is N d And the airborne phased array radar receives the ground clutter in the detection range and uniformly divides the ground clutter into L clutter rings according to the set width delta L, and the corresponding slope distance of the ith clutter ring is R l Dividing each clutter ring into N based on Doppler channel c Pitch angle of individual clutter block, first clutter ringExpressed as:
wherein L is equal to {1,2, \8230;, L }, k is equal to {1,2, \8230;, N is equal to ∈ {1,2, \8230;) c L is the number of clutter rings contained in ground clutter in a detection range received by the airborne phased array radar, N c For the number of clutter blocks contained in each clutter ring, acos (-) is an inverse cosine operation, R l Is the slope distance corresponding to the first hetero-wave ring, R e The radius of the earth and H are the height of the airborne phased array radar.
Then, selecting the N c The azimuth angle of the kth clutter block in the clutter blocks is used as the azimuth angle theta of the kth clutter block k And according to the pitch angle of the l-th hetero-wave ringCalculating to obtain the ground clutter normalized Doppler frequency f received by the airborne phased array radar d 。
In particular toReferring to fig. 2, a schematic diagram of a coordinate system of an airborne phased array radar and an airborne vehicle is shown; in a three-dimensional coordinate system XOYZ, X, Y and Z are coordinate axes respectively, Z, X and Y form a right-hand coordinate system, an airborne phased array radar is integrated with an airborne phased array radar, the airborne phased array radar is arranged in the airborne aircraft, a projection point of the airborne aircraft on the ground is used as a coordinate origin O, the height of the airborne phased array radar is H, the airborne phased array radar flies forwards and horizontally along the Y-axis direction at a speed v, the airborne phased array radar on the airborne aircraft is in a front side view mounting mode, and an antenna array surface of the airborne phased array radar is a rectangular plane, wherein the horizontal direction comprises N a Each array element having a pitch direction containing N e The horizontal and pitching array element intervals are d; the azimuth direction of the main beam of the antenna of the airborne phased array radar is vertical to the normal of the rectangular array surface of the phased array radar antenna, and the pitching direction of the main beam of the antenna of the airborne phased array radar points to infinity of a horizontal sight line; pulse repetition frequency f of airborne phased array radar r The transmitting gain and the receiving gain of the airborne phased array radar are respectively G t 、G r The receiver bandwidth of the airborne phased array radar is B, the transmitting pulse number of the airborne phased array radar is M, and the FFT point number of the airborne phased array radar is N d (ii) a Because the Doppler channel number of the airborne phased array radar is equal to the FFT point number, the Doppler channel number of the airborne phased array radar is N d (ii) a The carrier wavelength of the airborne phased array radar is lambda,f 0 the carrier frequency is the transmission signal carrier frequency of the airborne phased array radar, and c is the propagation speed of light in vacuum; the horizontal array element interval of the antenna array surface of the airborne phased array radar is d y The pitch array element interval of the antenna array surface of the airborne phased array radar is d z And are respectively distributed at carrier wavelength intervals of half of the airborne phased array radar, i.e.
In the airborne phased array radar geometric model, the airborne phased array radar receives ground clutter in a detection rangeThe ground clutter distribution distance range received by the airborne phased array radar array surface is H to R max Wherein H is the height of the carrier,is the maximum direct viewing distance, R, of the airborne phased array radar e Is the radius of the earth; and uniformly dividing the ground clutter into L clutter rings according to a set width delta L, wherein the corresponding slope distance of the ith clutter ring is R l And R is l ＝l·Δl，H≤R l ≤R max ，Dividing each clutter ring into N for the width of any one clutter ring c Pitch angle of individual clutter block, first clutter ringExpressed as:
then, selecting the N c The azimuth of the center of the kth clutter block in the clutter blocks is used as the azimuth theta of the kth clutter block k And according to the pitch angle of the l-th hetero-wave ringCalculating to obtain the ground clutter normalized Doppler frequency f received by the airborne phased array radar d And then sequentially calculating to obtain the maximum normalized Doppler frequency f of the ground clutter received by the airborne phased array radar d max And the minimum ground clutter normalized Doppler frequency f received by the airborne phased array radar d min The expression is as follows:
because the airborne and the airborne phased arrayThe radar is integrated, and the airborne phased array radar is arranged in the airborne machine, so that the included angle between the axial direction of the airborne phased array radar array surface and the speed of the airborne machine is 0, namely alpha =0 degrees; azimuth angle theta of kth clutter block k The value range is 0-180 degrees; azimuth angle theta of the kth clutter block k When the frequency is not less than 0 degree, calculating to obtain the maximum normalized Doppler frequency f of the ground clutter received by the airborne phased array radar array surface d max (ii) a When theta is measured k When the frequency is =180 degrees, the minimum normalized Doppler frequency f of the ground clutter received by the airborne phased array radar array surface is obtained through calculation d min The expressions are respectively:
wherein L is equal to {1,2, \8230;, L }, k is equal to {1,2, \8230;, N is equal to ∈ {1,2, \8230;) c L is the number of clutter rings contained in ground clutter in a detection range received by the airborne phased array radar, N c For the number of clutter blocks contained in each clutter ring, acos (-) is an inverse cosine operation, R l For the first distance, R e Is the radius of the earth, H is the height of the airborne phased array radar, v is the speed of the airborne phased array radar, f r Is the pulse repetition frequency of the airborne phased array radar,f 0 carrier frequency of the transmitted signal of the airborne phased array radar, c propagation speed of light in vacuum, theta k For the azimuth corresponding to the k-th spur block,the included angle alpha is the included angle between the axial direction of the airborne phased array radar array surface and the speed of the airborne phased array radar.
Based on ground clutter received by airborne phased array radarMaximum normalized Doppler frequency f d max And the minimum ground clutter normalized Doppler frequency f received by the airborne phased array radar d min Respectively obtaining the minimum normalized Doppler frequency f d min With said maximum normalized Doppler frequency f d max Respective corresponding Doppler channels N 1 And N 2 So as to obtain the azimuth angle theta of the kth clutter block k The number of Doppler channels covered by the ground clutter in the set range is N c I.e. the azimuth angle theta of the k-th clutter block k The number of Doppler channels covered by the ground clutter within the range of 0-180 DEG is N c (ii) a The number of Doppler channels of the airborne phased array radar is N d So that each Doppler channel has a width ofTherefore, the azimuth angle theta of the k-th clutter block k The number N of Doppler channels covered by ground clutter in the range of 0-180 DEG c Is from the Nth 1 A Doppler channel is started toIs a space up to the Nth 2 One Doppler channel ends, i.e. N c ＝N 2 -N 1 +1。
Step 2, according to the pitch angle of the l-th clutter ringAnd the ground clutter normalized Doppler frequency f received by the airborne phased array radar d Respectively calculating the pitch angle of the clutter block of the ith clutter ring and the azimuth angle of the kth clutter block of the airborne phased array radar to obtain the voltage gain of the transmitted signal of the airborne phased array radar on the pitch angle of the clutter block of the kth clutter ringAnd the airborne phased array radar receives signal voltage gain on the clutter block pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockAnd calculating to obtain the two-way signal voltage gain of the airborne phased array radar on the pitch angle of the l clutter ring and the azimuth angle of the k clutter blockAnd then calculating to obtain the two-way signal power gain of the airborne phased array radar on the pitch angle of the l clutter ring and the azimuth angle of the k clutter blockWhere two passes represent transmission and reception, L ∈ {1,2, \8230;, L }, k ∈ {1,2, \8230;, N ∈ {1,2, \8230;, (N;) c L is the number of clutter rings contained in the ground clutter in the detection range received by the airborne phased array radar, N c The number of clutter blocks, θ, contained for each clutter ring k Is the azimuth angle of the k-th spur block,the pitch angle of the l-th hetero-wave ring.
Specifically, the Doppler frequency f is normalized according to the ground clutter received by the airborne phased array radar d Obtaining the ground clutter normalized Doppler frequency f received by the airborne phased array radar d Left boundary f of the Doppler channel dl And a right boundary f dr And calculating the left boundary theta of the azimuth angle of the kth clutter block according to the inverse kl And the azimuthal right boundary θ of the kth spur block kr The expression is as follows:
azimuthal left boundary theta based on kth clutter block kl And the azimuthal right boundary θ of the kth spur block kr Calculating the center of the kth clutter blockAzimuth, i.e. the azimuth theta of the kth clutter block k The expression is as follows:
the azimuth direction of the main beam of the antenna of the airborne phased array radar is perpendicular to the normal line of the rectangular array surface of the phased array radar antenna, and the pitching direction of the main beam of the antenna of the airborne phased array radar points to the infinity of a horizontal sight line; therefore, the main beam azimuth angle theta of the antenna of the airborne phased array radar 0 Antenna main beam pitch angle with airborne phased array radarRespectively 90 deg. and 0 deg., and then using the azimuth angle theta of the kth clutter block k And pitch angle of the l-th hetero-wave ringRespectively calculating the pitch angle of the airborne phased array radar on the l clutter ring and the transmitting signal voltage gain on the azimuth angle of the k clutter blockAnd the receiving signal voltage gain of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockAnd calculating to obtain the two-way signal voltage gain of the airborne phased array radar on the pitch angle of the l clutter ring and the azimuth angle of the k clutter blockAnd then calculating to obtain the two-way signal power gain of the airborne phased array radar on the pitch angle of the l clutter ring and the azimuth angle of the k clutter blockThe expressions are respectivelyComprises the following steps:
where two passes represent transmission and reception, L ∈ {1,2, \8230;, L }, k ∈ {1,2, \8230;, N ∈ {1,2, \8230;, (N;) c L is the number of clutter rings contained in the ground clutter in the detection range received by the airborne phased array radar, N c The number of clutter blocks, θ, contained for each clutter ring k Is the azimuth angle of the k-th clutter block,is the pitch angle of the ith hetero-wave ring, | | | | | | non-woven phosphor ∞ Indicates an infinite norm, <' > indicates a dot product, f d Normalizing Doppler frequency for ground clutter received by an airborne phased array radar, na ∈ {1,2, \8230;, N a }，ne∈{1,2,…,N e }，N a The number of array elements contained in the horizontal direction of the airborne phased array radar antenna array surface, N e The number of array elements contained in the pitching direction of the airborne phased array radar antenna array surface is d is the interval of the array elements, andd y spacing of array elements in horizontal direction of antenna array surface of airborne phased array radar, d z The antenna array surface of the airborne phased array radar is spaced from the array elements in the pitching direction; theta.theta. 0 Azimuth angle of main beam of antenna for airborne phased array radar，Pitch angle, w, of main beam of antenna for airborne phased array radar na Windowing weight value w for the nth array element of the array surface azimuth direction of the airborne phased array radar antenna ne And adding a window weight to the ne array element in the pitching direction of the airborne phased array radar antenna array surface.
Step 3, according to the corresponding slope distance of the first hetero-wave ring as R l Calculating to obtain the ground rubbing angle psi on the first clutter ring l And calculating the area S of the kth clutter block on the first clutter ring lk Then according to the pitch angle of the airborne phased array radar on the l clutter ring and the azimuth angle of the k clutter block, obtaining the power gain of the two-way signalCalculating to obtain clutter power of the airborne phased array radar on a pitch angle of the ith clutter ring and an azimuth angle of the kth clutter block
In particular, the ground clearance angle psi on the first clutter ring l The expression is as follows:
azimuthal left boundary θ due to kth clutter block kl And the azimuthal right boundary θ of the kth spur block kr Therefore, the azimuth angle range corresponding to the k-th clutter block is: delta theta k ＝θ kr -θ kl 。
Then the area S of the kth clutter block on the ith clutter ring is obtained by calculation lk The expression is as follows:
and then according to the airborne phased array radar in the l-th clutter ringPitch angle, two-way signal power gain in azimuth of kth clutter blockCalculating to obtain clutter power of the airborne phased array radar on a pitch angle of the ith clutter ring and an azimuth angle of the kth clutter blockThe expression is as follows:
wherein L is equal to {1,2, \8230;, L }, k is equal to {1,2, \8230;, N is equal to ∈ {1,2, \8230;) c L is the number of clutter rings contained in the ground clutter in the detection range received by the airborne phased array radar, N c The number of clutter blocks, R, contained for each clutter ring l The first hetero-wave ring corresponding to the slant distance, R e The radius of the earth, H is the carrier height of the airborne phased array radar, c is the propagation speed of light in vacuum, B is the receiver bandwidth of the airborne phased array radar, G t And G r Respectively the transmission gain and the reception gain, sigma, of an airborne phased array radar 0 Is clutter backscattering coefficient, and sigma, of an airborne phased array radar 0 ＝γsinψ l ，ψ l The ground rubbing angle on the first clutter ring is, gamma is a clutter normalized backward scattering coefficient, and the value of the coefficient is related to the actual terrain; lambda is the carrier wavelength, P, of the airborne phased array radar t For the transmission peak power, L, of an airborne phased array radar s And tau is the loss of the airborne phased array radar, and tau is the emission pulse width of the airborne phased array radar.
Step 4, according to the azimuth angle theta of the kth clutter block k And pitch angle of the l-th hetero-wave ringRespectively calculating to obtain clutter azimuth guiding vectors of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockAnd clutter pitching guiding vector of the airborne phased array radar on the pitching angle of the ith clutter ring and the azimuth angle of the kth clutter blockCalculating to obtain clutter space domain guide vector s of the kth clutter block on the ith clutter ring lk And then calculating to obtain a clutter space-time guide vector s of a kth clutter block on the ith clutter ring st Then according to the clutter power of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockCalculating to obtain a clutter covariance matrix of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter block
Specifically, the airborne phased array radar has clutter azimuth direction guiding vector on the pitching angle of the ith clutter ring and the azimuth angle of the kth clutter blockThe expression is as follows:
clutter pitching guiding vector of airborne phased array radar on the pitching angle of the l clutter ring and the azimuth angle of the k clutter blockThe expression is as follows:
clutter space domain guide vector s of kth clutter block on the ith clutter ring lk The expression is as follows:
clutter space-time guiding vector s of kth clutter block on ith clutter ring st The expression is as follows:
clutter covariance matrix of airborne phased array radar on pitch angle of ith clutter ring and azimuth angle of kth clutter blockThe expression is as follows:
wherein s is t A ground clutter time domain steering vector received for the airborne phased array radar, an Representing the Kronecker product; l is one element of {1,2, \8230;, L }, k is one element of {1,2, \8230;, N is one element of c L is the number of clutter rings contained in the ground clutter in the detection range received by the airborne phased array radar, N c For the number of clutter blocks contained in each clutter ring, acos (-) is an inverse cosine operation, R l The tilt distance corresponding to the first clutter ring, lambda is the carrier wave length of the airborne phased array radar, na is an element {1,2, \8230;, N is a }，ne∈{1,2,…,N e }，N a For airborne phased array minesNumber of elements contained in horizontal direction of antenna array surface, N e The number of array elements contained in the pitching direction of the airborne phased array radar antenna array surface is d is the interval of the array elements, andd y horizontal array element spacing of antenna array surface of airborne phased array radar, d z The array elements are spaced in the pitching direction of the antenna array surface of the airborne phased array radar.
Step 5, according to the antenna main beam azimuth angle theta of the airborne phased array radar 0 And the main beam pitch angle of the antenna of the airborne phased array radarRespectively calculating azimuth steering vectors s of airborne phased array radar a0 And the pitching steering vector s of the airborne phased array radar e0 And sequentially calculating to obtain the airspace guide vector s of the airborne phased array radar according to the airspace guide vector s s0 And space-time steering vector s of airborne phased array radar 0 Then according to the clutter covariance matrix of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockCalculating to obtain clutter and noise covariance matrix R of the airborne phased array radar, and obtaining space-time steering vector s of the airborne phased array radar according to the clutter and noise covariance matrix R 0 And calculating to obtain clutter power spectrum P of the airborne phased array radar c 。
In particular, the azimuth steering vector s of an airborne phased array radar a0 And the pitching steering vector s of the airborne phased array radar e0 Are respectively:
airspace guide vector s of airborne phased array radar s0 And space-time steering vector s of airborne phased array radar 0 Are respectively:
the expression of the clutter and noise covariance matrix R of the airborne phased array radar is as follows:
clutter power spectrum P of airborne phased array radar c The expression of (a) is:
wherein d is y Spacing of array elements in horizontal direction of antenna array surface of airborne phased array radar, d z The space of the antenna array surface pitch array elements of the airborne phased array radar is shown, lambda is the carrier wave wavelength of the airborne phased array radar, and theta 0 Is the azimuth angle of the main beam of the antenna of the airborne phased array radar,pitch angle of main beam of antenna for airborne phased array radar, N a The number of array elements contained in the horizontal direction of the airborne phased array radar antenna array surface, N e The number of array elements contained in the pitching direction of the airborne phased array radar antenna array surface, N a >＝1，N e &=1, superscript T denotes transpose,represents the Kronecker product, w 0 The first weight, R, of the time domain windowing n Is a noise covariance matrix, andfor the noise power；R c Is a clutter covariance matrix of the airborne phased array radar, and is formed by L E {1,2, \8230;, L }, and k E {1,2, \8230;, N c L is the number of clutter rings contained in clutter within the detection range received by the airborne phased array radar, N c For each clutter ring, the number of clutter blocks, superscript H represents the conjugate transpose, (.) -1 Representing an inversion operation.
The effect of the present invention will be further described in detail with reference to simulation experiments.
Simulation parameter(s)
In the simulation experiment of the invention, the height H =8000m of the airborne phased array radar, the speed v =200m/s of the airborne phased array radar, and the carrier frequency f of the emission signal of the airborne phased array radar 0 The azimuth angle theta of the main beam of the antenna of the airborne phased array radar is equal to 1.5GHz, and the phased array radar on the airborne phased array radar is in a front side view installation mode, so that the included angle between the array surface of the airborne phased array radar and the speed of the airborne phased array radar is alpha =0 DEG, and the azimuth angle theta of the main beam of the antenna of the airborne phased array radar is theta 0 =90 °, antenna main beam pitch angle of airborne phased array radarArray element number N contained in horizontal direction of airborne phased array radar antenna array surface a =128, number of array elements N included in pitching direction of airborne phased array radar antenna array e =10, array element interval d is 0.1m, pulse repetition frequency f of airborne phased array radar r =6000Hz, receiver bandwidth B =5MHz of the airborne phased array radar, transmission pulse number M =64 of the airborne phased array radar, and FFT point number N of the airborne phased array radar d =128, the emission peak power of the airborne phased array radar is 600kW, and the loss L of the airborne phased array radar is s =7dB, and clutter normalized backscatter coefficient γ = -13dB.
(II) simulation data processing result and analysis
A. In order to illustrate the superiority of the invention, clutter simulation is firstly carried out by using a clutter simulation method of J.Ward according to the radar system parameters, each clutter ring is averagely divided into 6000 clutter blocks, then simulation is carried out by adopting the method of the invention, the method adopts Doppler division to carry out clutter block division on the clutter of each clutter ring, and data processing is carried out on the divided clutter blocks.
Under the same parameters, the time consumed for completing the operation of the clutter simulation program by using the clutter simulation method of j.ward is as follows: 27884 s; the time consumed by simulating the running of the clutter program by using the method of the invention is as follows: 593 seconds. Compared with a clutter simulation method using J.Ward, the method has absolute advantages in simulation speed.
B. To further illustrate the advantages of the present invention, fig. 3 is a clutter range-doppler plot obtained using the clutter simulation method of j.ward; wherein the abscissa represents doppler and the ordinate represents distance; FIG. 4 is a range-Doppler plot of clutter obtained using the method of the present invention; wherein the abscissa represents doppler and the ordinate represents distance.
As can be seen from fig. 3, in the clutter distance doppler plot obtained by simulation using the clutter simulation method of j.ward, the rectangular bar on the right represents decibel (dB), and the clutter level is higher at brighter colors. As can be seen from fig. 4, in the range-doppler plot of clutter data obtained using the method of the present invention, the right rectangle represents decibels (dB), and the clutter level is higher the brighter the color. Comparing fig. 3 and fig. 4, it can be seen that the clutter distance doppler plot obtained by using the clutter simulation method of j.ward is almost the same as the clutter distance doppler plot obtained by using the method of the present invention, and the included angle α =0 ° between the airborne phased array radar array surface and the airborne speed, so that the ground clutter is intensively distributed near the zero doppler frequency, and therefore, the ground clutter data obtained by the simulation of the method of the present invention is correct, so that the method of the present invention can embody the vivid clutter characteristics.
From the above analysis it can be concluded that: compared with the clutter simulation method of J.Ward, the clutter simulation method has great advantages, and vivid clutter simulation data can be obtained more quickly by using the method.
In conclusion, the simulation experiment verifies the correctness, the effectiveness and the reliability of the method.
It will be apparent to those skilled in the art that various changes and modifications may be made in the present invention without departing from the spirit and scope of the invention; thus, if such modifications and variations of the present invention fall within the scope of the claims of the present invention and their equivalents, the present invention is also intended to include such modifications and variations.
Claims (7)
1. An optimization method of an airborne radar clutter power spectrum based on Doppler channel division is characterized by comprising the following steps:
step 1, establishing a geometric model of an airborne phased array radar, wherein in the geometric model of the airborne phased array radar, the azimuth angle of a main beam of an antenna of the airborne phased array radar is theta 0 The main beam pitch angle of the antenna of the airborne phased array radar isThe number of Doppler channels of the airborne phased array radar is N d And the airborne phased array radar receives the ground clutter in the detection range and uniformly divides the ground clutter into L clutter rings according to the set width delta L, wherein the corresponding slope distance of the first clutter ring is R l Dividing each clutter ring into N based on the Doppler channel c Pitch angle of individual clutter block, first clutter ringExpressed as:
wherein L is equal to {1,2, \8230;, L }, k is equal to {1,2, \8230;, N is equal to ∈ {1,2, \8230;) c L is the number of clutter rings contained in the ground clutter in the detection range received by the airborne phased array radar, N c For the number of clutter blocks contained in each clutter ring, acos (-) is an inverse cosine operation, R l Is the slope distance corresponding to the first hetero-wave ring, R e The radius of the earth is shown, and H is the carrier height of the airborne phased array radar;
then, selecting the N c In the k-th clutter block of the clutter blocksAzimuth of the heart as the azimuth theta of the k-th clutter block k And according to the pitch angle of the l-th hetero-wave ringCalculating to obtain the ground clutter normalized Doppler frequency f received by the airborne phased array radar d ；
Step 2, according to the pitch angle of the l-th clutter ringAnd the ground clutter normalized Doppler frequency f received by the airborne phased array radar d Respectively calculating the transmitting signal voltage gain of the airborne phased array radar on the clutter block pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockAnd the airborne phased array radar receives signal voltage gain on the clutter block pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockAnd calculating to obtain the two-way signal voltage gain of the airborne phased array radar on the pitch angle of the l clutter ring and the azimuth angle of the k clutter blockAnd then calculating to obtain the two-way signal power gain of the airborne phased array radar on the pitch angle of the l clutter ring and the azimuth angle of the k clutter block
Where two passes represent transmission and reception, L ∈ {1,2, \8230;, L }, k ∈ {1,2, \8230;, N ∈ {1,2, \8230;, (N;) c L is the number of clutter rings contained in ground clutter in a detection range received by the airborne phased array radar, N c The number of clutter blocks, θ, contained for each clutter ring k Is the azimuth angle of the k-th clutter block,the pitch angle of the l-th clutter ring;
step 3, according to the slope distance corresponding to the first clutter ring as R l Calculating to obtain the ground rubbing angle psi on the first clutter ring l And calculating the area S of the kth clutter block on the first clutter ring lk Then according to the pitch angle of the airborne phased array radar on the l clutter ring and the azimuth angle of the k clutter block, the power gain of the two-way signalCalculating to obtain clutter power of the airborne phased array radar on a pitch angle of the ith clutter ring and an azimuth angle of the kth clutter block
Step 4, according to the azimuth angle theta of the kth clutter block k And pitch angle of the l-th hetero-wave ringRespectively calculating clutter azimuth direction guiding vectors of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockAnd clutter pitching guiding vector of the airborne phased array radar on the pitching angle of the ith clutter ring and the azimuth angle of the kth clutter blockCalculating to obtain clutter space domain guide vector s of the kth block clutter block on the ith clutter ring lk And then calculating to obtain a clutter space-time guide vector s of the kth block clutter block on the ith clutter ring st Then according to the pitch angle of the airborne phased array radar on the ith clutter ringClutter power at azimuth of kth clutter blockCalculating to obtain a clutter covariance matrix of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter block
Step 5, according to the antenna main beam azimuth angle theta of the airborne phased array radar 0 And the main beam pitch angle of the antenna of the airborne phased array radarRespectively calculating azimuth steering vectors s of airborne phased array radar a0 And the pitching steering vector s of the airborne phased array radar e0 And sequentially calculating to obtain the airspace guide vector s of the airborne phased array radar according to the space guide vector s s0 And space-time steering vector s of airborne phased array radar 0 Then according to the clutter covariance matrix of the airborne phased array radar on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockCalculating to obtain clutter and noise covariance matrix R of the airborne phased array radar, and guiding the vector s according to space time of the airborne phased array radar 0 And calculating to obtain a clutter power spectrum P of the airborne phased array radar c 。
2. The method as claimed in claim 1, wherein in step 1, the ground clutter normalization doppler frequency f received by the airborne phased array radar is normalized d The expression is as follows:
wherein, l ∈ {1,2，…，L}，k∈{1，2，…，N c l is the number of clutter rings contained in ground clutter in a detection range received by the airborne phased array radar, N c The number of clutter blocks contained in each clutter ring, v is the carrier speed of the carrier phased array radar, f r Is the pulse repetition frequency of the airborne phased array radar,f 0 carrier frequency of the transmitting signal of the airborne phased array radar, c propagation speed of light in vacuum, theta k For the azimuth corresponding to the k-th spur block,and a clutter block pitch angle corresponding to the ith clutter ring, wherein alpha is an included angle between the axial direction of the airborne phased array radar array surface and the speed of an airborne.
3. The method as claimed in claim 1, wherein in step 1, each clutter ring is divided into N clutter rings based on doppler channel division c A clutter block of N c Is from the Nth 1 A Doppler channel is started withIs spacing, up to Nth 2 One Doppler channel ends, i.e. N c ＝N 2 -N 1 +1，N 2 Maximum normalized Doppler frequency f of ground clutter received by airborne phased array radar dmax Corresponding Doppler channel, N 1 Normalizing Doppler frequency f for minimum ground clutter received by airborne phased array radar dmin The corresponding doppler channel.
4. The method for optimizing the clutter power spectrum of the airborne radar based on the doppler channel division as claimed in claim 1, wherein in step 2, the airborne phased array radar tilts the clutter block of the ith clutter ringTransmit signal voltage gain in elevation, azimuth of the kth spur blockAnd the airborne phased array radar receives signal voltage gain on the clutter block pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockThe expressions are respectively:
the airborne phased array radar is in the pitch angle of the l-th clutter ring and the two-way signal voltage gain of the azimuth angle of the k-th clutter blockAnd the airborne phased array radar has two-way signal power gain on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockThe expressions are respectively:
wherein L is equal to {1,2, \8230;, L }, k is equal to {1,2, \8230;, N is equal to ∈ {1,2, \8230;) c L is an airborne phased array radarNumber of clutter rings, N, included in the ground clutter within the detection range of the receiver c The number of clutter blocks, θ, contained for each clutter ring k Is the azimuth angle of the k-th spur block,is the pitch angle of the ith hetero-wave ring, | | | | | | non-woven phosphor ∞ Indicates an infinite norm, <' > indicates a dot product, f d Normalizing Doppler frequency for ground clutter received by an airborne phased array radar, na ∈ {1,2, \8230;, N a }，ne∈{1，2，…，N e }，N a The number of array elements contained in the horizontal direction of the airborne phased array radar antenna array surface, N e The number of array elements contained in the pitching direction of the airborne phased array radar antenna array surface is d, the d is the interval of the array elements, andd y horizontal array element spacing of antenna array surface of airborne phased array radar, d z The antenna array surface of the airborne phased array radar is spaced from the array elements in the pitching direction; theta 0 Is the azimuth angle of the main beam of the antenna of the airborne phased array radar,pitch angle, w, of main beam of antenna for airborne phased array radar na Windowing weight value w for the nth array element of the array surface azimuth direction of the airborne phased array radar antenna ne And adding a window weight to the ne array element in the pitching direction of the antenna array surface of the airborne phased array radar, wherein lambda is the carrier wave wavelength of the airborne phased array radar.
5. The method for optimizing the power spectrum of the airborne radar clutter based on doppler channel segmentation as claimed in claim 1, wherein in step 3, the ground-scrape angle ψ on the ith clutter ring l And the area S of the kth clutter block on the l clutter ring lk Are respectively:
the airborne phased array radar has clutter power on the pitch angle of the ith clutter ring and the azimuth angle of the kth clutter blockThe expression of (a) is:
wherein L is equal to {1,2, \8230;, L }, k is equal to {1,2, \8230;, N is equal to ∈ {1,2, \8230;) c L is the number of clutter rings contained in ground clutter in a detection range received by the airborne phased array radar, N c The number of clutter blocks, R, contained for each clutter ring l The first hetero-wave ring corresponding to the slant distance, R e The radius of the earth, H is the carrier height of the airborne phased array radar, c is the propagation speed of light in vacuum, B is the receiver bandwidth of the airborne phased array radar, G t And G r Respectively the transmission gain and the reception gain, sigma, of an airborne phased array radar 0 Is clutter backscattering coefficient, and sigma, of an airborne phased array radar 0 ＝γsinψ l ，ψ l The ground rubbing angle on the l clutter ring is, gamma is a clutter normalized backscattering coefficient, and the value of the backscattering coefficient is related to the actual terrain; lambda is the carrier wavelength, P, of the airborne phased array radar t For the transmitted peak power, L, of an airborne phased array radar s And tau is the transmission pulse width of the airborne phased array radar.
6. The method for optimizing the power spectrum of the airborne radar clutter based on Doppler channel division as claimed in claim 1, wherein in step 4, the airborne phased array radar clutter azimuth direction vector at the pitch angle of the l-th clutter ring and the azimuth angle of the k-th clutter blockAnd clutter elevation direction vector of the airborne phased array radar on the pitching angle of the ith clutter ring and the azimuth angle of the kth clutter blockThe expressions are respectively:
clutter space domain guide vector s of kth clutter block on the ith clutter ring lk And a clutter space-time steering vector s of the kth clutter block on the ith clutter ring st And the clutter covariance matrix of the airborne phased array radar on the pitching angle of the ith clutter ring and the azimuth angle of the kth clutter blockThe expressions are respectively:
wherein s is t A ground clutter time domain steering vector received for the airborne phased array radar, an Representing the Kronecker product; l is equal to {1,2, \8230;, L }, k is equal to {1,2, \8230;, N is equal to ∈ {1,2, \8230;) c L is the number of clutter rings contained in ground clutter in a detection range received by the airborne phased array radar, N c Clutter contained for each clutter ringThe number of blocks, acos (-) is an inverse cosine operation, R l The tilt distance corresponding to the first clutter ring, lambda is the carrier wave length of the airborne phased array radar, na is an element {1,2, \8230;, N is a }，ne∈{1，2，…，N e }，N a The number of array elements contained in the horizontal direction of the airborne phased array radar antenna array surface, N e The number of array elements contained in the pitching direction of the airborne phased array radar antenna array surface is d is the interval of the array elements, andd y horizontal array element spacing of antenna array surface of airborne phased array radar, d z The array elements are spaced in the pitching direction of the antenna array surface of the airborne phased array radar.
7. The method as claimed in claim 1, wherein in step 5, the azimuth steering vector s of the airborne phased array radar is used as the steering vector s a0 And a pitch steering vector s of the airborne phased array radar e0 Are respectively:
airspace guide vector s of airborne phased array radar s0 And the space-time steering vector s of the airborne phased array radar 0 Are respectively:
a clutter-plus-noise covariance matrix R of the airborne phased array radar and a clutter power spectrum P of the airborne phased array radar c Are respectively:
wherein d is y Spacing of array elements in horizontal direction of antenna array surface of airborne phased array radar, d z The pitch of the antenna array surface of the airborne phased array radar is spaced from the array element, lambda is the carrier wave wavelength of the airborne phased array radar, theta 0 Is the azimuth angle of the main beam of the antenna of the airborne phased array radar,pitch angle of main beam of antenna for airborne phased array radar, N a The number of array elements contained in the horizontal direction of the airborne phased array radar antenna array surface, N e The number of array elements contained in the pitching direction of the airborne phased array radar antenna array surface, N a ＞＝1，N e > =1, the superscript T denotes transpose,represents the Kronecker product, w 0 The first weight, R, of the time domain windowing n Is a noise covariance matrix or noise power, andR c is a clutter covariance matrix of the airborne phased array radar, L belongs to {1,2, \8230;, L }, and k belongs to {1,2, \8230;, N ∈ {1,2, \\ 8230;) c L is the number of clutter rings contained in clutter in a detection range received by the airborne phased array radar, N c For the number of clutter blocks contained in each clutter ring, superscript H denotes the conjugate transpose, (. Cndot.) -1 Representing the inversion operation.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201610067201.2A CN105738887B (en) | 2016-01-29 | 2016-01-29 | The optimization method of airborne radar clutter power spectrum based on the division of Doppler's passage |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201610067201.2A CN105738887B (en) | 2016-01-29 | 2016-01-29 | The optimization method of airborne radar clutter power spectrum based on the division of Doppler's passage |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN105738887A CN105738887A (en) | 2016-07-06 |
| CN105738887B true CN105738887B (en) | 2018-03-06 |
Family
ID=56247214
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201610067201.2A Active CN105738887B (en) | 2016-01-29 | 2016-01-29 | The optimization method of airborne radar clutter power spectrum based on the division of Doppler's passage |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN105738887B (en) |
Families Citing this family (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN108120976B (en) * | 2017-12-08 | 2021-02-23 | 中国船舶重工集团公司第七二四研究所 | Ground clutter spectrum leakage suppression method based on Doppler channel characteristics |
| CN108875280B (en) * | 2018-08-08 | 2019-04-30 | 西北工业大学 | A kind of carrier-borne phased array guidance radar residence time dynamic dispatching method |
| CN111398907B (en) * | 2019-01-02 | 2023-04-07 | 中国人民解放军空军预警学院 | Phased array radar space domain two-dimensional digital difference beam forming method |
| CN111612121B (en) * | 2020-06-02 | 2023-04-18 | 电子科技大学 | Optimization method for dynamic gain of liquid crystal microwave phased array antenna |
| CN112163454A (en) * | 2020-08-27 | 2021-01-01 | 中国海洋大学 | High-frequency ground wave radar clutter intelligent classification and positioning method based on RD spectrum enhancement |
| RU2760976C1 (en) * | 2021-03-18 | 2021-12-02 | Федеральное государственное бюджетное образовательное учреждение высшего образования "Рязанский государственный радиотехнический университет им. В.Ф. Уткина" | Method for tomographic registration of inclined range and azimuth of position of surface objects and objects above underlying surface |
| CN115047425B (en) * | 2022-05-25 | 2024-06-25 | 西安电子科技大学 | Rapid simulation method and device for ultra-high speed platform clutter |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1218185A (en) * | 1998-12-14 | 1999-06-02 | 中国人民解放军空军雷达学院 | Method for processing space-time multibeam adaptive signals |
| EP1067400A2 (en) * | 1999-07-09 | 2001-01-10 | General Electric Company | Method and apparatus for adaptive wall filtering in spectral doppler ultrasound imaging |
| CN103926572A (en) * | 2014-03-28 | 2014-07-16 | 西安电子科技大学 | Clutter rejection method of self-adaption subspace for non-sidelooking airborne array radar |
| CN104237883A (en) * | 2014-09-15 | 2014-12-24 | 西安电子科技大学 | Airborne radar space time self-adaptation processing method with sparse representation |
-
2016
- 2016-01-29 CN CN201610067201.2A patent/CN105738887B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1218185A (en) * | 1998-12-14 | 1999-06-02 | 中国人民解放军空军雷达学院 | Method for processing space-time multibeam adaptive signals |
| EP1067400A2 (en) * | 1999-07-09 | 2001-01-10 | General Electric Company | Method and apparatus for adaptive wall filtering in spectral doppler ultrasound imaging |
| CN103926572A (en) * | 2014-03-28 | 2014-07-16 | 西安电子科技大学 | Clutter rejection method of self-adaption subspace for non-sidelooking airborne array radar |
| CN104237883A (en) * | 2014-09-15 | 2014-12-24 | 西安电子科技大学 | Airborne radar space time self-adaptation processing method with sparse representation |
Non-Patent Citations (2)
| Title |
|---|
| Adaptively iterative weighting covariance matrix estimation for airborne radar clutter suppression;Baoquan Dai et.al;《Signal Processing》;20140814;第282-293页 * |
| 机载雷达优化多普勒和差通道杂波抑制方法;杨海峰等;《空军雷达学院学报》;20120831;第26卷(第4期);第240-243页 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN105738887A (en) | 2016-07-06 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN105738887B (en) | The optimization method of airborne radar clutter power spectrum based on the division of Doppler's passage | |
| CN109116311B (en) | Clutter suppression method based on knowledge-aided sparse iteration covariance estimation | |
| CN104035095B (en) | Based on the low level wind shear velocity estimation method of optimal processor during sky | |
| CN103176168B (en) | A kind of airborne non-working side battle array radar short range clutter cancellation method | |
| CN108387884B (en) | Airborne radar clutter suppression method based on knowledge-assisted sparse progressive minimum variance | |
| CN106772253B (en) | Radar clutter suppression method under non-uniform clutter environment | |
| CN108020817A (en) | Air-borne Forward-looking battle array radar clutter suppression method based on registration | |
| CN108957419B (en) | Asynchronous interference suppression method based on notch filtering processing | |
| CN109765529B (en) | Millimeter wave radar anti-interference method and system based on digital beam forming | |
| CN107942295B (en) | Sparse antenna of forward-looking array SAR system | |
| CN110554391B (en) | Low-altitude wind shear wind speed estimation method based on DDD-GMB | |
| CN114781190B (en) | Radar detection capability simulation method and device | |
| CN111220955B (en) | Airborne weather radar ground clutter suppression method based on vertical array covariance matrix characteristic decomposition | |
| CN106405557B (en) | A kind of radar detecting method for helicopter anticollision high-voltage line | |
| CN104280566A (en) | Low altitude wind shear wind speed estimation method based on space-time amplitude and phase estimation | |
| CN107976673A (en) | Improve the MIMO radar imaging method of large scene target imaging quality | |
| CN106291476B (en) | The Radar Clutter acquisition methods of airborne three-dimensional isomery battle array | |
| CN112098999A (en) | High-dynamic radar seeker sea-grazing target electromagnetic signal modeling method | |
| CN108152836A (en) | A kind of deception measures based on the anti-Samsung frequency difference location method of FDA antennas | |
| CN109932696A (en) | Digital beam froming method based on radar channel noise power | |
| CN106291547B (en) | Doppler ambiguity component Adaptive Suppression method based on antenna radiation pattern auxiliary | |
| CN108761417B (en) | Airborne radar clutter suppression method based on knowledge-aided maximum likelihood | |
| US20180074180A1 (en) | Ultrafast target detection based on microwave metamaterials | |
| CN113376625A (en) | Method and device for obtaining deviation angle of target object, electronic equipment and storage medium | |
| CN104914421A (en) | Low-altitude wind shear wind speed estimating method based on sum-difference beam |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |