CN105496702A - Surgical nursing dressing-changing device - Google Patents

Abstract

The invention discloses a surgical nursing dressing-changing device. A cart body is spatially divided into four parts by a first partition, a second partition and a third partition, a guide-in channel is located in the upper portion of the right end of the cart body, and a refuse box is optionally placed in the right space right below the guide-in channel; an ultraviolet generator is disposed at the lower end of the first partition, a storage battery is mounted at the lower end of the third partition, a first door plate is disposed in the front of the cart body and is connected with the cart body through hinges, the first door plate is provided with a first handle, an armrest is located at the rightmost end of the cart body, rollers are disposed below the cart body, a second door plate is mounted on the right end surface of the cart body and is connected with the cart body through hinges, and the second door plate is provided with a second handle. The problems are solved that a dressing-changing device cannot be sterilized in time and changed waste is abandoned at discretion, and the surgical nursing dressing-changing device is convenient for nursing staff to use.

Description

A kind of surgical nursing dressing change device

Technical field

The invention belongs to surgical nursing auxiliary device, particularly relate to a kind of surgical nursing dressing change device.

Background technology

The existing dressing change cart for surgical nursing does not have decontaminating apparatus, and dressing change in surgical department utensil is placed on dressing change cart and exposes in atmosphere, is easy to cause secondary pollution.And what the garbage changed was careless is discarded in refuse bin, be also easy to cause cross-contamination.

Summary of the invention

The object of the present invention is to provide a kind of surgical nursing dressing change device, be intended to solve implement for changing fresh dressing for wound and can not disinfect and change the problem that garbage arbitrarily abandons in time.

The present invention realizes like this, a kind of surgical nursing dressing change device, this surgical nursing dressing change device comprises: car body, the first dividing plate, the first door-plate, the first in command, second partition, lead-in groove, refuse bin, handrail, roller, accumulator, the 3rd dividing plate, ultraviolet ray generating apparatus, the second door-plate, the second in command;

Space is divided into four parts by the first dividing plate, second partition, the 3rd dividing plate by described car body, and lead-in groove is positioned on the upside of the right-hand member of car body, and refuse bin is freely placed on rightward space, immediately below lead-in groove; Ultraviolet ray generating apparatus is arranged on the first dividing plate lower end, accumulator is arranged on the 3rd dividing plate lower end, the front side of car body is provided with the first door-plate, first door-plate and car body are by gemel connection, and the first door-plate is provided with the first in command, and handrail is positioned at the low order end of car body, roller is provided with below car body, car body right side is provided with the second door-plate, and the second door-plate and car body, by gemel connection, the second door-plate are provided with the second in command; First door-plate inside is provided with safety device;

Described ultraviolet ray generating apparatus comprises: biosensor, ultraviolet generation module, sterilization control module, microprocessor, automatic cleaning apparatus, supply module;

Biosensor is connected with microprocessor, for responsive to biological substance and its concentration is converted to the signal of telecommunication;

Ultraviolet generation module is connected with microprocessor, under control of the microprocessor, realizes ultraviolet disinfection for generation of ultraviolet;

Sterilization control module is connected with microprocessor, under control of the microprocessor, for realizing the unlatching of sterilization pattern;

Microprocessor, the signal of telecommunication is reverted back original concentration data by calculation process through processor after receiving the signal of telecommunication of biosensor again, and compares with the concentration threshold stored in the program of the inside of processor; The threshold value that the concentration of the biological substance received is arranged lower than user;

Automatic cleaning apparatus is connected with microprocessor, for the clean quartz burner of the interval timing of the setting according to user;

Supply module is connected with microprocessor, for providing stable power supply for supply module;

Described car body entirety is stainless steel;

Described safety device comprises fault alarm loudspeaker, GPRS communication set, heat dissipation box and alarm lamp, disinfecting tube and antiseptic solution bottle, described fault alarm loudspeaker are arranged on the lower left side of GPRS communication set by being electrically connected, described antiseptic solution bottle is arranged on the bottom of disinfecting tube; Described heat dissipation box is arranged on the right side of alarming horn by being electrically connected, the exhaust fan that described heat dissipation box specifically adopts radiating fin to form; Described alarm lamp is arranged on the bottom of heat dissipation box by being electrically connected, described alarm lamp specifically adopts LED red alarm lamp; Described disinfecting tube is specifically arranged on the top of antiseptic solution bottle, and described disinfecting tube specifically adopts multiple ultraviolet disinfecting lamp tube; FPGA module and digital matched filter are set in GPRS communication set;

Described FPGA module comprises:

For obtaining the first sample circuit unit of the voltage difference that tested end produces;

Be connected with the first sample circuit unit, for improving the first pre-amplification circuit unit that signal to noise ratio is disturbed with noise decrease factor;

Be connected with the first pre-amplification circuit unit, for being reduced to the first automatic gain control circuit unit when rated current is less than 20%, working signal amplified at operating current;

Be connected with the first automatic gain control circuit unit, for suppressing the first filter circuit unit of higher hamonic wave in sampled signal;

Be connected with the first filter circuit unit, for first sample holding unit of keeping in the voltage difference being obtained the generation of tested end by the first filter circuit unit filtering first sample circuit unit;

Be connected with the first sample holding unit, the analogue signal producing voltage difference for the first sample circuit unit being obtained tested end is converted to the first a/d converter unit of digital signal;

Be connected with the first a/d converter unit, the second a/d converter unit, zero-crossing pulse unit, for to the digital signal of the first a/d converter cell translation and the Digital Signal Processing of standard secondary side sample circuit, carry out sampling analysis, find out the amplitude of first-harmonic, then obtain ratio and phase contrast according to division equations; According to zero-crossing pulse, timesharing samples, and as sampling markers, obtains the in-phase component FPGA digital signal processing circuit unit of difference and normal end;

For obtaining the second sample circuit unit of signal on normal end;

Be connected with the second sample circuit unit, for improving the second pre-amplification circuit unit that signal to noise ratio is disturbed with noise decrease factor;

Be connected with the second pre-amplification circuit unit, for being reduced to the second automatic gain control circuit unit when rated current is less than 20%, working signal amplified at operating current;

With the second pre-amplification circuit unit, for being realized the ac/dc inverter unit of AC and DC conversion by full-wave rectifying circuit;

Be connected with the second automatic gain control circuit unit, for suppressing the second filter circuit unit of higher hamonic wave in sampled signal;

Be connected with the second filter circuit unit, for the formation of the signal of waveform standard, input FPGA is as the shaping circuit unit of 0 ° of triggering signal;

Being connected with shaping circuit unit, for receiving the waveshape signal of shaping circuit unit, signal being carried out to the zero-crossing pulse unit of zero-crossing pulse process;

Be connected with the second filter circuit unit, for second sample holding unit of keeping in the signal of the second filter circuit unit;

Be connected with the second sample holding unit, the analogue signal for the second sample circuit unit being obtained signal on normal end is converted to the second a/d converter unit of digital signal;

Be connected with the first automatic gain control circuit unit, the second automatic gain control circuit unit and ac/dc inverter unit, for amplifying to the direct current signal after the rectification of ac/dc inverter unit and the first automatic gain control circuit unit, the second automatic gain control circuit cell operation signal the dial gauge unit shown.

Further, described digital matched filter comprises:

Gathered each sampled value is carried out to the A/D modular converter of sample quantization;

Be connected with described A/D modular converter, n the sampling in front and back for same for image data chip is carried out separates, obtain odd and the even sequence data on I road and Q road, to the serial/parallel conversion module that odd and the even sequence data on the I road obtained and Q road export;

Be connected with described serial/parallel conversion module, for receiving the I road and the odd on Q road and even sequence data that described serial/parallel conversion module exports, by Golay sequence correlator, the odd on received I road and Q road and even sequence data are carried out to the matched filtering module of Data Matching;

Be connected with described matched filtering module, become original I road and Q circuit-switched data sequence with Q road odd with even recovered data sequence for the I road described matched filtering module exported, and to the parallel/serial modular converter that original I road and Q circuit-switched data sequence export;

Be connected with described parallel/serial modular converter, for receiving original I road and the Q circuit-switched data sequence of described parallel/serial modular converter output, quadratic sum is asked to original I road and Q circuit-switched data sequence, and ask the result of quadratic sum to export to original I road and Q circuit-switched data sequence ask quadratic sum module;

Be connected with described quadratic sum module of asking, ask the result of quadratic sum to carry out peakvalue's checking for the original I road of asking quadratic sum module to export to described and Q circuit-switched data sequence, realize the coherent detection module that main synchronizing sequence is synchronous;

Be provided with multiple sub-matched filter in described matched filtering module, if carry out the sampling of n secondary data, then need each chip samples value on I road and Q road to enter a 2n in parallel sub-matched filter respectively;

Described quadratic sum module of asking adopts look-up method to ask square original I road and Q circuit-switched data sequence, adopts the summation of exampleization quaternary rechoning by the abacus adder, the realization of utilization carry look ahead chain;

Describedly the quaternary rechoning by the abacus adder in quadratic sum module is asked to be asynchronous serial rechoning by the abacus adder, adopt two weights be 5 high pearl and 5 weights be 1 low pearl structure, a unit can represent that decimal range is 0-15, it is just in time a quarternary numerical representation scope, simultaneously because squared results is 24bit, adopt exampleization statement to copy the adder unit of 6 quarternary full adders, six quaternary adder units adopt the method for carry look ahead chain to carry out cascade;

When 2 samplings in the front and back that described serial/parallel conversion module carries out same chip separately, each sampled value carried out 4bit quantize time, namely 4bitI road and 4bitQ road are converted to parallel 4bitI road odd numbered sequences, 4bitI road even order, 4bitQ road odd numbered sequences and 4bitQ road even order, matched filtering module is entered respectively to four tunnel sequences and carries out related operation, and convert result to the I road sequence of 12bit and the Q road sequence of 12bit through parallel/serial modular converter;

The transfer function of described sub-matched filter is: c _ibe modulated by hierarchical sequence u, v, u is hierarchical Golay sequence u={1,1,1,1,1,1 ,-1 ,-1,1 ,-1,1 ,-1,1, and-1 ,-1,1}, v={1,1,1 ,-1 ,-1,1 ,-1 ,-1,1,1,1 ,-1,1 ,-1,1,1}, C _16m+n=u _nv _m;

$H\left(z\right)=X\left(z\right)=C\left(z\right)=\underset{t=0}{\overset{L_u{L}_v-1}{\Σ}}{C}_t{z}^{-t}=\underset{t=0}{\overset{L_u{L}_v-1}{\Σ}}{C}_{16m+n}{z}^{-(16m+n)}=\underset{t=1}{\overset{L_v-1}{\Σ}}{u}_u{z}^{-n}\underset{t=1}{\overset{L_v-1}{\Σ}}{v}_m{z}^{-16m}=H\left(z_u\right)H\left(z_v\right),$ Golay sequence pair transfer function according to layering is improved, then have:

H(z _u)＝[1+z ^-8+z ^-1(1-z ^-8)][1+z ^-4+z ^-2(1-z ^-4)]；

H(z _v)＝(1+z ^-1)[1-z ^-6+z ^-8+z ^-14]+(1-z ^-1)[z ^-2-z ^-4+z ^-10+z ^-12]；

Described coherent detection module adopts bubbling relative method, namely the correlation of adjacent moment compares a higher value stored in depositor A, the position of higher value is stored in depositor B, constantly update, until there is identical value, detect position and whether differ the code length cycle, if, just carry out one-time detection again, continuous both sides detect and are just considered as acquisition success;

Described matched filtering module is formed primarily of delay unit and multiplicaton addition unit, and delay unit adopts d type flip flop to realize, and multiplicaton addition unit adopts common taking advantage of to add module; Described matched filtering module realizes Golay sequence capturing, and sequence enters matched filter by input, and carry out displacement and take advantage of and add, and result exported, when there being Golay sequence by matched filter, matched filter exports maximum 256.

Further, the synchronized orthogonal Frequency Hopping Signal blind source separation method of described microprocessor comprises the following steps:

Step one, utilizes the array antenna received containing M array element from the Frequency Hopping Signal of multiple synchronized orthogonal frequency hopping radio set, samples to each road Received signal strength, obtains the M road discrete time-domain mixed signal after sampling $\begin{array}{cc}{\tilde{x}}_m\left(k\right)(k=1,2,\mathrm{....})& m=1,2,\mathrm{...},M\end{array};$

Step 2, carries out overlapping windowing Short Time Fourier Transform to M road discrete time-domain mixed signal, obtains the time-frequency domain matrix of M mixed signal wherein P represents total window number, N _fftrepresent FFT transform length;

Step 3, to the frequency-hopping mixing signal time-frequency domain matrix obtained in step 2 carry out pretreatment;

Step 4, utilizes clustering algorithm to estimate each jumping moment of jumping and each normalized hybrid matrix column vector, Hopping frequencies of jumping correspondence;

According to step 4, step 5, estimates that the normalization hybrid matrix column vector obtained estimates time-frequency domain frequency hopping synthesizer signal;

Step 6, splices the time-frequency domain frequency hopping synthesizer signal between different frequency hopping point;

Step 7, according to source signal time-frequency domain estimated value, recovers time domain frequency hopping synthesizer signal.

Further, in step 2, (p, q) represents time-frequency index, and concrete time-frequency value is here N _fftrepresent the length of FFT conversion, p represents windowing number of times, T _srepresent the sampling interval, f _srepresent sample frequency, C is integer, represents the sampling number at Short Time Fourier Transform windowing interval, C < N _fft, and K _c=N _fft/ C is integer, and what that is adopt is the Short Time Fourier Transform of overlapping windowing.

Further, in step 3, to frequency-hopping mixing signal time-frequency domain matrix carry out pretreatment, specifically comprise following two steps:

The first step is right carry out low-yield pretreatment, namely at each sampling instant p, will the value that amplitude is less than thresholding ε sets to 0, and obtains the setting of thresholding ε can be determined according to the average energy of Received signal strength;

Second step, find out the p moment (p=0,1,2 ... P-1) the time-frequency domain data of non-zero, use represent, wherein represent the response of p moment time-frequency frequency indices corresponding time non-zero, to these non-zero normalization pretreatment, obtains pretreated vectorial b (p, q)=[b ₁(p, q), b ₂(p, q) ..., b _m(p, q)] ^t, wherein

Further, in step 4, when utilizing clustering algorithm to estimate normalized hybrid matrix column vector, the Hopping frequencies of each jumping moment of jumping and each jumping correspondence, comprise the following steps:

The first step, p (p=0,1,2 ... P-1) moment, right the frequency values represented carries out cluster, the cluster centre number obtained represent the carrier frequency number that the p moment exists, individual cluster centre then represents the size of carrier frequency, uses respectively represent;

Second step, to each sampling instant p (p=0,1,2 ... P-1), utilize clustering algorithm pair carry out cluster, can obtain equally individual cluster centre, uses represent;

3rd step, to all average and round, obtaining the estimation of source signal number namely

$\hat{N}=round\left(\frac{1}{p}\underset{p=0}{\overset{P-1}{\&Sigma;}}{\hat{N}}_p\right);$

4th step, finds out in all moment, use p _hrepresent, to the p of each section of continuous value _hask intermediate value, use represent that l section is connected p _hintermediate value, then represent the estimation in l frequency hopping moment;

5th step, according to what estimate in second step to obtain and the 4th estimates that the frequency hopping moment obtained estimates each and jumps corresponding in step individual hybrid matrix column vector concrete formula is:

${\hat{a}}_n\left(l\right)=\left\{\begin{array}{cc}\frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}\&CenterDot;\underset{p=1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}{\&Sigma;}}{b}_{n,p}^0& l=1,\\ \frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(l\right)-{\stackrel{\&OverBar;}{p}}_h(l-1)}\&CenterDot;\underset{p={\stackrel{\&OverBar;}{p}}_h(l-1)+1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(l\right)}{\&Sigma;}}{b}_{n,p}^0& l>1,\end{array}\right.n=1,2,\mathrm{...},\hat{N}$

Here $\begin{array}{cc}{\hat{a}}_n\left(l\right)={\&lsqb;{\hat{a}}_{n,1}\left(l\right),{\hat{a}}_{n,2}\left(i\right),\mathrm{...},{\hat{a}}_{n,M}\left(i\right)\&rsqb;}^T& (n=1,2,\mathrm{...},\hat{N})\end{array}$ Represent that l jumps corresponding individual hybrid matrix column vector estimated value;

6th step, estimates that each jumps corresponding carrier frequency, uses represent that l jumps corresponding individual frequency estimation, computing formula is as follows:

${\hat{f}}_{c,n}\left(l\right)=\left\{\begin{array}{cc}\frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}\&CenterDot;\underset{p=1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}{\&Sigma;}}{f}_o^n\left(p\right)& l=1,\\ \frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(l\right)-{\stackrel{\&OverBar;}{p}}_h(l-1)}\&CenterDot;\underset{p={\stackrel{\&OverBar;}{p}}_h(l-1)+1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(l\right)}{\&Sigma;}}{f}_o^n& l>1.\end{array}\right.n=1,2,\mathrm{...},\hat{N}.$

Further, in step 5, estimate time-frequency domain frequency hopping synthesizer signal according to the normalization hybrid matrix column vector estimating in step 4 to obtain, concrete steps are as follows:

The first step, judge which this moment index belongs to and jump to all sampling instant index p, concrete grammar is: if then represent that moment p belongs to l and jumps; If then represent that moment p belongs to the 1st and jumps;

Second step, to l (l=1,2 ...) all moment p of jumping _l, estimate the time-frequency domain data of each frequency hopping synthesizer signal of this jumping, computing formula is as follows:

$\left\{\begin{array}{c}{\tilde{S}}_j(p_l,q)=\frac{1}{\left|\right|{\hat{a}}_j\left(l\right)|{|}^2}\&CenterDot;{\hat{a}}_j^H\left(l\right)\&times;\left[\begin{array}{c}{\tilde{X}}_1(p_l,q)\\ {\tilde{X}}_2(p_l,q)\\ .\\ .\\ .\\ {\tilde{X}}_M(p_l,q)\end{array}\right]\\ j=\underset{j_0=1,2,\mathrm{...},\hat{N}}{\arg \max }\left(\right|{\&lsqb;{\tilde{X}}_1\left(p_l,q\right),{\tilde{X}}_2\left(p_l,q\right),\mathrm{...},{\tilde{X}}_M\left(p_l,q\right),\mathrm{...},{\tilde{X}}_M\left(p_l,q\right)\&rsqb;}^H\&times;{\hat{a}}_{j_0}\left(l\right)\left|\right)\\ \begin{array}{cc}{\tilde{S}}_m(p_l,q)=0& m=1,2,\mathrm{...},M,m\&NotEqual;j\end{array}\\ q=0,1,2,\mathrm{...},N_{fft}-1\end{array}\right.$

Further, in step 6, splice the time-frequency domain frequency hopping synthesizer signal between different frequency hopping point, concrete steps are as follows:

The first step, estimates that l jumps corresponding individual incident angle, uses represent that l jumps incident angle corresponding to the n-th source signal, computing formula as follows:

$\begin{array}{cc}{\widehat{\mathrm{\&theta;}}}_n\left(l\right)=\frac{1}{M-1}\underset{m=2}{\overset{M}{\&Sigma;}}{\sin }^{-1}\&lsqb;\frac{angle\left({\hat{a}}_{n,m}\right(l)/{\hat{a}}_{n,m-1}\left(l\right))*c}{2\mathrm{\&pi;}{\hat{f}}_{c,n}\left(l\right)d}\&rsqb;& n=1,2,\mathrm{...},\hat{N}\end{array}$

represent that l jumps the n-th hybrid matrix column vector estimating to obtain m element, c represents the light velocity, i.e. v _c=3 × 10 ⁸meter per second;

Second step, judge l (l=2,3 ...) and jump the source signal and first estimated and jump corresponding relation between the source signal estimated, judgment formula is as follows:

${m_n}^{\left(l\right)}=\underset{m}{\arg \min }|{\widehat{\mathrm{\&theta;}}}_m^{\left(l\right)}-{\widehat{\mathrm{\&theta;}}}_n^{\left(1\right)}|,n=1,2,\mathrm{...},\hat{N}$

Wherein m _n ^(l)represent that l jumps the m estimated _n ^(l)individual signal and first is jumped the n-th signal estimated and is belonged to same source signal;

3rd step, by different frequency hopping point estimation to the signal belonging to same source signal be stitched together, as final time-frequency domain source signal estimate, use Y _n(p, q) represents the time-frequency domain estimated value of the n-th source signal in time frequency point (p, q), p=0,1,2 ...., P, q=0,1,2 ..., N _fft-1, namely

Further, in step 7, when recovering time domain frequency hopping synthesizer signal according to source signal time-frequency domain estimated value, concrete steps are as follows:

The first step, to each sampling instant p (p=0,1,2 ...) and frequency domain data Y _n(p, q), q=0,1,2 ..., N _fft-1 is N _fftthe IFFT conversion of point, obtains the time domain frequency hopping synthesizer signal that p sampling instant is corresponding, uses y _n(p, q _t) (q _t=0,1,2 ..., N _fft-1) represent;

Second step, the time domain frequency hopping synthesizer signal y that above-mentioned all moment are obtained _n(p, q _t) carry out merging treatment, obtain final time domain frequency hopping synthesizer Signal estimation, concrete formula is as follows:

$s_n\&lsqb;kC:(k+1)C-1\&rsqb;=\left\{\begin{array}{cc}\underset{m=0}{\overset{k}{\&Sigma;}}{y}_n\&lsqb;m,(k-m)C:(k-m+1)C-1\&rsqb;& k<K_c\\ \underset{m=k-K_c+1}{\overset{k}{\&Sigma;}}{y}_n\&lsqb;m,(k-m)C:(k-m+1)C-1\&rsqb;& k\&GreaterEqual;K_c\end{array}\right.k=0,1,2,\mathrm{...}$

Here K _c=N _fft/ C, C are the sampling number at Short Time Fourier Transform windowing interval, N _fftfor the length of FFT conversion.

Surgical nursing dressing change device provided by the invention is accompanied with ultraviolet ray generating apparatus, can the medical apparatus of dressing change in surgical department be put in the chamber with ultraviolet ray generating apparatus, the medicines such as the common liquid medicine with medicine bottle are put to above the first dividing plate, the garbage changed is rendered to by lead-in groove in the refuse bin in car body by nursing staff, thus solves implement for changing fresh dressing for wound and can not disinfect and change the problem that garbage arbitrarily abandons in time.Digital matched filter of the present invention, A/D modular converter carries out sample quantization to gathered each sampled value, serial/parallel conversion module separates n the sampling in front and back that same for image data chip carries out, obtain odd and the even sequence data on I road and Q road, matched filtering module carries out Data Matching by Golay sequence correlator to the odd on received I road and Q road and even sequence data, the I road that matched filtering module exports by parallel/serial modular converter and Q road odd become original I road and Q circuit-switched data sequence with even recovered data sequence, quadratic sum module is asked to ask quadratic sum to original I road and Q circuit-switched data sequence, coherent detection module asks the result of quadratic sum to carry out peakvalue's checking to the original I road asking quadratic sum module to export and Q circuit-switched data sequence, realize main synchronizing sequence synchronous, while matched filtering module decreases hardware resource, improve data processing speed, in the slot synchronization of communication system cell search, synchronizing sequence can be caught rapidly, improve the probability of coherent detection, reduce false-alarm probability largely.Synchronized orthogonal Frequency Hopping Signal blind source separation method of the present invention, under the condition of not knowing any channel information, only according to the mixed signal of the multiple Frequency Hopping Signals received, estimate frequency hopping synthesizer signal, can under reception antenna number be less than the condition of source signal number, blind estimate is carried out to multiple Frequency Hopping Signal, with only Short Time Fourier Transform, amount of calculation is little, easy realization, the method, while carrying out blind separation to Frequency Hopping Signal, can also be estimated partial parameters, practical, there is stronger propagation and employment and be worth.

Accompanying drawing explanation

Fig. 1 is the surgical nursing dressing change device structural front view that the embodiment of the present invention provides;

Fig. 2 is the surgical nursing dressing change device structure right view that the embodiment of the present invention provides;

In figure: 1, car body; 2, the first dividing plate; 3, the first door-plate; 4, the first in command; 5, second partition; 6, lead-in groove; 7, refuse bin; 8, handrail; 9, roller; 10, accumulator; 11, the 3rd dividing plate; 12, ultraviolet ray generating apparatus; 13, the second door-plate; 14, the second in command.

Detailed description of the invention

In order to make object of the present invention, technical scheme and advantage clearly understand, below in conjunction with embodiment, the present invention is further elaborated.Should be appreciated that specific embodiment described herein only in order to explain the present invention, be not intended to limit the present invention.

Below in conjunction with drawings and the specific embodiments, application principle of the present invention is further described.

A kind of surgical nursing dressing change device, it is characterized in that, this surgical nursing dressing change device comprises: car body 1, first dividing plate 2, first door-plate 3, the first in command 4, second partition 5, lead-in groove 6, refuse bin 7, handrail 8, roller 9, accumulator 10, the 3rd dividing plate 11, ultraviolet ray generating apparatus 12, second door-plate 13, the second in command 14;

Space is divided into four parts by the first dividing plate 2, second partition 5, the 3rd dividing plate 11 by car body 1, and lead-in groove 6 is positioned on the upside of the right-hand member of car body 1, and refuse bin 7 is freely placed on rightward space, immediately below lead-in groove 6; Ultraviolet ray generating apparatus 12 is arranged on the first dividing plate 2 lower end, accumulator 10 is arranged on the 3rd dividing plate 11 lower end, the front side of car body 1 is provided with the first door-plate 3, first door-plate 3 and car body 1 pass through gemel connection, first door-plate 3 is provided with the first in command 4, handrail 8 is positioned at the low order end of car body 1, car body 1 is provided with roller 9 below, car body 1 right side is provided with the second door-plate 13, second door-plate 13 passes through gemel connection with car body 1, second door-plate 13 is provided with the second in command 14, and 3 first door-plate inside are provided with safety device.

Described ultraviolet ray generating apparatus comprises: biosensor, ultraviolet generation module, sterilization control module, microprocessor, automatic cleaning apparatus, supply module;

Biosensor is connected with microprocessor, for responsive to biological substance and its concentration is converted to the signal of telecommunication;

Ultraviolet generation module is connected with microprocessor, under control of the microprocessor, realizes ultraviolet disinfection for generation of ultraviolet;

Sterilization control module is connected with microprocessor, under control of the microprocessor, for realizing the unlatching of sterilization pattern;

Microprocessor, the signal of telecommunication is reverted back original concentration data by calculation process through processor after receiving the signal of telecommunication of biosensor again, and compares with the concentration threshold stored in the program of the inside of processor; The threshold value that the concentration of the biological substance received is arranged lower than user;

Automatic cleaning apparatus is connected with microprocessor, for the clean quartz burner of the interval timing of the setting according to user;

Supply module is connected with microprocessor, for providing stable power supply for supply module; Described safety device comprises fault alarm loudspeaker, GPRS communication set, heat dissipation box and alarm lamp, disinfecting tube and antiseptic solution bottle, described fault alarm loudspeaker are arranged on the lower left side of GPRS communication set by being electrically connected, described antiseptic solution bottle is arranged on the bottom of disinfecting tube; Described heat dissipation box is arranged on the right side of alarming horn by being electrically connected, the exhaust fan that described heat dissipation box specifically adopts radiating fin to form; Described alarm lamp is arranged on the bottom of heat dissipation box by being electrically connected, described alarm lamp specifically adopts LED red alarm lamp; Described disinfecting tube is specifically arranged on the top of antiseptic solution bottle, and described disinfecting tube specifically adopts multiple ultraviolet disinfecting lamp tube; FPGA module and digital matched filter are set in GPRS communication set;

Described FPGA module comprises:

For obtaining the first sample circuit unit of the voltage difference that tested end produces;

Be connected with the first sample circuit unit, for improving the first pre-amplification circuit unit that signal to noise ratio is disturbed with noise decrease factor;

Be connected with the first pre-amplification circuit unit, for being reduced to the first automatic gain control circuit unit when rated current is less than 20%, working signal amplified at operating current;

Be connected with the first automatic gain control circuit unit, for suppressing the first filter circuit unit of higher hamonic wave in sampled signal;

Be connected with the first filter circuit unit, for first sample holding unit of keeping in the voltage difference being obtained the generation of tested end by the first filter circuit unit filtering first sample circuit unit;

Be connected with the first sample holding unit, the analogue signal producing voltage difference for the first sample circuit unit being obtained tested end is converted to the first a/d converter unit of digital signal;

Be connected with the first a/d converter unit, the second a/d converter unit, zero-crossing pulse unit, for to the digital signal of the first a/d converter cell translation and the Digital Signal Processing of standard secondary side sample circuit, carry out sampling analysis, find out the amplitude of first-harmonic, then obtain ratio and phase contrast according to division equations; According to zero-crossing pulse, timesharing samples, and as sampling markers, obtains the in-phase component FPGA digital signal processing circuit unit of difference and normal end;

For obtaining the second sample circuit unit of signal on normal end;

Be connected with the second sample circuit unit, for improving the second pre-amplification circuit unit that signal to noise ratio is disturbed with noise decrease factor;

Be connected with the second pre-amplification circuit unit, for being reduced to the second automatic gain control circuit unit when rated current is less than 20%, working signal amplified at operating current;

With the second pre-amplification circuit unit, for being realized the ac/dc inverter unit of AC and DC conversion by full-wave rectifying circuit;

Be connected with the second automatic gain control circuit unit, for suppressing the second filter circuit unit of higher hamonic wave in sampled signal;

Be connected with the second filter circuit unit, for the formation of the signal of waveform standard, input FPGA is as the shaping circuit unit of 0 ° of triggering signal;

Being connected with shaping circuit unit, for receiving the waveshape signal of shaping circuit unit, signal being carried out to the zero-crossing pulse unit of zero-crossing pulse process;

Be connected with the second filter circuit unit, for second sample holding unit of keeping in the signal of the second filter circuit unit;

Be connected with the second sample holding unit, the analogue signal for the second sample circuit unit being obtained signal on normal end is converted to the second a/d converter unit of digital signal;

Be connected with the first automatic gain control circuit unit, the second automatic gain control circuit unit and ac/dc inverter unit, for amplifying to the direct current signal after the rectification of ac/dc inverter unit and the first automatic gain control circuit unit, the second automatic gain control circuit cell operation signal the dial gauge unit shown.

Described car body 1 entirety is stainless steel.

Described digital matched filter comprises:

Gathered each sampled value is carried out to the A/D modular converter of sample quantization;

Be connected with described A/D modular converter, n the sampling in front and back for same for image data chip is carried out separates, obtain odd and the even sequence data on I road and Q road, to the serial/parallel conversion module that odd and the even sequence data on the I road obtained and Q road export;

Be connected with described serial/parallel conversion module, for receiving the I road and the odd on Q road and even sequence data that described serial/parallel conversion module exports, by Golay sequence correlator, the odd on received I road and Q road and even sequence data are carried out to the matched filtering module of Data Matching;

Be connected with described matched filtering module, become original I road and Q circuit-switched data sequence with Q road odd with even recovered data sequence for the I road described matched filtering module exported, and to the parallel/serial modular converter that original I road and Q circuit-switched data sequence export;

Be connected with described parallel/serial modular converter, for receiving original I road and the Q circuit-switched data sequence of described parallel/serial modular converter output, quadratic sum is asked to original I road and Q circuit-switched data sequence, and ask the result of quadratic sum to export to original I road and Q circuit-switched data sequence ask quadratic sum module;

Be connected with described quadratic sum module of asking, ask the result of quadratic sum to carry out peakvalue's checking for the original I road of asking quadratic sum module to export to described and Q circuit-switched data sequence, realize the coherent detection module that main synchronizing sequence is synchronous;

Be provided with multiple sub-matched filter in described matched filtering module, if carry out the sampling of n secondary data, then need each chip samples value on I road and Q road to enter a 2n in parallel sub-matched filter respectively;

Described quadratic sum module of asking adopts look-up method to ask square original I road and Q circuit-switched data sequence, adopts the summation of exampleization quaternary rechoning by the abacus adder, the realization of utilization carry look ahead chain;

Describedly the quaternary rechoning by the abacus adder in quadratic sum module is asked to be asynchronous serial rechoning by the abacus adder, adopt two weights be 5 high pearl and 5 weights be 1 low pearl structure, a unit can represent that decimal range is 0-15, it is just in time a quarternary numerical representation scope, simultaneously because squared results is 24bit, adopt exampleization statement to copy the adder unit of 6 quarternary full adders, six quaternary adder units adopt the method for carry look ahead chain to carry out cascade;

When 2 samplings in the front and back that described serial/parallel conversion module carries out same chip separately, each sampled value carried out 4bit quantize time, namely 4bitI road and 4bitQ road are converted to parallel 4bitI road odd numbered sequences, 4bitI road even order, 4bitQ road odd numbered sequences and 4bitQ road even order, matched filtering module is entered respectively to four tunnel sequences and carries out related operation, and convert result to the I road sequence of 12bit and the Q road sequence of 12bit through parallel/serial modular converter;

The transfer function of described sub-matched filter is: c _ibe modulated by hierarchical sequence u, v, u is hierarchical Golay sequence u={1,1,1,1,1,1 ,-1 ,-1,1 ,-1,1 ,-1,1, and-1 ,-1,1}, v={1,1,1 ,-1 ,-1,1 ,-1 ,-1,1,1,1 ,-1,1 ,-1,1,1}, C _16m+n=u _nv _m;

$H\left(z\right)=X\left(z\right)=C\left(z\right)=\underset{t=0}{\overset{L_u{L}_v-1}{\&Sigma;}}{C}_t{z}^{-t}=\underset{t=0}{\overset{L_u{L}_v-1}{\&Sigma;}}{C}_{16m+n}{z}^{-(16m+n)}=\underset{t=1}{\overset{L_v-1}{\&Sigma;}}{u}_u{z}^{-n}\underset{t=1}{\overset{L_v-1}{\&Sigma;}}{v}_m{z}^{-16m}=H\left(z_u\right)H\left(z_v\right),$ Golay sequence pair transfer function according to layering is improved, then have:

H(z _u)＝[1+z ^-8+z ^-1(1-z ^-8)][1+z ^-4+z ^-2(1-z ^-4)]；

H(z _v)＝(1+z ^-1)[1-z ^-6+z ^-8+z ^-14]+(1-z ^-1)[z ^-2-z ^-4+z ^-10+z ^-12]；

Described coherent detection module adopts bubbling relative method, namely the correlation of adjacent moment compares a higher value stored in depositor A, the position of higher value is stored in depositor B, constantly update, until there is identical value, detect position and whether differ the code length cycle, if, just carry out one-time detection again, continuous both sides detect and are just considered as acquisition success;

Described matched filtering module is formed primarily of delay unit and multiplicaton addition unit, and delay unit adopts d type flip flop to realize, and multiplicaton addition unit adopts common taking advantage of to add module; Described matched filtering module realizes Golay sequence capturing, and sequence enters matched filter by input, and carry out displacement and take advantage of and add, and result exported, when there being Golay sequence by matched filter, matched filter exports maximum 256.

The synchronized orthogonal Frequency Hopping Signal blind source separation method of described microprocessor comprises the following steps:

Step one, utilizes the array antenna received containing M array element from the Frequency Hopping Signal of multiple synchronized orthogonal frequency hopping radio set, samples to each road Received signal strength, obtains the M road discrete time-domain mixed signal after sampling $\begin{array}{cc}{\tilde{x}}_m\left(k\right)(k=1,2,\mathrm{....})& m=1,2,\mathrm{...},M\end{array};$

Step 2, carries out overlapping windowing Short Time Fourier Transform to M road discrete time-domain mixed signal, obtains the time-frequency domain matrix of M mixed signal wherein P represents total window number, N _fftrepresent FFT transform length;

Step 3, to the frequency-hopping mixing signal time-frequency domain matrix obtained in step 2 carry out pretreatment;

Step 4, utilizes clustering algorithm to estimate each jumping moment of jumping and each normalized hybrid matrix column vector, Hopping frequencies of jumping correspondence;

According to step 4, step 5, estimates that the normalization hybrid matrix column vector obtained estimates time-frequency domain frequency hopping synthesizer signal;

Step 6, splices the time-frequency domain frequency hopping synthesizer signal between different frequency hopping point;

Step 7, according to source signal time-frequency domain estimated value, recovers time domain frequency hopping synthesizer signal.

In step 2, (p, q) represents time-frequency index, and concrete time-frequency value is here N _fftrepresent the length of FFT conversion, p represents windowing number of times, T _srepresent the sampling interval, f _srepresent sample frequency, C is integer, represents the sampling number at Short Time Fourier Transform windowing interval, C < N _fft, and K _c=N _fft/ C is integer, and what that is adopt is the Short Time Fourier Transform of overlapping windowing.

In step 3, to frequency-hopping mixing signal time-frequency domain matrix carry out pretreatment, specifically comprise following two steps:

The first step is right carry out low-yield pretreatment, namely at each sampling instant p, will the value that amplitude is less than thresholding ε sets to 0, and obtains the setting of thresholding ε can be determined according to the average energy of Received signal strength;

Second step, find out the p moment (p=0,1,2 ... P-1) the time-frequency domain data of non-zero, use represent, wherein represent the response of p moment time-frequency frequency indices corresponding time non-zero, to these non-zero normalization pretreatment, obtains pretreated vectorial b (p, q)=[b ₁(p, q), b ₂(p, q) ..., b _m(p, q)] ^t, wherein

In step 4, when utilizing clustering algorithm to estimate normalized hybrid matrix column vector, the Hopping frequencies of each jumping moment of jumping and each jumping correspondence, comprise the following steps:

The first step, p (p=0,1,2 ... P-1) moment, right the frequency values represented carries out cluster, the cluster centre number obtained represent the carrier frequency number that the p moment exists, individual cluster centre then represents the size of carrier frequency, uses respectively represent;

Second step, to each sampling instant p (p=0,1,2 ... P-1), utilize clustering algorithm pair carry out cluster, can obtain equally individual cluster centre, uses represent;

3rd step, to all average and round, obtaining the estimation of source signal number namely

$\hat{N}=round\left(\frac{1}{p}\underset{p=0}{\overset{P-1}{\&Sigma;}}{\hat{N}}_p\right);$

4th step, finds out moment, use p _hrepresent, to the p of each section of continuous value _hask intermediate value, use represent that l section is connected p _hintermediate value, then represent the estimation in l frequency hopping moment;

5th step, according to what estimate in second step to obtain and the 4th estimates that the frequency hopping moment obtained estimates each and jumps corresponding in step individual hybrid matrix column vector concrete formula is:

${\hat{a}}_n\left(l\right)=\left\{\begin{array}{cc}\frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}\&CenterDot;\underset{p=1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}{\&Sigma;}}{b}_{n,p}^0& l=1,\\ \frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(l\right)-{\stackrel{\&OverBar;}{p}}_h(l-1)}\&CenterDot;\underset{p={\stackrel{\&OverBar;}{p}}_h(l-1)+1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(l\right)}{\&Sigma;}}{b}_{n,p}^0& l>1,\end{array}\right.n=1,2,\mathrm{...},\hat{N}$

Here $\begin{array}{cc}{\hat{a}}_n\left(l\right)={\&lsqb;{\hat{a}}_{n,1}\left(l\right),{\hat{a}}_{n,2}\left(l\right),\mathrm{...},{\hat{a}}_{n,M}\left(l\right)\&rsqb;}^T& (n=1,2,\mathrm{...},\hat{N})\end{array}$ Represent that l jumps corresponding individual hybrid matrix column vector estimated value;

6th step, estimates that each jumps corresponding carrier frequency, uses represent that l jumps corresponding individual frequency estimation, computing formula is as follows:

${\hat{f}}_{c,n}\left(l\right)=\left\{\begin{array}{cc}\frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}\&CenterDot;\underset{p=1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}{\&Sigma;}}{f}_o^n\left(p\right)& l=1,\\ \frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(l\right)-{\stackrel{\&OverBar;}{p}}_h(l-1)}\&CenterDot;\underset{p={\stackrel{\&OverBar;}{p}}_h(l-1)+1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(l\right)}{\&Sigma;}}{f}_o^n& l>1.\end{array}\right.n=1,2,\mathrm{...},\hat{N}.$

In step 5, estimate time-frequency domain frequency hopping synthesizer signal according to the normalization hybrid matrix column vector estimating in step 4 to obtain, concrete steps are as follows:

The first step, judge which this moment index belongs to and jump to all sampling instant index p, concrete grammar is: if then represent that moment P belongs to l and jumps; If then represent that moment P belongs to the 1st and jumps;

Second step, to l (l=1,2 ...) all moment p of jumping _l, estimate the time-frequency domain data of each frequency hopping synthesizer signal of this jumping, computing formula is as follows:

$\left\{\begin{array}{c}{\tilde{S}}_j(p_l,q)=\frac{1}{\left|\right|{\hat{a}}_j\left(l\right)|{|}^2}\&CenterDot;{\hat{a}}_j^H\left(l\right)\&times;\left[\begin{array}{c}{\tilde{X}}_1(p_l,q)\\ {\tilde{X}}_2(p_l,q)\\ .\\ .\\ .\\ {\tilde{X}}_M(p_l,q)\end{array}\right]\\ j=\underset{j_0=1,2,\mathrm{...},\hat{N}}{\arg \max }\left(\right|{\&lsqb;{\tilde{X}}_1\left(p_l,q\right),{\tilde{X}}_2\left(p_l,q\right),\mathrm{...},{\tilde{X}}_M\left(p_l,q\right),\mathrm{...},{\tilde{X}}_M\left(p_l,q\right)\&rsqb;}^H\&times;{\hat{a}}_{j_0}\left(l\right)\left|\right)\\ \begin{array}{cc}{\tilde{S}}_m(p_l,q)=0& m=1,2,\mathrm{...},M,m\&NotEqual;j\end{array}\\ q=0,1,2,\mathrm{...},N_{fft}-1\end{array}\right..$

In step 6, splice the time-frequency domain frequency hopping synthesizer signal between different frequency hopping point, concrete steps are as follows:

The first step, estimates that l jumps corresponding individual incident angle, uses represent that l jumps incident angle corresponding to the n-th source signal, computing formula as follows:

$\begin{array}{cc}{\widehat{\mathrm{\&theta;}}}_n\left(l\right)=\frac{1}{M-1}\underset{m=2}{\overset{M}{\&Sigma;}}{\sin }^{-1}\&lsqb;\frac{angle\left({\hat{a}}_{n,m}\right(l)/{\hat{a}}_{n,m-1}\left(l\right))*c}{2\mathrm{\&pi;}{\hat{f}}_{c,n}\left(l\right)d}\&rsqb;& n=1,2,\mathrm{...},\hat{N}\end{array}$

represent that l jumps the n-th hybrid matrix column vector estimating to obtain m element, c represents the light velocity, i.e. v _c=3 × 10 ⁸meter per second;

Second step, judge l (l=2,3 ...) and jump the source signal and first estimated and jump corresponding relation between the source signal estimated, judgment formula is as follows:

${m_n}^{\left(l\right)}=\underset{m}{\arg \min }|{\widehat{\mathrm{\&theta;}}}_m^{\left(l\right)}-{\widehat{\mathrm{\&theta;}}}_n^{\left(1\right)}|,n=1,2,\mathrm{...},\hat{N}$

Wherein m _n ^(l)represent that l jumps the m estimated _n ^(l)individual signal and first is jumped the n-th signal estimated and is belonged to same source signal;

3rd step, by different frequency hopping point estimation to the signal belonging to same source signal be stitched together, as final time-frequency domain source signal estimate, use Y _n(p, q) represents the time-frequency domain estimated value of the n-th source signal in time frequency point (p, q), p=0,1,2 ...., P, q=0,1,2 ..., N _fft-1, namely

In step 7, when recovering time domain frequency hopping synthesizer signal according to source signal time-frequency domain estimated value, concrete steps are as follows:

The first step, to each sampling instant p (p=0,1,2 ...) and frequency domain data Y _n(p, q), q=0,1,2 ..., N _fft-1 is N _fftthe IFFT conversion of point, obtains the time domain frequency hopping synthesizer signal that p sampling instant is corresponding, uses y _n(p, q _t) (q _t=0,1,2 ..., N _fft-1) represent;

Second step, the time domain frequency hopping synthesizer signal y that above-mentioned all moment are obtained _n(p, q _t) carry out merging treatment, obtain final time domain frequency hopping synthesizer Signal estimation, concrete formula is as follows:

$s_n\&lsqb;kC:(k+1)C-1\&rsqb;=\left\{\begin{array}{cc}\underset{m=0}{\overset{k}{\&Sigma;}}{y}_n\&lsqb;m,(k-m)C:(k-m+1)C-1\&rsqb;& k<K_c\\ \underset{m=k-K_c+1}{\overset{k}{\&Sigma;}}{y}_n\&lsqb;m,(k-m)C:(k-m+1)C-1\&rsqb;& k\&GreaterEqual;K_c\end{array}\right.k=0,1,2,\mathrm{...}$

Here K _c=N _fft/ C, C are the sampling number at Short Time Fourier Transform windowing interval, N _fftfor the length of FFT conversion.

The medical apparatus and instruments of changing dressings can be placed in the cavity between the first dividing plate 2 and the 3rd dividing plate 11 by nursing staff, inside was disinfected to medical apparatus and instruments by ultraviolet ray generating apparatus 12 moment, accumulator 10 gives ultraviolet ray generating apparatus 12 supply of electrical energy, liquid medicine and packed medicine are placed on above the first dividing plate 2 by nursing staff, also the garbage changed can be rendered to the refuse bin 7 li in car body 1 by lead-in groove 6, thus solve implement for changing fresh dressing for wound and can not disinfect and change the problem that garbage arbitrarily abandons in time.

The foregoing is only preferred embodiment of the present invention, not in order to limit the present invention, all any amendments done within the spirit and principles in the present invention, equivalent replacement and improvement etc., all should be included within protection scope of the present invention.

Claims (9)

1. a surgical nursing dressing change device, it is characterized in that, this surgical nursing dressing change device comprises: car body, the first dividing plate, the first door-plate, the first in command, second partition, lead-in groove, refuse bin, handrail, roller, accumulator, the 3rd dividing plate, ultraviolet ray generating apparatus, the second door-plate, the second in command;

Space is divided into four parts by the first dividing plate, second partition, the 3rd dividing plate by described car body, and lead-in groove is positioned on the upside of the right-hand member of car body, and refuse bin is freely placed on rightward space, immediately below lead-in groove; Ultraviolet ray generating apparatus is arranged on the first dividing plate lower end, accumulator is arranged on the 3rd dividing plate lower end, the front side of car body is provided with the first door-plate, first door-plate and car body are by gemel connection, and the first door-plate is provided with the first in command, and handrail is positioned at the low order end of car body, roller is provided with below car body, car body right side is provided with the second door-plate, and the second door-plate and car body, by gemel connection, the second door-plate are provided with the second in command; First door-plate inside is provided with safety device;

Described ultraviolet ray generating apparatus comprises: biosensor, ultraviolet generation module, sterilization control module, microprocessor, automatic cleaning apparatus, supply module;

Biosensor is connected with microprocessor, for responsive to biological substance and its concentration is converted to the signal of telecommunication;

Ultraviolet generation module is connected with microprocessor, under control of the microprocessor, realizes ultraviolet disinfection for generation of ultraviolet;

Sterilization control module is connected with microprocessor, under control of the microprocessor, for realizing the unlatching of sterilization pattern;

Microprocessor, the signal of telecommunication is reverted back original concentration data by calculation process through processor after receiving the signal of telecommunication of biosensor again, and compares with the concentration threshold stored in the program of the inside of processor; The threshold value that the concentration of the biological substance received is arranged lower than user;

Automatic cleaning apparatus is connected with microprocessor, for the clean quartz burner of the interval timing of the setting according to user;

Supply module is connected with microprocessor, for providing stable power supply for supply module;

Described car body entirety is stainless steel;

Described safety device comprises fault alarm loudspeaker, GPRS communication set, heat dissipation box and alarm lamp, disinfecting tube and antiseptic solution bottle, described fault alarm loudspeaker are arranged on the lower left side of GPRS communication set by being electrically connected, described antiseptic solution bottle is arranged on the bottom of disinfecting tube; Described heat dissipation box is arranged on the right side of alarming horn by being electrically connected, the exhaust fan that described heat dissipation box specifically adopts radiating fin to form; Described alarm lamp is arranged on the bottom of heat dissipation box by being electrically connected, described alarm lamp specifically adopts LED red alarm lamp; Described disinfecting tube is specifically arranged on the top of antiseptic solution bottle, and described disinfecting tube specifically adopts multiple ultraviolet disinfecting lamp tube; FPGA module and digital matched filter are set in GPRS communication set;

Described FPGA module comprises:

For obtaining the first sample circuit unit of the voltage difference that tested end produces;

Be connected with the first sample circuit unit, for improving the first pre-amplification circuit unit that signal to noise ratio is disturbed with noise decrease factor;

Be connected with the first pre-amplification circuit unit, for being reduced to the first automatic gain control circuit unit when rated current is less than 20%, working signal amplified at operating current;

Be connected with the first automatic gain control circuit unit, for suppressing the first filter circuit unit of higher hamonic wave in sampled signal;

Be connected with the first filter circuit unit, for first sample holding unit of keeping in the voltage difference being obtained the generation of tested end by the first filter circuit unit filtering first sample circuit unit;

Be connected with the first sample holding unit, the analogue signal producing voltage difference for the first sample circuit unit being obtained tested end is converted to the first a/d converter unit of digital signal;

Be connected with the first a/d converter unit, the second a/d converter unit, zero-crossing pulse unit, for to the digital signal of the first a/d converter cell translation and the Digital Signal Processing of standard secondary side sample circuit, carry out sampling analysis, find out the amplitude of first-harmonic, then obtain ratio and phase contrast according to division equations; According to zero-crossing pulse, timesharing samples, and as sampling markers, obtains the in-phase component FPGA digital signal processing circuit unit of difference and normal end;

For obtaining the second sample circuit unit of signal on normal end;

Be connected with the second sample circuit unit, for improving the second pre-amplification circuit unit that signal to noise ratio is disturbed with noise decrease factor;

Be connected with the second pre-amplification circuit unit, for being reduced to the second automatic gain control circuit unit when rated current is less than 20%, working signal amplified at operating current;

With the second pre-amplification circuit unit, for being realized the ac/dc inverter unit of AC and DC conversion by full-wave rectifying circuit;

Be connected with the second automatic gain control circuit unit, for suppressing the second filter circuit unit of higher hamonic wave in sampled signal;

Be connected with the second filter circuit unit, for the formation of the signal of waveform standard, input FPGA is as the shaping circuit unit of 0 ° of triggering signal;

Being connected with shaping circuit unit, for receiving the waveshape signal of shaping circuit unit, signal being carried out to the zero-crossing pulse unit of zero-crossing pulse process;

Be connected with the second filter circuit unit, for second sample holding unit of keeping in the signal of the second filter circuit unit;

Be connected with the second sample holding unit, the analogue signal for the second sample circuit unit being obtained signal on normal end is converted to the second a/d converter unit of digital signal;

Be connected with the first automatic gain control circuit unit, the second automatic gain control circuit unit and ac/dc inverter unit, for amplifying to the direct current signal after the rectification of ac/dc inverter unit and the first automatic gain control circuit unit, the second automatic gain control circuit cell operation signal the dial gauge unit shown.

2. surgical nursing dressing change device as claimed in claim 1, it is characterized in that, described digital matched filter comprises:

Gathered each sampled value is carried out to the A/D modular converter of sample quantization;

Be connected with described A/D modular converter, n the sampling in front and back for same for image data chip is carried out separates, obtain odd and the even sequence data on I road and Q road, to the serial/parallel conversion module that odd and the even sequence data on the I road obtained and Q road export;

Be connected with described serial/parallel conversion module, for receiving the I road and the odd on Q road and even sequence data that described serial/parallel conversion module exports, by Golay sequence correlator, the odd on received I road and Q road and even sequence data are carried out to the matched filtering module of Data Matching;

Be connected with described matched filtering module, become original I road and Q circuit-switched data sequence with Q road odd with even recovered data sequence for the I road described matched filtering module exported, and to the parallel/serial modular converter that original I road and Q circuit-switched data sequence export;

Be connected with described parallel/serial modular converter, for receiving original I road and the Q circuit-switched data sequence of described parallel/serial modular converter output, quadratic sum is asked to original I road and Q circuit-switched data sequence, and ask the result of quadratic sum to export to original I road and Q circuit-switched data sequence ask quadratic sum module;

Be connected with described quadratic sum module of asking, ask the result of quadratic sum to carry out peakvalue's checking for the original I road of asking quadratic sum module to export to described and Q circuit-switched data sequence, realize the coherent detection module that main synchronizing sequence is synchronous;

Be provided with multiple sub-matched filter in described matched filtering module, if carry out the sampling of n secondary data, then need each chip samples value on I road and Q road to enter a 2n in parallel sub-matched filter respectively;

Described quadratic sum module of asking adopts look-up method to ask square original I road and Q circuit-switched data sequence, adopts the summation of exampleization quaternary rechoning by the abacus adder, the realization of utilization carry look ahead chain;

Describedly the quaternary rechoning by the abacus adder in quadratic sum module is asked to be asynchronous serial rechoning by the abacus adder, adopt two weights be 5 high pearl and 5 weights be 1 low pearl structure, a unit can represent that decimal range is 0-15, it is just in time a quarternary numerical representation scope, simultaneously because squared results is 24bit, adopt exampleization statement to copy the adder unit of 6 quarternary full adders, six quaternary adder units adopt the method for carry look ahead chain to carry out cascade;

When 2 samplings in the front and back that described serial/parallel conversion module carries out same chip separately, each sampled value carried out 4bit quantize time, namely 4bitI road and 4bitQ road are converted to parallel 4bitI road odd numbered sequences, 4bitI road even order, 4bitQ road odd numbered sequences and 4bitQ road even order, matched filtering module is entered respectively to four tunnel sequences and carries out related operation, and convert result to the I road sequence of 12bit and the Q road sequence of 12bit through parallel/serial modular converter;

The transfer function of described sub-matched filter is: $H\left(z\right)=\underset{i=0}{\overset{N-1}{\&Sigma;}}{h}_i{z}^{-i}=\underset{i=0}{\overset{N-1}{\&Sigma;}}{x}_{N-1-i}{Z}^{-i}=X\left(z^{-1}\right)Z^{-(N-1)},$ C _ibe modulated by hierarchical sequence u, v, u is hierarchical Golay sequence u={1,1,1,1,1,1 ,-1 ,-1,1 ,-1,1 ,-1,1, and-1 ,-1,1}, v={1,1,1 ,-1 ,-1,1 ,-1 ,-1,1,1,1 ,-1,1 ,-1,1,1}, C _16m+n=u _nv _m;

$H\left(z\right)=X\left(z\right)=C\left(z\right)=\underset{i=0}{\overset{L_u{L}_v-1}{\&Sigma;}}{C}_i{z}^{-i}=\underset{i=0}{\overset{L_u{L}_v-1}{\&Sigma;}}{C}_{16m+n}{z}^{-(16m+n)}=\underset{i=1}{\overset{L_u-1}{\&Sigma;}}{u}_n{z}^{-n}\underset{i=1}{\overset{L_v-1}{\&Sigma;}}{v}_m{z}^{-16m}=H\left(z_u\right)H\left(z_v\right),$ Golay sequence pair transfer function according to layering is improved, then have:

H(z _u)＝[1+z ^-8+z ^-1(1-z ^-8)][1+z ^-4+z ^-2(1-z ^-4)]；

H(z _v)＝(1+z ^-1)[1-z ^-6+z ^-8+z ^-14]+(1-z ^-1)[z ^-2-z ^-4+z ^-10+z ^-12]；

Described coherent detection module adopts bubbling relative method, namely the correlation of adjacent moment compares a higher value stored in depositor A, the position of higher value is stored in depositor B, constantly update, until there is identical value, detect position and whether differ the code length cycle, if, just carry out one-time detection again, continuous both sides detect and are just considered as acquisition success;

Described matched filtering module is formed primarily of delay unit and multiplicaton addition unit, and delay unit adopts d type flip flop to realize, and multiplicaton addition unit adopts common taking advantage of to add module; Described matched filtering module realizes Golay sequence capturing, and sequence enters matched filter by input, and carry out displacement and take advantage of and add, and result exported, when there being Golay sequence by matched filter, matched filter exports maximum 256.

3. surgical nursing dressing change device as claimed in claim 1, it is characterized in that, the synchronized orthogonal Frequency Hopping Signal blind source separation method of described microprocessor comprises the following steps:

Step one, utilizes the array antenna received containing M array element from the Frequency Hopping Signal of multiple synchronized orthogonal frequency hopping radio set, samples to each road Received signal strength, obtains the M road discrete time-domain mixed signal after sampling ${\tilde{x}}_m\left(k\right),(k=1,2,....),m=1,2,...,M;$

Step 2, carries out overlapping windowing Short Time Fourier Transform to M road discrete time-domain mixed signal, obtains the time-frequency domain matrix of M mixed signal

P=0,1 ..., P-1, q=0,1 ..., N _fft-1, wherein P represents total window number, N _fftrepresent FFT transform length;

Step 3, to the frequency-hopping mixing signal time-frequency domain matrix obtained in step 2

carry out pretreatment;

Step 4, utilizes clustering algorithm to estimate each jumping moment of jumping and each normalized hybrid matrix column vector, Hopping frequencies of jumping correspondence;

According to step 4, step 5, estimates that the normalization hybrid matrix column vector obtained estimates time-frequency domain frequency hopping synthesizer signal;

Step 6, splices the time-frequency domain frequency hopping synthesizer signal between different frequency hopping point;

Step 7, according to source signal time-frequency domain estimated value, recovers time domain frequency hopping synthesizer signal.

4. surgical nursing dressing change device as claimed in claim 3, it is characterized in that, in step 2, (p, q) represents time-frequency index, and concrete time-frequency value is here N _fftrepresent the length of FFT conversion, p represents windowing number of times, T _srepresent the sampling interval, f _srepresent sample frequency, C is integer, represents the sampling number at Short Time Fourier Transform windowing interval, C < N _fft, and K _c=N _fft/ C is integer, and what that is adopt is the Short Time Fourier Transform of overlapping windowing.

5. surgical nursing dressing change device as claimed in claim 3, is characterized in that, in step 3, to frequency-hopping mixing signal time-frequency domain matrix carry out pretreatment, specifically comprise following two steps:

The first step is right carry out low-yield pretreatment, namely at each sampling instant p, will the value that amplitude is less than thresholding ε sets to 0, and obtains the setting of thresholding ε can be determined according to the average energy of Received signal strength;

Second step, find out the p moment (p=0,1,2 ... P-1) the time-frequency domain data of non-zero, use represent, wherein represent the response of p moment time-frequency frequency indices corresponding time non-zero, to these non-zero normalization pretreatment, obtains pretreated vectorial b (p, q)=[b ₁(p, q), b ₂(p, q) ..., b _m(p, q)] ^t, wherein

6. surgical nursing dressing change device as claimed in claim 3, is characterized in that, in step 4, when utilizing clustering algorithm to estimate normalized hybrid matrix column vector, the Hopping frequencies of each jumping moment of jumping and each jumping correspondence, comprises the following steps:

The first step, p (p=0,1,2 ... P-1) moment, right the frequency values represented carries out cluster, the cluster centre number obtained represent the carrier frequency number that the p moment exists, individual cluster centre then represents the size of carrier frequency, uses respectively represent;

Second step, to each sampling instant p (p=0,1,2 ... P-1), utilize clustering algorithm pair carry out cluster, can obtain equally individual cluster centre, uses represent;

3rd step, to all average and round, obtaining the estimation of source signal number namely

$\hat{N}=round\left(\frac{1}{p}\underset{p=0}{\overset{P-1}{\&Sigma;}}{\hat{N}}_p\right);$

4th step, finds out moment, use p _hrepresent, to the p of each section of continuous value _hask intermediate value, use represent that l section is connected p _hintermediate value, then represent the estimation in l frequency hopping moment;

5th step, according to what estimate in second step to obtain and the 4th estimates that the frequency hopping moment obtained estimates each and jumps corresponding in step individual hybrid matrix column vector concrete formula is:

${\hat{a}}_n\left(l\right)=\left\{\begin{array}{cc}\frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}\&CenterDot;\underset{p=1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}{\&Sigma;}}{b}_{n,p}^0& l=1,\\ \frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(l\right)-{\stackrel{\&OverBar;}{p}}_h(l-1)}\&CenterDot;\underset{p={\stackrel{\&OverBar;}{p}}_h(l-1)+1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(l\right)}{\&Sigma;}}{b}_{n,p}^0& l>1,\end{array}\right.n=1,2,...,\hat{N}$

Here ${\hat{a}}_n\left(l\right)={\&lsqb;{\hat{a}}_{n,1}\left(l\right),{\hat{a}}_{n,2}\left(l\right),...,{\hat{a}}_{n,M}\left(l\right)\&rsqb;}^T,(n=1,2,...,\hat{N})$ Represent that l jumps corresponding individual hybrid matrix column vector estimated value;

6th step, estimates that each jumps corresponding carrier frequency, uses represent that l jumps corresponding individual frequency estimation, computing formula is as follows:

${\hat{f}}_{c,n}\left(l\right)=\left\{\begin{array}{cc}\frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}\&CenterDot;\underset{p=1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(1\right)}{\&Sigma;}}{f}_o^n\left(p\right)& l=1,\\ \frac{1}{{\stackrel{\&OverBar;}{p}}_h\left(l\right)-{\stackrel{\&OverBar;}{p}}_h(l-1)}\&CenterDot;\underset{p={\stackrel{\&OverBar;}{p}}_h(l-1)+1,p\&NotEqual;p_h}{\overset{{\stackrel{\&OverBar;}{p}}_h\left(l\right)}{\&Sigma;}}{f}_o^n\left(p\right)& l>1,\end{array}\right.n=1,2,...,\hat{N}.$

7. surgical nursing dressing change device as claimed in claim 3, is characterized in that, in step 5, estimate time-frequency domain frequency hopping synthesizer signal according to the normalization hybrid matrix column vector estimating in step 4 to obtain, concrete steps are as follows:

The first step, judge which this moment index belongs to and jump to all sampling instant index p, concrete grammar is: if then represent that moment p belongs to l and jumps; If then represent that moment p belongs to the 1st and jumps;

Second step, to l (l=1,2 ...) all moment p of jumping _l, estimate the time-frequency domain data of each frequency hopping synthesizer signal of this jumping, computing formula is as follows:

$\left\{\begin{array}{c}{\tilde{S}}_j(p_l,q)=\frac{1}{\left|\right|{\hat{a}}_j\left(l\right)|{|}^2}\&CenterDot;{\hat{a}}_j^H\left(l\right)\&times;\left[\begin{array}{c}{\tilde{X}}_1(p_l,q)\\ {\tilde{X}}_2(p_l,q)\\ \&CenterDot;\\ \&CenterDot;\\ \&CenterDot;\\ {\tilde{X}}_M(p_l,q)\end{array}\right]\\ j=\underset{j_0=1,2,...,\hat{N}}{\arg \max }\left(\right|{\&lsqb;{\tilde{X}}_1(p_l,q),{\tilde{X}}_2(p_l,q),...,{\tilde{X}}_M(p_l,q)\&rsqb;}^H\&times;{\hat{a}}_{j_0}\left(l\right)\left|\right)\\ {\tilde{S}}_m(p_l,q)=0,m=1,2,...,M,m\&NotEqual;j\\ q=0,1,2,...,N_{fft}-1\end{array}\right..$

8. surgical nursing dressing change device as claimed in claim 3, it is characterized in that, in step 6, splice the time-frequency domain frequency hopping synthesizer signal between different frequency hopping point, concrete steps are as follows:

The first step, estimates that l jumps corresponding individual incident angle, uses represent that l jumps incident angle corresponding to the n-th source signal, computing formula as follows:

${\widehat{\mathrm{\&theta;}}}_n\left(l\right)=\frac{1}{M-1}\underset{m=2}{\overset{M}{\&Sigma;}}{\sin }^{-1}\&lsqb;\frac{angle\left({\hat{a}}_{n,m}\right(l)/{\hat{a}}_{n,m-1}\left(l\right))*c}{2\mathrm{\&pi;}{\hat{f}}_{c,n}\left(l\right)d}\&rsqb;,n=1,2,...,\hat{N}$

represent that l jumps the n-th hybrid matrix column vector estimating to obtain m element, c represents the light velocity, i.e. v _c=3 × 10 ⁸meter per second;

Second step, judge l (l=2,3 ...) and jump the source signal and first estimated and jump corresponding relation between the source signal estimated, judgment formula is as follows:

${m_n}^{\left(l\right)}=\underset{m}{\mathrm{argmin}}|{\widehat{\mathrm{\&theta;}}}_m^{\left(l\right)}-{\widehat{\mathrm{\&theta;}}}_n^{\left(1\right)}|,n=1,2,...,\hat{N}$

Wherein m _n ^(l)represent that l jumps the m estimated _n ^(l)individual signal and first is jumped the n-th signal estimated and is belonged to same source signal;

3rd step, by different frequency hopping point estimation to the signal belonging to same source signal be stitched together, as final time-frequency domain source signal estimate, use Y _n(p, q) represents the time-frequency domain estimated value of the n-th source signal in time frequency point (p, q), p=0,1,2 ...., P, q=0,1,2 ..., N _fft-1, namely

9. surgical nursing dressing change device as claimed in claim 3, is characterized in that, in step 7, when recovering time domain frequency hopping synthesizer signal according to source signal time-frequency domain estimated value, concrete steps are as follows:

The first step, to each sampling instant p (p=0,1,2 ...) and frequency domain data Y _n(p, q), q=0,1,2 ..., N _fft-1 is N _fftthe IFFT conversion of point, obtains the time domain frequency hopping synthesizer signal that p sampling instant is corresponding, uses y _n(p, q _t) (q _t=0,1,2 ..., N _fft-1) represent;

Second step, the time domain frequency hopping synthesizer signal y that above-mentioned all moment are obtained _n(p, q _t) carry out merging treatment, obtain final time domain frequency hopping synthesizer Signal estimation, concrete formula is as follows:

$s_n\&lsqb;kC:(k+1)C-1\&rsqb;=\left\{\begin{array}{cc}\underset{m=0}{\overset{k}{\mathrm{\&Sigma;}}}{y}_n\&lsqb;m,(k-m)C:(k-m+1)C-1\&rsqb;& k<K_c\\ \underset{m=k-K_c+1}{\overset{k}{\mathrm{\&Sigma;}}}{y}_n\&lsqb;m,(k-m)C:(k-m+1)C-1\&rsqb;& k\&GreaterEqual;K_c\end{array}\right.,k=0,1,2,...$

Here K _c=N _fft/ C, C are the sampling number at Short Time Fourier Transform windowing interval, N _fftfor the length of FFT conversion.