CN105375759A - Adjustment method for parallel operation of at least two self-oscillating switching converters - Google Patents
Adjustment method for parallel operation of at least two self-oscillating switching converters Download PDFInfo
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- CN105375759A CN105375759A CN201510506355.2A CN201510506355A CN105375759A CN 105375759 A CN105375759 A CN 105375759A CN 201510506355 A CN201510506355 A CN 201510506355A CN 105375759 A CN105375759 A CN 105375759A
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- switch transducer
- value
- electric parameter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
- H02M3/1586—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention relates to a method for parallel operation of at least a first self-oscillating switching converter (4) and a second self-oscillating switching converter (6), in which a value of a first electrical parameter of the first switching converter (4) is detected and compared with a limit value (Ithres) will, when the first electrical parameter reaches or exceeds the limit (Ithres) by the value of the first electrical parameter of the first switching converter (4), the second self-oscillating switching converter (6) is turned off, a value of the first electrical parameter of the second switching converter (6) is detected and is compared with the limit value (Ithres), and when the first electrical parameter reaches or exceeds the limit (Ithres) by the value of the first electrical parameter, the first self-oscillating switching converter (6) is turned off.
Description
Technical field
The present invention relates to for parallel running at least two self-oscillating switch transducers method and there is the circuit arrangement of two self-oscillating switch transducers.
Background technology
Known switch transducer.Dc-dc converter is for supplying such as the electric equipment of the control appliance of motor vehicles.At this, the 12V power supply on vehicle network voltage of the power supply on vehicle network of such as motor vehicles is transformed into such as 40V voltage by dc-dc converter.
Dc-dc converter can be configured to step-down controller and/or boost converter.
Namely step-down controller, also buck converter provides it to be highly less than the output voltage of the height of input voltage, and boost converter, also namely booster converter provides it to be highly greater than the output voltage of the height of input voltage.The combination be made up of step-down controller and boost converter is step-down and the boost converter that can set less and larger input voltage value.
Boost converter can have the inductance of such as coil form, this inductance and Diode series, and charging capacitor is cumulative output voltage after this diode.Inductance connects by switch element by means of such as thyristor, such as transistor over the ground.Input voltage declines at inductance place now, and the energy stored in the electric current of inductance and the magnetic field therefore at inductance raises.If thyristor is disconnected and being interrupted by electric current therefore through inductance, then inductance is attempted maintaining current strength by the disappearance of the energy in the magnetic field of inductance.The voltage of output end raises very fast, until its exceed charging capacitor place apply voltage and diode become conduction.Electric current flows further unchangeably in the first moment and charges to charging capacitor further.Magnetic field disappears at this and provides its energy, and its mode is that electric current is driven in charging capacitor by diode by magnetic field.
The thyristor of dc-dc converter can control by means of pulse-width modulation (PWM).In relating to the dc-dc converter of built-in oscillation.
Alternately, dc-dc converter also can run as self-oscillating switch transducer.The adjustment of self-oscillating switch transducer can reach by detecting or exceed lowest high-current value to carry out.Reach or exceed lowest high-current value, especially flow through the electric current of inductance time, deactivate the thyristor of dc-dc converter by turning off.So reclose or activating semiconductor switch element can by voltage over zero (ZeroVoltageSwitching(Zero voltage transition) – ZVS) or alternately current zero-crossing point (ZeroCurrentSwitching(zero-current switching) – ZCS) trigger, can switching loss be minimized thus.
But due to the ripple current occurred, it is level and smooth for voltage that this dc-dc converter (built-in oscillation and free-running) loads to the intermediate circuit of such as electrolytic capacitor.At this, ripple current is understood to the alternating current of optional frequency and curve form, and this alternating current is superimposed upon on direct current.This alternating current mainly appears at capacitor place below.
In order to reduce ripple current load, but two self-oscillating switch transducers can be run with along with phase shift, the time offsetting from each other concurrently.Because the cycle duration of self-oscillating switch transducer depends on its component, so cause the different cycle duration of two self-oscillating switch transducers due to inevitable component tolerance.This can cause the formation of beat (Schwebung), make to provide no longer constantly reduce ripple current load, temporal phase shift between two self-oscillating switch transducers.
Therefore demand is: a kind of control method is described, utilizes this control method can stop the formation of this beat.
Summary of the invention
According to the present invention, the Method and circuits device with the feature of independent claims is proposed.Favourable configurations is the theme of dependent claims and description below.
In the method at least one first self-oscillating switch transducer of parallel running and the second self-oscillating switch transducer, detect the value of the first electric parameter of the first dc-dc converter and compare with limiting value.The second self-oscillating switch transducer is deactivated when the value of the first electric parameter reaches or go beyond the limit of value.Also detect the value of the first electric parameter of second switch transducer and compare with limiting value and deactivate the first self-oscillating switch transducer when the value of the first electric parameter reaches or go beyond the limit of value.Guaranteed by simple especially mode surprisingly thus: do not form the beat because the time migration between two self-oscillating switch transducers causes.Therefore ripple current load is reduced.
Preferably, electric current is detected as the first electric parameter.But therefore use first parameter that simply will reliably detect in the process.
According to another execution mode, the first electric parameter is the coil current of the inductance of the first dc-dc converter or second switch transducer.Therefore the measurement parameter of coil current not by after the capacitor that connects and/or diode distort.This simplify measured value process.
According to another execution mode, use first thyristor that can manipulate to deactivate the first dc-dc converter and/or use second thyristor that can manipulate to deactivate second switch transducer.The described thyristor manipulated can be MOSFET, transistor (such as IGBT), thyristor (such as GTO thyristor).Therefore can service-strong standard element.
According to another execution mode, described limiting value is less than the maximum of described electric parameter when the first dc-dc converter activated and/or when the second switch transducer activated.At this, if dc-dc converter runs as self-oscillating switch transducer, the maximum of electric parameter is such as the maximum current intensity of the coil current of inductance.In addition, the breaking-up not caused the parts of self-oscillating switch transducer by overload is guaranteed thus.
According to another execution mode, activate the first dc-dc converter when the value of the first or second electric parameter of the first dc-dc converter is zero and/or activate second switch transducer when the value of the first or second electric parameter of second switch transducer is zero.Therefore, the activation of first and/or second switch transducer can be realized especially in measuring technique.As the second electric parameter, the voltage at the preferred detection especially inductance place of respective switch transducer.Therefore, turn-on time can be detected by the voltage over zero (ZeroVoltageSwitching(Zero voltage transition) – ZVS) of the zero crossing (ZeroCurrentSwitching(zero-current switching) – ZCS) of magnetic test coil electric current or such as inductance.Which reduce connection loss.
According to another execution mode, the phase shift between the time variations determining the time variations of the first electric parameter of the first dc-dc converter and the first electric parameter of second switch transducer.So so determine limiting value when analyzing phase shift, make to occur that the very first time changes to the phase shift of the duration of half period substantially of the second time variations.At this, " substantially " is understood to depart from 5%, 10% or 20%.Therefore limiting value can follow the trail of the aging operational factor change caused of the component of such as corresponding self-oscillating switch transducer.
Also belonging to of the present invention is the circuit arrangement with at least one first self-oscillating switch transducer and the second self-oscillating switch transducer, and this circuit arrangement is set to perform according to method of the present invention.
This method and this circuit arrangement such as can adopt in the motor vehicle, to give such as the boost capacitor supply voltage of such as known from DE102011085655A1 magnet injector, the voltage height of this voltage is positioned on the height of power supply on vehicle network of network voltage of these motor vehicles.
Additional advantage of the present invention and configurations are from describing and drawing appended accompanying drawing.
Be appreciated that feature that is aforesaid and that still will set forth with the compound mode illustrated respectively and with other compound mode or can not only use individually below, and do not leaving scope of the present invention.
Schematically show in the accompanying drawings according to embodiment and describe the present invention in detail with reference to the accompanying drawings.
Accompanying drawing explanation
Fig. 1 has illustrated the circuit arrangement with two parallel self-oscillating switch transducers in indicative icon.
Fig. 2 has illustrated the current-vs-time figure when the circuit arrangement of parallel running Fig. 1 in indicative icon.
Embodiment
Fig. 1 has illustrated for by input direct voltage U in indicative icon
battconvert output dc voltage U to
bocircuit arrangement 2.It is (English: BoostConverter) that this circuit arrangement 2 is constructed to boost converter in the present embodiment.Output dc voltage U
bonumerical value be greater than input direct voltage U
battnumerical value.
Circuit arrangement 2 can be adopted, to give such as the boost capacitor supply output dc voltage U of magnet injector in motor vehicles (not shown)
bo, the voltage height of this output dc voltage is at input direct voltage U
batton and therefore on the vehicle power network of network voltage of motor vehicles.
In the present embodiment, circuit arrangement 2 has the first self-oscillating switch transducer 4, the second switch transducer 6 in parallel with the first dc-dc converter 4 and input buffer cell 8, and this input buffer cell is at input side and input voltage U
battconnect, and input buffer cell 8 is connected with two self-oscillating switch transducers 4,6 at outlet side.Described two self-oscillating switch transducers 4,6 provide output dc voltage U
bo.
Input buffer cell 8 is for level and smooth input voltage U
batt.To this, input buffer cell 8 has input capacitor C in the present embodiment
e, input inductance L
ewith output capacitor C
a.In the present embodiment, output capacitor C
afor smmothing capacitor, such as, it is electrolytic capacitor.
Described two self-oscillating switch transducers 4,6 have identical structure.Two self-oscillating switch transducers 4,6 have each inductance L for voltage transfer in the present embodiment
1, L
2.
Inductance L
1, L
2be connected conductively at the output of input side with input buffer cell 8 respectively.Inductance L
1, L
2at outlet side and each thyristor T
1, T
2connect conductively.Thyristor T
1, T
2be respectively MOSFET in the present embodiment.Also other thyristor as transistor (such as IGBT) or thyristor (such as GTO thyristor) can be used.
At outlet side at thyristor T
1, T
2place arranges each capacitor C
r1, C
r2, each diode D
1, D
2with each charging capacitor C
bo1, C
bo2.Capacitor C
r1, C
r2respectively with affiliated inductance L
1, L
2form oscillating circuit, realize ZVS method thus, thus T
1, T
2connection loss be retained as minimum.Idle running diode D
1, D
2stop charging capacitor C
bo1, C
bo2electric discharge.
Charging capacitor C
bo1, C
bo2be electrolytic capacitor in the present embodiment.Such as MOSFET, transistor (such as IGBT) or thyristor (such as GTO thyristor) can be used to replace diode D
1, D
2carry out rectification on one's own initiative, to form synchronous converter.
The parallel running of circuit arrangement 2 is described according to Fig. 1 and 2 now.
Input voltage U
battlevel and smooth by input buffer cell 8.Then, thyristor T is utilized
1, T
2limit and be applied to inductance L
1, L
2the voltage at place.To this, thyristor T
1, T
2manipulated by drive circuit (not shown).This drive circuit can be a part for the control appliance of motor vehicles.Drive circuit and/or control appliance can have hardware and/or software part.
Inductance L
1, L
2by thyristor T
1, T
2connect over the ground.The output voltage of input buffer cell 8 falls inductance L now
1, L
2place.Corresponding coil current I
l1, I
l2and therefore in inductance L
1, L
2magnetic field in the energy fluence that stores respectively increase.If thyristor T
1, T
2disconnect, then inductance L
1, L
2attempt maintenance and pass through electric current.The voltage at the respective secondary end place of described inductance raises very fast, until this voltage exceedes be applied to charging capacitor C
bo1, C
bo2place relevant voltage and respective diode D
1, D
2disconnect.Corresponding coil current I
l1, I
l2the first moment unchangeably further flowing and further give corresponding charging capacitor C
bo1, C
bo2charging.Magnetic field disappears at this and provides its energy, and its mode is that magnetic field is by coil current I
l1, I
l2by respective diode D
1, D
2be driven into charging capacitor C
bo1, C
bo2in.
In order to reduce especially output capacitor C
adue to thyristor T
1, T
2the ripple current load that causes of handoff procedure, but concurrently the time runs two free-running dc-dc converters 4,6 with offsetting from each other.
So the first thyristor T is manipulated to this
1with the second thyristor T
2, make the First Line loop current I at the first electric parameter as the first dc-dc converter 4
l1time variations I and the second coil current I of the first electric parameter as second switch transducer 6
l2time variations II between draw phase shift Δ T, this phase shift is corresponding half period duration T substantially, because so draw minimum ripple current load, and there is maximum ripple current load when phase shift Δ T is zero.The phase shift Δ T departing from 5%, 10% or 20% is understood to this " substantially ".
In order to ensure the phase shift Δ T of half period duration T substantially, measuring unit (not shown) is utilized to measure the inductance L of second switch transducer 6 when the first self-oscillating switch transducer 4 runs
2the second coil current I
l2and utilize comparing unit (not shown) and limiting value I
thresrelatively.
If drawn described comparison when the first dc-dc converter 4 is active: the second coil current I
l2go beyond the limit of value I
thres, then the thyristor T of the first self-oscillating switch transducer 4
1driven circuit is by turning off deactivation.
On the contrary, First Line loop current I is detected when second switch transducer 6 is active
l1whether go beyond the limit of value I
thres.If First Line loop current I
l1go beyond the limit of value I
thres, then the thyristor T of the second self-oscillation transducer 6
2driven circuit is by turning off deactivation.Therefore avoided the formation of beat by simple mode, otherwise this beat causes especially output capacitor C
athe ripple current load of rising.Therefore such as output capacitor C can smaller be determined
asize.
After turning off deactivation two thyristors by driven circuit, these two thyristor T
1, T
2turn-on time point can by detecting as the coil current I of the first electric parameter
l1, I
l2zero crossing (ZeroCurrentSwitching(zero-current switching) – ZCS) or alternately trigger as the voltage over zero (ZeroVoltageSwitching(Zero voltage transition) – ZVS) of the second electric parameter.If therefore such as First Line loop current I
l1be zero, then the first thyristor T1 is switched on again, and if the second coil current I
l2be zero, then the second thyristor T2 is switched on again.Therefore the first dc-dc converter 4 and second switch transducer 6 alternately influence each other when deactivating, and this does not occur when activating or connect the first dc-dc converter 4 and second switch transducer 6.
Limiting value I
thresit can be the value of fixed size.Alternately can specify, determine the inductance L of the first dc-dc converter 4
1coil current I
l1time variations I and the inductance L of second switch transducer 6
2coil current I
l2time variations II between phase shift Δ T.Described limiting value I is determined like this after the described phase shift Δ T of analysis
thres, make the phase shift Δ T of the duration T of half period substantially appeared between very first time change the I to the second time variations II.Therefore limiting value I
thresthe aging operational factor change caused of the component of such as corresponding self-oscillating switch transducer 4,6 can be followed the trail of.
If the first dc-dc converter 4 is constructed by component identical respectively with second switch transducer 6, then can specify unique limiting value I for the first dc-dc converter 4 and second switch transducer 6
thres.And if the first dc-dc converter 4 and second switch transducer 6 are constructed by different components, then can the first limiting value be specified for the first dc-dc converter 4 and specify the second limiting value for second switch transducer 6.
Claims (9)
1. for the method for at least one first self-oscillating switch transducer (4) of parallel running and the second self-oscillating switch transducer (6), wherein detect the first electric parameter of the first dc-dc converter (4) value and with limiting value (I
thres) compare, reach in the value of the first electric parameter of the first dc-dc converter (4) or go beyond the limit of value (I
thres) time deactivate the second self-oscillating switch transducer (6), detect second switch transducer (6) the first electric parameter value and with limiting value (I
thres) compare, and reach in the value of the first electric parameter of second switch transducer (6) or go beyond the limit of value (I
thres) time deactivate the first self-oscillating switch transducer (4).
2. method according to claim 1, wherein detects as the first electric parameter and analyzes electric current.
3. method according to claim 2, wherein said electric current is the inductance (L of the first dc-dc converter (4)
1) coil current (I
l1) and/or the inductance (L of second switch transducer (6)
2) coil current (I
l2).
4., according to the method one of aforementioned claim Suo Shu, wherein use the first switch element (T that can manipulate to deactivate the first dc-dc converter (4)
1) and/or use the second switch element (T that can manipulate to deactivate second switch transducer (6)
2).
5. according to the method one of aforementioned claim Suo Shu, wherein limiting value (I
thres) second switch transducer (6) when the first dc-dc converter (4) of non-deactivation and/or in non-deactivation be less than the maximum of described electric parameter.
6. according to the method one of aforementioned claim Suo Shu, if wherein the first or second electric parameter of the first dc-dc converter (4) is zero, then activate the first dc-dc converter (4), if and/or the first or second electric parameter of wherein second switch transducer (6) is zero, then activate second switch transducer (6).
7. method according to claim 6, wherein detects and analytical voltage as the second electric parameter.
8. according to the method one of aforementioned claim Suo Shu, determine the phase shift (Δ T) between the time variations (I) of the first electric parameter of the first dc-dc converter (4) and the time variations (II) of the first electric parameter of second switch transducer (6) in the method, and so determine limiting value (I when analyzing described phase shift (Δ T)
thres), make the phase shift (Δ T) occurring very first time change (I) to the duration of half period substantially (T) of the second time variations (II).
9. have the circuit arrangement (2) of at least one first self-oscillating switch transducer (4) and the second self-oscillating switch transducer (6), this circuit arrangement is arranged for and performs according to the method one of aforementioned claim Suo Shu.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| DE102014216405.2A DE102014216405B4 (en) | 2014-08-19 | 2014-08-19 | Control procedure for the parallel operation of at least two self-oscillating switching converters |
| DE102014216405.2 | 2014-08-19 |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN105375759A true CN105375759A (en) | 2016-03-02 |
| CN105375759B CN105375759B (en) | 2019-07-16 |
Family
ID=55273778
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201510506355.2A Active CN105375759B (en) | 2014-08-19 | 2015-08-18 | For running the adjusting method of at least two self-oscillating switch converters parallel |
Country Status (2)
| Country | Link |
|---|---|
| CN (1) | CN105375759B (en) |
| DE (1) | DE102014216405B4 (en) |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20020011824A1 (en) * | 2000-07-06 | 2002-01-31 | Sluijs Ferdinand Jacob | Multi-output DC/DC converter in PFM/PWM mode |
| CN202309521U (en) * | 2011-09-23 | 2012-07-04 | 东南大学 | Control circuit for single-inductance dual-output switching power supply |
| CN103490630A (en) * | 2013-09-16 | 2014-01-01 | 矽力杰半导体技术(杭州)有限公司 | Control circuit and control method for staggered parallel type switching power supply |
| TWI433439B (en) * | 2011-03-07 | 2014-04-01 | Au Optronics Corp | Dc/dc boost converter |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE102005045889B4 (en) | 2005-09-26 | 2008-11-20 | Continental Automotive Gmbh | Polyphase DC-DC controller and method for operating a polyphase DC-DC controller |
| DE102011085655A1 (en) | 2011-11-03 | 2013-05-08 | Osram Gmbh | Illumination device with semiconductor light sources |
-
2014
- 2014-08-19 DE DE102014216405.2A patent/DE102014216405B4/en active Active
-
2015
- 2015-08-18 CN CN201510506355.2A patent/CN105375759B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20020011824A1 (en) * | 2000-07-06 | 2002-01-31 | Sluijs Ferdinand Jacob | Multi-output DC/DC converter in PFM/PWM mode |
| TWI433439B (en) * | 2011-03-07 | 2014-04-01 | Au Optronics Corp | Dc/dc boost converter |
| CN202309521U (en) * | 2011-09-23 | 2012-07-04 | 东南大学 | Control circuit for single-inductance dual-output switching power supply |
| CN103490630A (en) * | 2013-09-16 | 2014-01-01 | 矽力杰半导体技术(杭州)有限公司 | Control circuit and control method for staggered parallel type switching power supply |
Also Published As
| Publication number | Publication date |
|---|---|
| DE102014216405B4 (en) | 2023-05-25 |
| CN105375759B (en) | 2019-07-16 |
| DE102014216405A1 (en) | 2016-02-25 |
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